Datasheet MC33364D, MC33364D1, MC33364D2 Datasheet (Motorola)

Order this document by MC33364/D

 

 
  

The MC33364 series are variable frequency SMPS controllers that operate
in the critical conduction mode. They are optimized for low power, high density
power supplies requiring minimum board area, reduced component count,
and low power dissipation. Each narrow body SOIC package provides a small
footprint. Integration of the high voltage startup saves approximately 0.7 W of
power compared to resistor bootstrapped circuits.

Each MC33364 features an on–board reference, UVLO function, a
watchdog timer to initiate output switching, a zero current detector to ensure
critical conduction operation, a current sensing comparator, leading edge
blanking, and a CMOS driver. Protection features include the ability to shut
down switching, and cycle–by–cycle current limiting.

The MC33364D1 is available in a surface mount SO–8 package. It has an
internal 126 kHz frequency clamp. For loads which have a low power
operating condition, the frequency clamp limits the maximum operating
frequency , preventing excessive switching losses and EMI radiation.

The MC33364D2 is available in the SO–8 package without an internal
frequency clamp.

The MC33364D is available in the SO–16 package. It has an internal
126 kHz frequency clamp which is pinned out, so that the designer can
adjust the clamp frequency by connecting appropriate values of resistance.

• Lossless Off–Line Startup

• Leading Edge Blanking for Noise Immunity

• Watchdog T imer to Initiate Switching

• Minimum Number of Support Components

• Shutdown Capability

• Over Temperature Protection

• Optional Frequency Clamp



CRITICAL CONDUCTION

GREENLINE SMPS

CONTROLLER

SEMICONDUCTOR

TECHNICAL DATA

8

1

D1, D2 SUFFIX

PLASTIC PACKAGE

CASE 751

(SO–8)

16

1

D SUFFIX

PLASTIC PACKAGE

CASE 751B

(SO–16)

PIN CONNECTIONS

ORDERING INFORMATION

Operating

Device

MC33364D1
MC33364D2
MC33364D SO–16

Temperature Range

TJ = –25° to +125°C

Package

SO–8
SO–8

Representative Block Diagram

Restart

Delay

PWM

Comparator

FB

Current

Sense

ZC Det

This document contains information on a new product. Specifications and information herein
are subject to change without notice.

MOTOROLA ANALOG IC DEVICE DATA

Leading

Edge

Blanking

Zero

Current

Detector

This device contains 335 active transistors.

S
R

Q

R

Watchdog

Timer

Thermal

Shutdown

V

ref

UVLO

V

UVLO

Bandgap

Reference

Frequency

Clamp

CC

Line

V

CC

V

ref

Gnd

Gate

Optional
Frequency
Clamp

MC33364D1
MC33364D2

Zero Current

Current Sense

Voltage FB

Zero Current

Current Sense

Voltage FB

Freq Clamp

 Motorola, Inc. 1997 Rev 0

18
2
3

V

4

ref

(Top View)

MC33364D

116

N/C

2
3
4

N/C

5

V

6

ref

7

N/C

8

(Top View)

Line
V

7

CC

Gate Drive

6

P Gnd

5

Line

A V

13

CC

P V

12

CC

11

Gate Drive

10

P Gnd

9

A Gnd

1

MAXIMUM RATINGS

Á

Á

Á

Á

Á

Á

Á

Á

Á

Á

Á

Á

ÁÁÁ
ÁÁÁ

ÁÁÁ

ÁÁÁ

ÁÁÁ

ÁÁÁ

ÁÁÁ

ÁÁÁ

Á

Á

Á

Á

Á

ÁÁÁ

Á

Á

Á

Á

Á

Á

ÁÁÁ

Á

Á

Á

Á

Á

Á

ÁÁÁ

Á

Á

Á

Á

Á

Á

ÁÁÁ

Á

ÁÁÁ

ÁÁÁ

ÁÁÁ

ÁÁÁ

ÁÁÁ

(TA = 25°C, unless otherwise noted.)

Rating Symbol Value Unit

Power Supply Voltage (Transient)
Power Supply Voltage (Operating)
Line Voltage
Current Sense, Compensation,

Voltage Feedback, Restart Delay and Zero

Current Input Voltage
Zero Current Detect Input
Restart Diode Current
Power Dissipation and Thermal Characteristics

D1 and D2 Suffix, Plastic Package Case 751

Maximum Power Dissipation @ TA = 70°C P
Thermal Resistance, Junction–to–Air R

D Suffix, Plastic Package Case 751B–05

Maximum Power Dissipation @ TA = 70°C P
Thermal Resistance, Junction–to–Air R

Operating Junction Temperature

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Operating Ambient Temperature

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Storage Temperature Range

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NOTE: ESD data available upon request.

V

CC

V

CC

V

Line

V

in1

I

in

I

in

D

θJA

D

θJA

T

J

ÁÁ

T

A

ÁÁ

T

stg

ÁÁ

MC33364

700

–1.0 to +10 V

±5.0

450 mW
178 °C/W

550 mW
145 °C/W

150

ÁÁÁ

–25 to +125

ÁÁÁ

–55 to +150

ÁÁÁ

20
16

5.0

mA
mA

°C

Á

°C

Á

°C

Á

V
V
V

ELECTRICAL CHARACTERISTICS (V

= 12 V, for typical values TA = 25°C, for min/max values TJ = –25 to 125°C)

CC

Characteristic

VOLTAGE REFERENCE

Reference Output Voltage (I

= 0 mA, TJ = 25°C)

Out

Line Regulation (VCC = 10 V to 20 V)
Load Regulation (I
Maximum V

ref

= 0 mA to 5.0 mA)

Out

Output Current

Reference Undervoltage Lockout Threshold

ZERO CURRENT DETECTOR

Input Threshold Voltage (Vin Increasing)
Hysteresis (Vin Decreasing)
Input Clamp Voltage

High State (I
Low State (I

= 3.0 mA) V

DET

= –3.0 mA) V

DET

CURRENT SENSE COMPARATOR

Input Bias Current (VCS = 0 to 2.0 V)

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Built In Offset

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Feedback Pin Input Range

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Feedback Pin to Output Delay

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DRIVE OUTPUT

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Source Resistance (Drive = 0 V, V
Sink Resistance (Drive = VCC, V

= VCC – 1.0 V)

Gate

= 1.0 V) R

Gate

Output Voltage Rise T ime (25% – 75%) (CL = 1.0 nF)
Output Voltage Fall Time (75% – 25%) (CL = 1.0 nF)
Output Voltage in Undervoltage (VCC = 7.0 V, I

Sink

= 1.0 mA)

Symbol Min Typ Max Unit

V

ref

Reg

line

Reg

load

I

O

V

th

V

th

V

H

IH
IL

I

IB

ÁÁÁ

V

IO

ÁÁÁ

V

FB

ÁÁÁ

t

DLY

ÁÁÁ

ÁÁÁ

R

OH
OL

t

r

t

f

V

O(UV)

4.90
–
–
–
–

0.9
–

5.05

2.0

0.3
5

4.5

1.0

200

5.20
50
50

–
–

1.1
–

9.0 10.33 12

–0.5 –0.75 –1.1

–0.5

ÁÁÁ

50

ÁÁÁ

1.1

ÁÁÁ

100

ÁÁÁ

ÁÁÁ

10

0.02

ÁÁÁ

108

ÁÁÁ

1.24

ÁÁÁ

232

ÁÁÁ

ÁÁÁ

36

0.5

ÁÁ

170

ÁÁ

1.4

ÁÁ

400

ÁÁ

ÁÁ

70

5 11 25 Ω
–

–
–

67
28

0.01

150

50

0.03

ÁÁ

ÁÁ

ÁÁ

ÁÁ

ÁÁ

V
mV
mV
mA

V

V
mV

V

µA

mV

V

ns

Ω

ns
ns

V

2

MOTOROLA ANALOG IC DEVICE DATA

MC33364

ÁÁÁ

ÁÁÁ

ÁÁÁ

ÁÁÁ

ÁÁÁ

ÁÁÁ

Á

Á

Á

Á

Á

ÁÁÁ

Á

Á

Á

Á

Á

Á

ÁÁÁ

Á

ÁÁÁ

ÁÁÁ

ÁÁÁ

ÁÁÁ
ÁÁÁ

ÁÁÁ

ÁÁÁ

Á

Á

Á

Á

Á

ÁÁÁ

Á

ÁÁÁ

ELECTRICAL CHARACTERISTICS (continued) (V

= 12 V, for typical values TA = 25°C, for min/max values TJ = –25 to 125°C)

CC

Characteristic UnitMaxTypMinSymbol

LEADING EDGE BLANKING

Delay to Current Sense Comparator Input

(VFB = 2.0 V, VCS = 0 V to 4.0 V step, CL = 1.0 nF)

TIMER

Watchdog Timer

UNDERVOLTAGE LOCKOUT

Startup Threshold (VCC Increasing)

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Minimum Operating Voltage After Turn–On (VCC Decreasing)

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FREQUENCY CLAMP

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Internal FC Function (pin open)

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Internal FC Function (pin grounded)

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Frequency Clamp Input Threshold

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Frequency Clamp Control Current Range

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TOTAL DEVICE

Line Startup Current (V

= 50 V) (VCC = V

Line

th(on)

– 1.0 V)

Restart Delay Time t
Line Pin Leakage (V

Line Startup Current (VCC = 0 V, V

= 575 V) I

Line

= 50 V) I

Line

VCC Dynamic Operating Current (50 kHz, CL = 1.0 nF)
VCC Static Operating Current (VCC = 16 V, V

БББББББББББББББ

ref

= 0)

VCC Pin Leakage (VCC = 11 V)

t

PHL(in/out)

t

DLY

V

th(on)

ÁÁÁ

V

Shutdown

ÁÁÁ

ÁÁÁ

f

max

ÁÁÁ

f

max

ÁÁÁ

V

th(FC)

ÁÁÁ

I

Control

ÁÁÁ

I

Line
DLY

Line
Line

I

CC

ÁÁÁ

ICC

Lkg

–

200

14

ÁÁÁ

6.5

ÁÁÁ

ÁÁÁ

ÁÁÁ90ÁÁÁ

400

ÁÁÁ

ÁÁÁ–ÁÁÁ

ÁÁÁ30ÁÁÁ70ÁÁ

5.0

250

410

15

ÁÁÁ

7.6

ÁÁÁ

ÁÁÁ

126
564

ÁÁÁ

2.0

8.5

700

16

ÁÁ

8.5

ÁÁ

ÁÁ

160

ÁÁ

700

ÁÁ

–

ÁÁ

110

12

100 ms

0.5 32 70 µA

6.0 10 12 mA

1.5
–

ÁÁÁ

300

2.75

3.0

ÁÁÁ

544

4.5
–

ÁÁ

800

ns

µs

V

ÁÁ

V

ÁÁ

ÁÁ

kHz

ÁÁ

kHz

ÁÁ

V

ÁÁ

µA

ÁÁ

mA

mA

ÁÁ

µA

MOTOROLA ANALOG IC DEVICE DATA

3

MC33364

0

5

OUTPUT VOLTAGE (V)

30
25
20
15

10

5.0

–5.0

16

12

8.0

Figure 1. Drive Output Waveform

Figure 2. Watchdog Timer Delay

versus T emperature

VCC = 14 V
CL = 1000 pF

°

C

TA = 25

0

5.0 µs/DIV

Figure 3. Reference V oltage

versus T emperature

VCC = 14 V

µ

, WATCHDOG TIME DELAY ( s)

DLY

t

500

450

400

350

300

–55

6.0

4.0
Circuit of Figure 7
TA = 25

VCC = 14 V

–25 0 25 50 75 100 12

TA, AMBIENT TEMPERATURE (°C)

Figure 4. Supply Current

versus Supply V oltage

°

C

4.0

, VOLTAGE FEEDBACK

FB

V

THRESHOLD CHANGE (mV)

5.0

∆

–4.0

–55

–25 0 25 50 75 125100

TA, AMBIENT TEMPERATURE (°C)

Figure 5. Transient Thermal Resistance

1000

D Suffix
16 Pin SOIC

°

100

, THERMAL RESISTANCE

JA(t)

JUNCTION–TO–AIR ( C/W)

θ

R

10

0.01

0.1 1.0 10 100
t, TIME (s)

2.0

, SUPPLY CURRENT (mA)

CC

I

0

4.0

1000

µ

100

10

1.0

, PROGRAMMED DEAD TIME ( sec)

d

T

0.1

0.1

6.0 8.0 10 12 14 16
VCC, SUPPLY VOLTAGE (V)

Figure 6. Dead Time

versus Input Current

D Suffix
16 Pin SOIC

°

C

TA = 25
VCC = 14 V

1.0 10 100 100

Iin, CURRENT SOURCED INTO PIN 8 (µA)

4

MOTOROLA ANALOG IC DEVICE DATA

MC33364

FUNCTIONAL DESCRIPTION

INTRODUCTION

With the goal of reducing the size and cost of off–line
power supplies, there is an ever increasing demand for an
economical method of obtaining a regulated galvanically
isolated dc output voltage using a control which operates

Figure 7. Functional Block Diagram

C5
10

D3
1N4006

92 to

270 Vac

EMI

Filter

1N4006

D2

D1

1N4006

1N4006

D4

MC33364

R2

22 k

1.5 V

UVLO

UVLO

+

Leading

Blanking

44 K

14 K

V

CC

5.0 V

Reference

Zero Current

Frequency

Clamp

C2

0.01

D9
1N4148

R13
100

4.0 K
10 V

Zero
Current
Detect

0.3/

0.25 V

2.0 V

RQ

Timer

R

Q

R

Q

S

En

5.0 V

10 pF

3.0

R
S

µ

Q

A

2.0 V

Line

+

15/7.6

Edge

5.0 k

A Gnd

directly from the ac line. This data sheet describes a
monolithic control IC that was specifically designed for power
supply control with a minimal number of external
components. It offers the designer a simple cost effective
solution to obtain the benefits of off–line power regulation.

T1

En

C3

V

CC

P V

Gate Drive

P Gnd

Current
Sense

Voltage FB

V

ref

1N4934

20

+

D5

CC

R1 56

R5 47 k

R6
47 K

470 R4

D7
1N4148

R12 100

C9 .01

C4
.001

R3

1.2 K

C10

0.1

D6
MURS160T3

Q1

MTD1N60

R7

2.2

D8
MBRS340T3

C5
300

U3

MOC8102

VO+

5

39 k

U2
TL431

2.5

R9

R8
430

R10
14 k

1
24

C7
10

2

R10
R11

C8
330 pF

1

R11
10 k

Ǔ

)

1

3

ǒ

6.0 V
2 Amp

Operating Description

The MC33364 contains many of the building blocks and
protection features that are employed in modern high
performance current mode power supply controllers.
Referring to the block diagram in Figure 7, note that this
device does not contain an oscillator. A description of each of
the functional blocks is given below.

Zero Current Detector

The MC33364 operates as a critical conduction current
mode controller, whereby output switch conduction is
initiated by the Zero Current Detector and terminated when
the peak inductor current reaches the input threshold level.
The Zero Current Detector initiates the next on–time by

MOTOROLA ANALOG IC DEVICE DATA

setting the RS Latch at the instant the inductor current
reaches zero. This critical conduction mode of operation has
two significant benefits. First, since the MOSFET cannot
turn–on until the inductor current reaches zero, the output
rectifier’s reverse recovery time becomes less critical
allowing the use of an inexpensive rectifier. Second, since
there are no deadtime gaps between cycles, the ac line
current is continuous thus limiting the peak switch to twice
the average input current

The Zero Current Detector indirectly senses the inductor
current by monitoring when the auxiliary winding voltage falls
below 0.25 V . To prevent false tripping, 50 mV of hysteresis is
provided. The Zero Current Detector input is internally

5

MC33364

protected by two clamps. The upper 0.7 V clamp prevents
input overvoltage breakdown while the lower –0.7 V clamp
prevents substrate injection. An external resistor must be
used in series with the auxiliary winding to limit the current
through the clamps to 5.0 mA or less.

Current Sense Comparator and RS Latch

The Current Sense Comparator RS Latch configuration
used ensures that only a single pulse appears at the Drive
Output during a given cycle. The inductor current is
converted to a voltage by inserting a ground–referenced
sense resistor in series with the source of output switch. This
voltage is monitored by the Current Sense Input and
compared to the divided down feedback voltage. The internal
feedback voltage divider is limited to 1.5 V maximum.
Therefore the maximum peak switch current is:

I

pk(max)

The Current Sense Input to Drive Output propagation
delay is typically 232 nS.

Timer

A watchdog timer function was added to the IC to eliminate
the need for an external oscillator when used in stand alone
applications. The Timer provides a means to automatically
start or restart the preconverter if the Drive Output has been
off for more than 410 microseconds after the inductor current
reaches zero.

Undervoltage Lockout

The MC33364 has a 5.0 V internal reference brought out
to Pin 6 (D Suffix) or Pin 4 (D1 and D2 Suffixes) and capable
of sourcing 10 mA typically . It also contains an Under V oltage
Lockout (UVLO) circuit which suppresses the Gate output at
Pin 1 1 if the VCC supply voltage drops below 7.6 V typical.

Restart Delay

A restart delay function is provided to allow hiccup mode
fault protection in case of a short circuit condition and to
prevent the SMPS from repeatedly trying to restart after the
input line voltage has been removed. When power is first
applied, the VCC bypass capacitor is charged through a
constant current source. The Restart Delay turns off the high
voltage startup MOSFET when VCC reaches the startup
threshold level. The Restart Delay turns on the high voltage
MOSFET after VCC has dropped below 4.5 V.

If the SMPS output is short circuited, the transformer
winding, which provides the VCC voltage to the MC33364, will
be unable to sustain VCC. The restart delay prevents the high
voltage startup transistor within the IC from maintaining the
voltage on the VCC pin bootstrap capacitor. After VCC drops
below the UVLO threshold in the SMPS, the SMPS switching
transistors are held off for the time programmed by the restart
delay circuit. In this manner, the SMPS switching transistor is
operated at a very low duty cyle, preventing destruction. If
the short circuit fault is removed, the power supply system
will turn on by itself in a normal startup mode after the restart
delay has timed out

+

1.5 V

R

Sense

Figure 8. Frequency Clamp Circuit

5.0 V

µ

A

10 pF

3.0
0 = Disable

FC Output
to PWM latch

2.0 V

Frequency
Clamp

4.0 k

2.0 V
Gate

Drive

Signal

Output Switching Frequency Clamp

In normal operation, the MC33364 operates the flyback
transformer primary inductance in the critical mode. That is,
the inductor current ramps to a peak value, ramps down to
zero, then immediately begins ramping positive again. The
peak current is programmed by the current sense resistance
value. If the output load is reduced from full load to a standby
load or no load condition, the switching frequency can
increase to hundreds of kilohertz. Because regulatory
agency EMI limits for allowed conducted current decreases
as the switching frequency increases beyond 150 kHz, this
may be an undesireable operating condition. The Output
Switching Frequency Clamp remedies this situation to
minimize EMI generated in this operating region. The internal
frequency clamp circuit in the MC33364D1 and MC33364D
programs a minimum off time, forcing discontinuous mode
operation and limiting the operating frequency to less than
126 kHz. The MC33364D2 does NOT contain a frequency
clamp circuit. The Output Switching Frequency Clamp
function in the MC33364D can be disabled by connecting the
FC input, Pin 8, to ground. The clamp frequency can be set
externally by sinking or sourcing a current into the pin of up to
100 microamperes.

Output

The IC contains a CMOS output driver specifically
designed for direct drive of power MOSFETs. The Drive
Output is capable of up to ±1500 mA peak current with a
typical rise and fall time of 50 nS with a 1.0 nF load. Additional
internal circuitry has been added to keep the Drive Output in
a sinking mode whenever the Undervoltage Lockout is
active. This characteristic eliminates the need for an external
gate pull–down resistor. The totem–pole output has been
optimized to minimize cross–conduction current during high
speed operation.

Design Example

Design an off–line Flyback converter according to the
following requirements:

Output Power: 12 W

Output: 6.0 V @ 2 Amperes

Input voltage range: 90 Vac – 270 Vac, 50/60 Hz

The operation for the circuit shown in Figure 9 is as
follows: the rectifier bridge D1–D4 and the capacitor C1
convert the ac line voltage to dc. This voltage supplies the
primary winding of the transformer T1 and the startup circuit

6

MOTOROLA ANALOG IC DEVICE DATA

MC33364

in U1 through Pin 8. The primary current loop is closed by the
transformer’s primary winding, the TMOS switch Q1 and the
current sense resistor R7. The switch Q1 is driven from Pin 6
of U1 through the resistor R4 and the diode D7. The resistor
R4 smooths the switch–on of Q1. The diode D7 ensures a
fast switching–off. The resistors R5, R6, diode D6 and
capacitor C4 create a clamping network that protects Q1
from spikes on the primary winding. The network consisting
of capacitor C3, diode D5 and resistor R1 provides a V
supply voltage for U1 from the auxiliary winding of the
transformer. The resistor R1 makes VCC more stable and
resistant to noise. The resistor R2 reduces the current flow
through the internal clamping and protection zener diode of
the Zero Crossing Detector (ZCD) within U1. C3 is the
decoupling capacitor of the supply voltage. The resistor R3
provides bias current for the optoisolator’s transistor. The
diode D8 and the capacitor C5 rectify and filter the output
voltage. The device U2 drives the primary side through the
optoisolator to make the output voltage stable. The output
voltage information is delivered to U2 by a resistive divider
that consists of resistors R10 and R11. The resistor R9 and
the capacitors C7, C8 provide frequency compensation of the
feedback loop.

Since the critical conduction mode converter is a variable
frequency system, the MC33364 has a built–in special block
to reduce switching frequency in the no load condition. This
block is named the ”frequency clamp” block. MC33364 used
in the design example has an internal frequency clamp set to
126 kHz. However, optional versions with a disabled or
variable frequency clamp are available. The frequency clamp
works as follows: the clamp controls the part of the switching
cycle when the MOSFET switch is turned off. If this ”off–time”
(determined by the reset time of the transformer’s core) is too
short, then the frequency clamp does not allow the switch to
turn–on again until the defined frequency clamp time is
reached (i.e., the frequency clamp will insert a dead time).

There are several advantages of the MC33364’s startup
circuit. The startup circuit includes a special high voltage
switch that controls the path between the rectified line
voltage and the VCC supply capacitor to charge that capacitor
by a limited current when the power is applied to the input.
After a few switching cycles the IC is supplied from the
transformer’s auxiliary winding. After VCC reaches the
undervoltage lockout threshold value, the startup switch is
turned off by the undervoltage and the overvoltage control
circuit. Because the power supply can be shorted on the
output, causing the auxiliary voltage to be zero, the MC33364
will periodically start its startup block. This mode is named
”hiccup mode”. During this mode the temperature of the chip
rises but remains protected by the thermal shutdown block.
During the power supply’s normal operation, the high voltage
internal MOSFET is turned off, preventing wasted power , and
thereby , allowing greater circuit efficiency.

Since a bridge rectifier is used, the resulting minimum and
maximum dc input voltages can be calculated:

V

in(min)

V

in(max)

Ǹ

dc+2

Ǹ

dc+2

xV

xV

in(min)

in(max)

ac

ac

Ǹ

+ǒ2

Ǹ

+ǒ2

Ǔ

(

90 Vac)+

Ǔ

(

270 Vac)+

CC

127 V

382 V

The maximum average input current is:

P

Iin+

where n = estimated circuit efficiency.

A TMOS switch with 600 V avalanche breakdown voltage
is used. The voltage on the switch’s drain consists of the
input voltage and the flyback voltage of the transformer’s
primary winding. There is a ringing on the rising edge’s top of
the flyback voltage due to the leakage inductance of the
transformer. This ringing is clamped by the RCD network.
Design this clamped wave for an amplitude of 50 V. Add
another 50 V to allow a safety margin for the MOSFET. Then
a suitable value of the flyback voltage may be calculated:

V

flbk

Since this value is very close to the V

V

flbk

The V

ē

max

The maximum input primary peak current:

I

ppk

Choose the desired minimum frequency f
to be 70 kHz.

After reviewing the core sizing information provided by a
core manufacturer, a EE core of size about 20 mm was
chosen. Siemens’ N67 magnetic material is used, which
corresponds to a Philips 3C85 or TDK PC40 material.

The primary inductance value is given by:

Lp+

The manufacturer recommends for that magnetic core a
maximum operating flux density of:

B

max

The cross–sectional area Ac of the EF20 core is:

Ac+

The operating flux density is given by:

B

max

From this equation the number of turns of the primary
winding can be derived:

np+

out

ƪ

nV

+

600 V*382 V*100 V+118 V

+

flbk

+

V

2I

+

[

ē

ē

max V

ǒ

I

ppk

+

33.5 mm

+

LpI

B

maxAc

ƫ

in(min)

V

TMOS

V

in(min)

value of the duty cycle is given by:

V

flbk

)

flbk

in

+

]

max

in(min)

ǒ

Ǔ

f

min

0.2 T

2

LpI

ppk

NpA

c

ppk

12 W

+

[

0.8(127 V

*

V

in(max)

+

127 V

V

in(min)

0.2(0.118 A

+

0.5

+

(

0.472 A)(70 kHz

Ǔ

+

0.118 A

)]

*

100 V

in(min)

127 V

[

127 V)127 V

)

+

0.472 A

0.5(127 V

)

+

, set:

+

]

of operation

min

+

1.92 mH

)

0.5

MOTOROLA ANALOG IC DEVICE DATA

7

MC33364

The AL factor is determined by:

ǒ

L

L

AL+

core with an AL of 100 nH is selected. The desired number of
turns of the primary winding is:

np+

(assuming a Schottky rectifier is used):

ns+

p

n2p

From the manufacturer‘s catalogue recommendation the

L

p

ǒ

Ǔ

A

L

The number of turns needed by the 6.0 V secondary is

ǒ

Vs)

ƪ

The auxiliary winding to power the control IC is 16 V and its

number of turns is given by:

naux

C1

where the minimum ripple frequency is 2 times the 50 Hz line
frequency and t
haversine cycle, is assumed to be half the cycle period.

calculations for the value of the output filter capacitors will be
done at the lowest frequency, since the ripple voltage will be
greatest at this frequency. The approximate equation for the
output capacitance value is given by:

C5

one uses the peak current in the predesign consideration.
Since within the IC there is a limitation of the voltage for the
current sensing, which is set to 1.2 V, the design of the
current sense resistor is simply given by:

R7

secondary, connected to the primary side via an optoisolator,
the MOC8102.

(V

+

The approximate value of rectifier capacitance needed is:

t

(Iin)

off

+

V

ripple

Because we have a variable frequency system, all the

I

+

(f

min

Determining the value of the current sense resistor (R7),

V

cs

+

I

ppk

The error amplifier function is provided by a TL431 on the

B

p

maxAc

+

ǒ

L

ƪ

p

ǒ

+

1ń2

ƪ

+

ǒ

Ǔ

V

1–ēmaxǓn

fwd

ē

maxǒV

in(min)

ǒ

+

)

V

aux

ƪ

ē

max(V

(16 V)0.9 V)(1*0.5)139

+

(5 m sec)(0.118 A)

+

, the discharge time of C1 during the

off

out

+

)(V

)

rip

1.2 V

+

0.472 A

2

Ǔ

2

Ǔ

I

ƫ

ppk

ǒ

Ǔ

0.2 T

33.5 E–6 m

ǒ

.00192 H

(

0.00192 H
(

6.0 V)0.3 V

fwd

(70 kHz)(0.1 V)

Ǔ

(

0.472 A

)

ƫ

100 nH

+

)

p

Ǔ

ƫ

ƪ

0.5ǒ127 V

)(1*ēmax)n

ƫ

)

in(min)

[0.5(127 V)]

50 V

2A

2.54W[

2

2

Ǔ

2

)

1ń2

+

139 turns

ǒ

Ǔ

1*0.5Ǔ139

Ǔ

ƫ

p

+

11.8mF

+

286mF

2.2

W

+

105 nH

+

7 turns

+

19 turns

The voltage of the optoisolator collector node sets the
peak current flowing through the power switch during each
cycle. This pin will be connected to the feedback pin of the
MC33364, which will directly set the peak current.

Starting on the secondary side of the power supply , assign
the sense current through the voltage–sensing resistor
divider to be approximately 0.25 mA. One can immediately
calculate the value of the lower and upper resistor:

V

(TL431)

R

R

current through the optoisolator and the TL431 is set by the
minimum operating current requirements of the TL431. This
currernt is minimum 1.0 mA. Assign the maximum current
through the branch to be 5 mA. That makes the bias resistor
value equal to:

R

100% with 25% tolerance. When the TL431 is full–on, 5 mA
will be drawn from the transistor within the MOC8102. The
transistor should be in saturated state at that time, so its
collector resistor must be

R

reference voltage to the feedback pin of the MC33364, the
external resistor can have a higher value

R

the optoisolator diode and the voltage sense divider on the
secondary side.

R

fpn+

+

lower

upper

The value of the resistor that would provide the bias

bias

The MOC8102 has a typical current transfer ratio (CTR) of

collector

Since a resistor of 5.0 k is internally connected from the

ext

This completes the design of the voltage feedback circuit.

In no load condition there is only a current flowing through

The load at that condition is given by:

noload

The output filter pole at no load is:

R11

+

R10

+

RS+

+

+

+R3+

+

(I

(2pR

ref

+

6.0 V*[2.5V)1.4V]

V

ref

(R

LED

noload

+

V

(R

I

int

V

1

I

div

V

*

V

out

out

*

LED

int

)*(R

out

)

ref

I

div

*

[V

(TL431))V

ref

I

5.0 mA

V

sat

+

)(R

collector

collector

I

)

div

+

(5.0 mA)0.25 mA)

C

)

out

+

(2p)(1143)(300mF)

2.5 V

+

0.25 mA

(TL431)

6.0 V*2.5V

+

0.25 mA

LED

LED

+

420W[

5.0 V*0.3 V

5.0 mA

)

(5.0 k)(940)

+

)

5.0 k*940

+

1157W[

6.0 V

1

+

+

10 k

]

940

1200

+

+

+

14 k

430

W

W

1143

0.46 Hz

W

W

8

MOTOROLA ANALOG IC DEVICE DATA

MC33364

In heavy load condition the I

heavy load resistance is given by:

V

out

6.0 V

R

fpn+

high input voltage will be:

A

fc+

bandwidth is calculated at the rated load because that yields
the bandwidth condition, which is:

+

heavy

The output filter pole at heavy load of this output is

(2pR

The gain exhibited by the open loop power supply at the

ǒ

V

in max

+

ǒ

(V

in max

The maximum recommended bandwidth is approximately:

fsmin

5

The gain needed by the error amplifier to achieve this

I

out

heavy

+

+

1

*

V

)(V

70 kHz

5

2.0 A

C

out

out

error

+

)

2

Ǔ

)(Np)

+

+

Ns

14 kHz

and I

LED

3.0

(2p)(3)(300mF)

+

Ǔ

div

W

1

(

382 V*6.0 V

(382 V)(1.2 V)(139)

+

15.53+23.82 dB

is negligible. The

+

177 Hz

2

)

(7)

f

Gc+20 log

The gain in absolute terms is:

Ac+

The output resistance of the voltage sense divider is given by
the parallel combination of resistors in the divider:

Rin+

R9+(Ac) (Rin)+29.75 k[30 k

C8

light load filter pole:

C7

(Gcń20)

10

Now the compensation circuit elements can be calculated.

R

upper

+

ƪ

2p(Ac)(Rin)(fc)

The compensation zero must be placed at or below the

+

ƪ

2p(R9) (fpn)

c

ǒ

f

ph

|| R

1

+

*A+

Ǔ

10

lower

20 log

(14.14ń20)

+

10 k || 14 k+5833

+

ƫ

1

+

11.63mF[10mF

ƫ

14 kHz

ǒ

+

382 pF[390 pF

51

177

Ǔ

+

*

23.82 dB

14.14 dB

W

MOTOROLA ANALOG IC DEVICE DATA

9

MC33364

Figure 9. 12 W Power Supply

92 to

270 Vac

Zero Current

Frequency

R13
100

R2

22 k

Clamp

EMI

Filter

C2

0.01

D9
1N4148

1N4006

1N4006

4.0 K
10 V

1N4006

D2

D1

U1

MC33364

Zero
Current
Detect

0.3/

0.25 V

2.0 V

R
S

D4

En

R

Q
Q

5.0 V

D3
1N4006

Timer

3.0

10 pF

C1
10

Line

C3

20

+

R1 56

V

CC

P V

CC

Gate Drive

470 R4

P Gnd

Current
Sense

Voltage FB

V

ref

R5 47 k

R6
47 K

D7
1N4148

R12 100

C9 .01

44 K

14 K

V

5.0 V

Reference

+

+

15/7.6

Leading

Edge

Blanking

5.0 k

CC

A Gnd

En

UVLO

RQ

R

Q

S

µ

A

2.0 V

1.5 V

UVLO

1N4934

D5

C4
.001

T1

D6
MURS160T3

Q1

MTD1N60

R7

2.2

R3

1.2 K

C10

0.1

D8
MBRS340T3

C5
300

U3

MOC8102

5

TL431

U2

R9

30 k

6.0 V
2 Amp

R8
430

R10
14 k

1
24

C7
10

3

C8
330 pF

1

2

R11
10 k

10

Line Regulation IO = 930 mA

Line Regulation Vin = 115 Vrms

Output Ripple

Efficiency

Vin = 90 to 270 Vac

IO = 110 to 1100 mA

Vin = 115 Vac, IO = 1100 mA

Vin = 115 Vac, IO = 1100 mA

∆

= 78 mV or ±6.5%

∆

= 103 mV or ±8.6%

600 mVpp

72.9%

MOTOROLA ANALOG IC DEVICE DATA

MC33364

Figure 10. Universal Input Battery Charger

J2

12

Output 12 V @ 0.8 Amp max
Input Voltage Range 90 – 270 Vac, 50/60 Hz

R8

4.7 k

D7

1N4148

5.1 V
D8

B2X84C5V1LT1

C6

µ

F

1.0
R7

100

T1

R13
22 k

54
6

7
8

C5

µ

F

100

D6
MURS320T3

79

543 2

R4

47 k

R12
82 k

S

CSB

U2

MC33341

V

CC

DO

D5
MURS

C4 1.0 nF

R5

47 k

160T3

R11

10 k

GndV

3

CMP

2

CTA

CSA

Q1
MTD1N60E

C7

33 nF

1

R9

100

R4

47 k

R10

0.25

12

54

U3

MOC8102

D3

1N4148

R1

220

20

18 V
D2

B2X84C18LT1

D1 B250R

F1

T 0.2 A

12

J1

Line

MOTOROLA ANALOG IC DEVICE DATA

C1

C2

R3

µ

F

10
350 V

22 k

6

Gate

1 ZCD

MC33364D1

7V

CC

8 Line

µ

f

T1 = 139 Turns #28 Awg, primary winding 2 – 3

2

CS

ref

3FB

C3

4V

µ

F

0.1

U1

Gnd

5

7 Turns, Bifilar 2 x #26 Awg, output winding 9 – 7
19 Turns #28 Awg, auxiliary winding 4 – 5 on Philips
EF20–3C85 core gap for a primary inductor of 1.92 mH.

11

–T–

MC33364

OUTLINE DIMENSIONS

D1, D2 SUFFIX

PLASTIC PACKAGE

CASE 751–05

A

E

B

C

A1

16 9

18

G

SEATING

PLANE

D

58

1

H

4

e

B

SS

–A–

–B–

K

D

16 PL

0.25 (0.010) A

M

S

B

T

0.25MB

A

SEATING
PLANE

A0.25MCB

C

S

M

h

0.10

PLASTIC PACKAGE

CASE 751B–05

8 PLP

0.25 (0.010) B

M

(SO–8)

ISSUE S

X 45

_

D SUFFIX

(SO–16)
ISSUE J

M

R

NOTES:

C

q

L

S

X 45

_

F

J

1. DIMENSIONING AND TOLERANCING PER ASME
Y14.5M, 1994.

2. DIMENSIONS ARE IN MILLIMETERS.

3. DIMENSION D AND E DO NOT INCLUDE MOLD
PROTRUSION.

4. MAXIMUM MOLD PROTRUSION 0.15 PER SIDE.

5. DIMENSION B DOES NOT INCLUDE MOLD
PROTRUSION. ALLOWABLE DAMBAR
PROTRUSION SHALL BE 0.127 TOTAL IN EXCESS
OF THE B DIMENSION AT MAXIMUM MATERIAL
CONDITION.

MILLIMETERS

DIM MIN MAX

A 1.35 1.75

A1 0.10 0.25

B 0.35 0.49
C 0.18 0.25
D 4.80 5.00
E

3.80 4.00

1.27 BSCe

H 5.80 6.20
h

0.25 0.50

L 0.40 1.25

0 7

q

NOTES:

1. DIMENSIONING AND TOLERANCING PER ANSI
Y14.5M, 1982.

2. CONTROLLING DIMENSION: MILLIMETER.

3. DIMENSIONS A AND B DO NOT INCLUDE
MOLD PROTRUSION.

4. MAXIMUM MOLD PROTRUSION 0.15 (0.006)
PER SIDE.

5. DIMENSION D DOES NOT INCLUDE DAMBAR
PROTRUSION. ALLOWABLE DAMBAR
PROTRUSION SHALL BE 0.127 (0.005) TOTAL
IN EXCESS OF THE D DIMENSION AT
MAXIMUM MATERIAL CONDITION.

DIM MIN MAX MIN MAX

A 9.80 10.00 0.386 0.393
B 3.80 4.00 0.150 0.157
C 1.35 1.75 0.054 0.068
D 0.35 0.49 0.014 0.019
F 0.40 1.25 0.016 0.049
G 1.27 BSC 0.050 BSC
J 0.19 0.25 0.008 0.009
K 0.10 0.25 0.004 0.009
M 0 7 0 7
P 5.80 6.20 0.229 0.244
R 0.25 0.50 0.010 0.019

__

INCHESMILLIMETERS

____

12

MOTOROLA ANALOG IC DEVICE DATA

MC33364

Motorola reserves the right to make changes without further notice to any products herein. Motorola makes no warranty, representation or guarantee regarding
the suitability of its products for any particular purpose, nor does Motorola assume any liability arising out of the application or use of any product or circuit, and
specifically disclaims any and all liability, including without limitation consequential or incidental damages. “T ypical” parameters which may be provided in Motorola
data sheets and/or specifications can and do vary in different applications and actual performance may vary over time. All operating parameters, including “T ypicals”
must be validated for each customer application by customer’s technical experts. Motorola does not convey any license under its patent rights nor the rights of
others. Motorola products are not designed, intended, or authorized for use as components in systems intended for surgical implant into the body, or other
applications intended to support or sustain life, or for any other application in which the failure of the Motorola product could create a situation where personal injury
or death may occur. Should Buyer purchase or use Motorola products for any such unintended or unauthorized application, Buyer shall indemnify and hold Motorola
and its officers, employees, subsidiaries, affiliates, and distributors harmless against all claims, costs, damages, and expenses, and reasonable attorney fees
arising out of, directly or indirectly, any claim of personal injury or death associated with such unintended or unauthorized use, even if such claim alleges that
Motorola was negligent regarding the design or manufacture of the part. Motorola and are registered trademarks of Motorola, Inc. Motorola, Inc. is an Equal
Opportunity/Affirmative Action Employer.

MOTOROLA ANALOG IC DEVICE DATA

13

MC33364

How to reach us:
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P.O. Box 5405, Denver, Colorado 80217. 1–303–675–2140 or 1–800–441–2447 Nishi–Gotanda, Shinagawa–ku, Tokyo 141, Japan. 81–3–5487–8488

Customer Focus Center: 1–800–521–6274
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HOME PAGE: http://motorola.com/sps/

14

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MOTOROLA ANALOG IC DEVICE DATA

Mfax is a trademark of Motorola, Inc.

MC33364/D