The MAX5893 programmable interpolating, modulating,
500Msps, dual digital-to-analog converter (DAC) offers
superior dynamic performance and is optimized for highperformance wideband, single-carrier transmit applications. The device integrates a selectable 2x/4x/8x
interpolating filter, a digital quadrature modulator, and
dual 12-bit high-speed DACs on a single integrated circuit. At 30MHz output frequency and 500Msps update
rate, the in-band SFDR is 84dBc while consuming 1.1W.
The device also delivers 72dB ACLR for single-carrier
WCDMA at a 61.44MHz output frequency.
The selectable interpolating filters allow lower input data
rates while taking advantage of the high DAC update
rates. These linear-phase interpolation filters ease
reconstruction filter requirements and enhance the
passband dynamic performance. Individual offset and
gain programmability allow the user to calibrate out local
oscillator (LO) feedthrough and sideband suppression
errors generated by analog quadrature modulators.
The MAX5893 features a f
IM
/4 digital image-reject modulator. This modulator generates a quadrature-modulated IF signal that can be presented to an analog I/Q
modulator to complete the upconversion process. A
second digital modulation mode allows the signal to be
frequency-translated with image pairs at fIM/2 or fIM/4.
The MAX5893 features a standard 1.8V CMOS, 3.3V tolerant data input bus for easy interface. A 3.3V SPI™ port
is provided for mode configuration. The programmable
modes include the selection of 2x/4x/8x interpolating filters, f
IM
/2, fIM/4 or no digital quadrature modulation with
image rejection, channel gain and offset adjustment, and
offset binary or two’s complement data interface.
Pin-compatible 14- and 16-bit devices are also available.
Refer to the MAX5894 data sheet for the 14-bit version
and the MAX5895 data sheet for the 16-bit version.
Applications
Base Stations: 3G UMTS, CDMA, and GSM
Broadband Wireless Transmitters
Broadband Cable Infrastructure
Instrumentation and Automatic Test Equipment (ATE)
Analog Quadrature Modulation Architectures
Features
o 72dB ACLR at f
OUT
= 61.44MHz (Single-Carrier
WCDMA)
o Meets 3G UMTS, cdma2000
®
, GSM Spectral Masks
(f
OUT
= 122MHz)
o Noise Spectral Density = -151dBFS/Hz at
f
OUT
= 16MHz
o 90dBc SFDR at Low-IF Frequency (10MHz)
o 86dBc SFDR at High-IF Frequency (50MHz)
o Low Power: 511mW (f
CLK
= 100MHz)
o User Programmable
Selectable 2x, 4x, or 8x Interpolating Filters
< 0.01dB Passband Ripple
> 99dB Stopband Rejection
Selectable Real or Complex Modulator Operation
Selectable Modulator LO Frequency: OFF, fIM/2,
or f
IM
/4
Selectable Output Filter: Lowpass or Highpass
Channel Gain and Offset Adjustment
mode, 50Ω double-terminated outputs, external reference at 1.25V, T
A
= -40°C to +85°C, unless otherwise noted. Typical values are
at T
A
= +25°C, unless otherwise noted.) (Note 2)
Stresses beyond those listed under “Absolute Maximum Ratings” may cause permanent damage to the device. These are stress ratings only, and functional
operation of the device at these or any other conditions beyond those indicated in the operational sections of the specifications is not implied. Exposure to
absolute maximum rating conditions for extended periods may affect device reliability.
DV
DD1.8
, AV
DD1.8
to GND, DACREF ..................-0.3V to +2.16V
AV
DD3.3
, AV
CLK
, DV
DD3.3
to GND, DACREF........-0.3V to +3.9V
DATACLK, A0–A11, B0–B9,
SELIQ/B11, DATACLK/B10, CS, RESET, SCLK,
SDI and SDO to GND, DACREF......-0.3V to (DV
DD3.3
+ 0.3V)
CLKP, CLKN to GND, DACREF..............-0.3V to (AV
CLK
+ 0.3V)
REFIO, FSADJ to GND, DACREF ........-0.3V to (AV
DD3.3
+ 0.3V)
OUTIP, OUTIN, OUTQP,
OUTQN to GND, DACREF..................-1V to (AV
DD3.3
+ 0.3V)
SDO, DATACLK, DATACLK/BIO Continuous Current ..........8mA
mode, 50Ω double-terminated outputs, external reference at 1.25V, T
A
= -40°C to +85°C, unless otherwise noted. Typical values are
at T
A
= +25°C, unless otherwise noted.) (Note 2)
Note 2: All specifications are 100% tested at T
A
≥ +25°C. Specifications at TA< +25°C are guaranteed by design and characteriza-
tion data.
Note 3: 3.84MHz bandwidth, single carrier.
Note 4: Excludes data latency.
Note 5: Measured single-ended into a 50Ω load.
Note 6: Excludes sin(x)/x rolloff.
Note 7: Guaranteed by design and characterization.
Note 8: Setup and hold time specifications characterized with 3.3V CMOS logic levels.
Note 9: Parameter defined as the change in midscale output caused by a ±5% variation in the nominal supply voltage.
PARAMETERSYMBOLCONDITIONSMINTYPMAXUNITS
POWER SUPPLIES
Digital Supply VoltageDV
Digital I/O Supply VoltageDV
Clock Supply VoltageAV
Analog Supply Voltage
AV
AV
I
AVDD3.3
Analog Supply Current
I
AVDD1.8
Digital Supply CurrentI
Digital I/O Supply CurrentI
Clock Supply CurrentI
DVDD1.8
DVDD3.3
AVCLK
Total Power DissipationP
Power-Down Current
AV
Ratio
Power-Supply Rejection
DD3.3
PSRR
DD1.8
DD3.3
CLK
DD3.3
DD1.8
TOTAL
1.711.81.89V
3.03.33.6V
3.1353.33.465V
3.1353.33.465
1.711.81.89
f
= 250MHz, 2x interpolation, 0dBFS,
CLK
f
= 10MHz, DATACLK output mode
OUT
f
= 250MHz, 2x interpolation, 0dBFS,
CLK
f
= 10MHz, DATACLK output mode
OUT
f
= 250MHz, 2x interpolation, 0dBFS,
CLK
= 10MHz, DATACLK output mode
f
OUT
f
= 250MHz, 2x interpolation, 0dBFS,
CLK
= 10MHz, DATACLK output mode
f
OUT
f
= 250MHz, 2x interpolation, 0dBFS,
CLK
= 10MHz, DATACLK output mode
f
OUT
110130
2732
205250mA
2132mA
35mA
511mW
AV
DD3.3
AV
DV
DV
AV
DD1.8
DD1.8
DD3.3
CLK
All I/O are static high or
low, bit 2 to bit 4 of
address 00h are set high
Digital Power Supply. Accepts a 1.71V to 1.89V supply range. Bypass each pin to ground with a
0.1µF capacitor as close to the pin as possible.
A-Port Data Inputs.
Dual-port mode:
I-channel data input. Data is latched on the rising/falling edge (programmable) of the DATACLK.
Single-port mode:
I-channel and Q-channel data input, with SELIQ.
13, 44DV
14DATACLKProgrammable Data Clock Input/Output. See the DATACLK Modes section for details.
26SELIQ/B11
27DATACLK/B10
28, 29, 31–36,
38, 39
45SDOSerial-Port Data Output
46SDISerial-Port Data Input
47SCLKSerial-Port Clock Input. Data on SDI is latched on the rising edge of SCLK.
48CSSerial-Port Interface Select. Drive CS low to enable serial-port interface.
49RESETReset Input. Set RESET low during power-up.
50REFIOReference Input/Output. Bypass to ground with a 1µF capacitor as close to the pin as possible.
51DACREF
52FSADJ
DD3.3
B9–B0
CMOS I/O Power Supply. Accepts a 3.0V to 3.6V supply range. Bypass each pin to ground with a
0.1µF capacitor as close to the pin as possible.
Select I/Q-Channel Input or B-Port MSB Input.
Single-port mode:
If SELIQ = LOW, data is latched into Q-channel on the rising/falling edge (programmable) of
the DATACLK.
If SELIQ = HIGH, data is latched into I-channel on the rising/falling edge (programmable) of the
DATACLK.
Dual-port mode:
Q-channel MSB input.
Alternate DATACLK Input/Output or B-Port Bit 10 Input.
Single-port mode:
See the DATACLK Modes section for details.
Dual-port mode:
Q-channel bit 10 input.
If unused connect to GND.
B-Port Data Bits 9–0.
Dual-port mode:
Q-channel inputs. Data is latched on the rising/falling (programmable) edge of the DATACLK.
Single-port mode:
Connect to GND.
C ur r ent- S et Resi stor Retur n P ath. For a 20m A ful l - scal e outp ut cur r ent, connect a 2kΩ r esi stor b etw een
FS AD J and D AC RE F. Inter nal l y connected to GN D . D o no t u s e a s a n e x t e r n a l g r o u n d co n n e c t io n .
Full-Scale Adjust Input. This input sets the full-scale output current of the DAC. For a 20mA fullscale output current, connect a 2kΩ resistor between FSADJ and DACREF.
The MAX5893 dual, 500Msps, high-speed, 12-bit, current-output DAC provides superior performance in
communication systems requiring low-distortion analog-signal reconstruction. The MAX5893 combines two
DAC cores with 8x/4x/2x/1x programmable digital interpolation filters, a digital quadrature modulator, an SPIcompatible serial interface for programming the device,
and an on-chip 1.20V reference. The full-scale output
current range is programmable from 2mA to 20mA to
optimize power dissipation and gain control.
Each channel contains three selectable interpolating filters making the MAX5893 capable of 1x, 2x, 4x, or 8x
interpolation, which allows for low-input and high-output data rates. When operating in 8x interpolation
mode, the interpolator increases the DAC conversion
rate by a factor of eight, providing an eight-fold
increase in separation between the reconstructed
waveform spectrum and its first image. The MAX5893
accepts either two’s complement or offset binary input
data format and can operate from either a single- or
dual-port input bus.
The MAX5893 includes modulation modes at f
IM
/2 and
fIM/4, where fIMis the data rate at the input of the modulator. If 2x interpolation is used, this data rate is 2x the
input data rate. If 4x or 8x interpolation is used, this data
rate is 4x the input data rate. Table 1 summarizes the
modulator operating data rates for dual-port mode.
The power-down modes can be used to turn off each
DAC’s output current or the entire digital section.
Programming both DACs into power-down simultaneously will automatically power down the digital interpolator filters. Note the SPI section is always active.
The analog and digital sections of the MAX5893 have
separate power-supply inputs (AV
DD3.3
, AV
DD1.8
,
AV
CLK
, DV
DD3.3
, and DV
DD1.8
), which minimize noise
coupling from one supply to the other. AV
DD1.8
and
DV
DD1.8
operate from a typical 1.8V supply, and all
other supply inputs operate from a typical 3.3V supply.
Serial Interface
The SPI-compatible serial interface programs the
MAX5893 registers. The serial interface consists of the
CS, SDI, SCLK, and SDO. Data is shifted into SDI on
the rising edge of the SCLK when CS is low. When CS
is high, data presented at SDI is ignored and SDO is in
high-impedance mode. Note: CS must transition highafter each read/write operation. SDO is the serial data
output for reading registers to facilitate easy debugging during development. SDI and SDO can be connected together to form a 3-wire serial interface bus or
remain separate and form a 4-wire SPI bus.
The serial interface supports two-byte transfer in a
communication cycle. The first byte is a control byte
written to the MAX5893 only. The second byte is a data
byte and can be written to or read from the MAX5893.
Table 1. Quadrature Modulator Operating Data Rates (fIMis the Data Rate at the Input of
the Modulator) for Dual-Port Mode
INTERPOLATION RATEMODULATION MODE (fLO)
1x
2x
4x
8x
fIM/2f
f
/4f
IM
fIM/2f
f
/4f
IM
fIM/2f
/4f
f
IM
fIM/2f
/4f
f
IM
MODULATION FREQUENCY
RELATIVE TO f
DAC
DAC
DAC
DAC
DAC
DAC
DAC
DAC
DAC
/2f
/4f
/2f
/4f
/22 x f
/4f
/42 x f
/8f
MODULATION FREQUENCY
RELATIVE TO f
DATA
DATA
DATA
DATA
/2
/4
DATA
/2
DATA
DATA
DATA
DATA
When writing to the MAX5893, data is shifted into SDI;
data is shifted out of SDO in a read operation. Bits 0 to
3 of the control byte are the address bits. These bits set
the address of the register to be written to or read from.
Bits 4 to 6 of the control byte must always be set to 0.
Bit 7 is a read/write bit: 0 for write operation and 1 for
read operation. The most significant bit (MSB) is shifted
in first in default mode. If the serial port is set to LSBfirst mode, both the control byte and data byte are shifted
LSB in first. Figures 1 and 2 show the SPI serial interface
operation in the default write and read mode, respectively.
Figure 3 is a timing diagram for the SPI serial interface.
Bit 6Logic 0 (default) causes the serial port to use
MSB first address/data format. When set to a
logic 1, the serial port will use LSB first
address/data format.
Bit 5When set to a logic 1, all registers reset to
their default state (this bit included).
Bit 4Logic 1 stops the clock to the digital interpo-
lators. DAC outputs hold last value prior to
interpolator power-down.
Bit 3IDAC power-down mode. A logic 1 to this bit
powers down the IDAC.
Bit 2QDAC power-down mode. A logic 1 to this bit
powers down the QDAC.
Note: If both bit 2 and bit 3 are 1, the MAX5893 is in
full-power-down mode, leaving only the serial interface
active.
Address 01h
Bits 7, 6 Configure the interpolation filters according
to the following table:
001x (no interpolation)
012x
104x
118x (default)
Bit 5Logic 0 configures FIR3 as a lowpass digital
filter (default). A logic 1 configures FIR3 as a
highpass digital filter.
Bits 4, 3 Configure the modulation frequency accord-
ing to the following table:
00No modulation
01fIM/2 modulation
10fIM/4 modulation (default)
11fIM/4 modulation
where fIMis the data rate at the input of the
modulator.
Bit 2Configures the modulation mode for either
real or complex (image reject) modulation.
Logic 1 sets the modulator to the real mode
(default). Complex modulation is only available for f
IM
/4 modulation.
Bit 1 Quadrature modulator sign inversion. With I-
channel data leading Q-channel data by 90°,
logic 0 sets the complex modulation to be
e
-jw
(default), cancelling the upper image
when used with an external quadrature mod-
ulator. A logic 1 sets the complex modulation
to be e
+jw
, cancelling the lower image when
used with an external quadrature modulator.
Address 02h
Bit 7Logic 0 (default) configures the data port for
two’s complement. A logic 1 configures the
data ports for offset binary.
Bit 6Logic 0 (default) configures the data bus for
single-port, interleaved I/Q data. I and Q data
enter through one 12-bit bus. Logic 1 configures the data bus for dual-port I/Q data. I and
Q data enter on separate buses.
Bit 5Logic 0 (default) configures the data clock
for pin 14. A logic 1 configures the data clock
for pin 27 (DATACLK/B10).
Bit 4Logic 0 (default) sets the internal latches to
latch the data on the rising edge of DATACLK.
A logic 1 sets the internal latches to latch the
data on the falling edge of DATACLK.
Bit 3Logic 0 (default) configures the DATACLK
pin (pin 14 or pin 27) to be an input. A logic 1
configures the DATACLK pin to be an output.
Bit 2Logic 0 (default) enables the data synchro-
nizer circuitry. A logic 1 disables the data
synchronizer circuitry.
Address 03h
Bits 7–0Unused.
Address 04h
Bits 7–0These 8 bits define the binary number for
fine-gain adjustment of the IDAC full-scale
current (see the
Gain Adjustment
section). Bit
7 is the MSB. Default is all zeros.
Address 05h
Bits 3–0 These four bits define the binary number for
the coarse-gain adjustment of the IDAC fullscale current (see the
Gain Adjustment
sec-
tion). Bit 3 is the MSB. Default is all ones.
Address 06h, Bits 7 to 0; Address 07h, Bit 1 and Bit 0
These 10 bits represent a binary number that
defines the magnitude of the offset added to
the IDAC output (see the
Offset Adjustment
section). Default is all zeros.
Address 07h
Bit 7Logic 0 (default) adds the 10 bits offset cur-
rent to OUTIN. A logic 1 adds the 10 bits offset current to OUTIP.
Address 08h
Bits 7–0These 8 bits define the binary number for
fine-gain adjustment of the QDAC full-scale
current (see the
Gain Adjustment
section). Bit
7 is the MSB. Default is all zeros.
Address 09h
Bits 3–0 These 4 bits define the binary number for the
coarse-gain adjustment of the QDAC fullscale current (see the
Gain Adjustment
sec-
tion). Bit 3 is the MSB. Default is all ones.
Address 0Ah, Bits 7 to 0; Address 0Bh, Bit 1 and Bit 0
These 10 bits represent a binary number that
defines the magnitude of the offset added to
the QDAC output (see the
Offset Adjustment
section). Default is all zeros.
Address 0Bh
Bit 7Logic 0 (default) adds the 10 bits offset to
OUTQN. A logic 1 adds the 10 bits offset to
OUTQP.
Offset Adjustment
Offset adjustment is achieved by adding a digital code
to the DAC inputs. The code OFFSET (see equation
below), as stored in the relevant control registers, has a
range from 0 to 1023 and a sign bit. The applied DAC
offset is 4 times the code stored in the register, providing an offset adjustment range of ±255 LSB codes. The
resolution is 1 LSB.
Gain Trim
Gain trimming is done by varying the full-scale current
according to the following formula:
where I
REF
is the reference current (see the
Internal
Reference
section). COARSE is the register content of
registers 05h and 09h for the I- and Q-channel, respectively. FINE is the register content of register 04h and
08h for the I- and Q-channel, respectively. The range of
coarse is from 0 to 11, with 11 being the default. The
range for FINE is from 0 to 255 with 0 being the default.
Given this, the gain can be adjusted in steps of approximately 0.01dB.
Single-Port/Dual-Port Data Input Modes
The MAX5893 is capable of capturing data in singleport and dual-port modes (selected through bit 6,
address 02h). In single-port mode, the data for both
channels is input through the A port (A11–A0).
The channel for the input data is determined through
the state of the SELIQ/B11 (pin 26) bit. When SELIQ is
set to logic-high, the input data is presented to the
I-channel, when set to logic-low, the input data is
presented to the Q-channel. The unused B-port inputs
(DATACLK/B10, B9–B0) should be grounded when running in single-port mode.
Dual-port mode, as the name implies, requires that
each channel receives its data from a separate data
bus. SELIQ/B11 and DATACLK/B10 revert to data bit
inputs for the Q-channel in dual-port mode.
The MAX5893 control registers can be programmed to
allow either signed or unsigned binary format (bit 7,
address 02h) data in either single-port or dual-port
mode. Table 3 shows the corresponding DAC output
levels when using signed or unsigned data modes.
Data Synchronization Modes
Data synchronization circuitry is provided to allow operation with an input data clock. The data clock must be
frequency locked to the DAC clock (f
DAC
), but can
have arbitrary phase with respect to the DAC clock.
The synchronization circuitry allows for phase jitter on
the input data clock of up to ±1 data clock cycles.
Synchronization is initially established when the reset
pin is asynchronously deasserted and the input data
clock has been running for at least 4 clock cycles.
Subsequently, the MAX5893 monitors the phase rela-
tionship and detects if the phase drifts more than ±1
data clock cycle. If this occurs, the synchronizer automatically reestablishes synchronization. However, during the resynchronization phase, up to 8 data words
may be lost or repeated.
Bit 2 of register 02h disables or enables (default) the
automatic data clock phase detection. Disabling the
data synchronization circuitry requires the data clock
and the DAC clock phase to be locked.
DATACLK Modes
The MAX5893 has a main DATACLK available at
pin 14. An alternate DATACLK is available at pin 27
(DATACLK/B10) when configured in single-port data
input mode (bit 5, address 02h). The DATACLK can be
configured to accept an input clock signal for latching
the input data, or to source a clock signal that can drive
up to 10pF load while latching the input data (bit 3,
address 02h). If DATACLK is configured as an output, it
is frequency divided from the CLKP/CLKN input,
depending on the operating mode, see Table 4.
The MAX5893 can be configured to latch the input
data on either the rising edge or falling edge of the
DATACLK signal (bit 4, address 02h). Figure 4 shows
the timing requirements between the DATACLK signal
and the input data bus with latching on the rising edge.
12-Bit, 500Msps Interpolating and Modulating
Dual DAC with CMOS Inputs
The MAX5893 features three cascaded FIR half-band
filters. The interpolating filters are enabled or disabled
in combinations to support 1x (no interpolation), 2x, 4x,
or 8x interpolation. Bits 7 and 6 of register 01h set the
interpolation rate (see Table 2). The last interpolation fil-
ter is located after the modulator. In the 8x interpolation
mode, the last filter (FIR3) can be configured as lowpass or highpass (bit 5, address 01h) to select the
lower or upper sideband from the modulation output.
The frequency responses of these three filters are plotted in Figures 5–8.
Figure 5. Interpolation Filter Frequency Response, 2x
Interpolation Mode
Figure 6. Interpolation Filter Frequency Response, 4x
Interpolation Mode
The programmable interpolation filters multiply the
MAX5893 input data rate by a factor of 2x, 4x, or 8x to
separate the reconstructed waveform spectrum and the
DAC image. The original spectral images, appearing at
around multiples of the input data rate, are attenuated
by the internal digital filters. This feature provides three
benefits:
1) Image separation reduces complexity of analog
reconstruction filters.
2) Lower input data rates eliminate board-level highspeed data transmission.
3) Sin(x)/x rolloff is reduced over the effective bandwidth.
Figure 9 illustrates a practical example of the benefits
when using the MAX5893 in 2x, 4x, and 8x interpolation
modes with the third filter configured as a lowpass filter.
With no interpolation filter, the first image signal appears
in the second Nyquist zone between fS/2 and fS. The first
interpolating filter removes this image. In fact, all of the
12-Bit, 500Msps Interpolating and Modulating
Dual DAC with CMOS Inputs
Figure 9. Spectral Representation of Interpolating Filter Responses (Output Frequencies are Relative to the Data Input Frequency, fS)
FILTER
IMAGE
IMAGE
RESPONSE
3f
S
3f
S
3f
S
INPUT
SPECTRUM
AND FIRST
FILTER
RESPONSE
OUTPUT
SPECTRUM
OF THE
FIRST
FILTER
INPUT
SPECTRUM
AND
SECOND
FILTER
RESPONSE
SIGNAL
SIGNAL
SIGNAL
IMAGE
f
S
f
S
f
S
2f
S
2f
S
2f
S
NO INTERPOLATION
4f
S
4f
S
4f
S
5f
5f
5f
S
S
S
FILTER
RESPONSE
6f
S
6f
S
6f
S
7f
S
7f
S
7f
S
8f
S
2x INTERPOLATION
8f
S
8f
S
OUTPUT
SPECTRUM
OF THE
SECOND
FILTER
INPUT
SPECTRUM
AND THIRD
FILTER
RESPONSE
OUTPUT
SPECTRUM
OF THE
THIRD
FILTER
SIGNAL
SIGNAL
SIGNAL
IMAGE
f
S
f
S
f
S
2f
S
2f
S
2f
S
FILTER
RESPONSE
3f
S
3f
S
3f
S
4f
S
4f
S
4f
S
IMAGE
5f
S
5f
S
5f
S
6f
S
6f
S
6f
S
7f
S
7f
S
IMAGE
7f
S
4x INTERPOLATION
8f
S
8f
S
8x INTERPOLATION
8f
S
images at odd numbers of fSare filtered. At the output of
the first filter, the images are at 2fS, 4fS, etc. This signal is
then passed to the second interpolating filter, which is
similar to the first filter and removes the images at 2fS, 6fS,
10fS, etc. Finally, the third filter removes images at 4fS,
12fS, 20fS, etc. Figures 10, 11, and 12 similarly illustrate
the spectral responses when using the interpolating filters
combined with the digital modulator.
Figure 11. Spectral Representation of 8x Interpolation Filter with fIM/4 Modulation and Lowpass Mode Enabled (Output Frequencies
are Relative to the Data Input Frequency, f
S
)
INPUT
SIGNAL
SPECTRUM
AND FIRST
FILTER
RESPONSE
OUTPUT
SIGNAL
SPECTRUM
OF THE
FIRST
FILTER
INPUT
SPECTRUM
SIGNAL
AND
SECOND
FILTER
RESPONSE
OUTPUT
SIGNAL
SPECTRUM
OF THE
SECOND
FILTER
FILTER
IMAGE
f
S
2f
S
RESPONSE
3f
S
4f
S
5f
S
6f
S
7f
S
IMAGE
f
S
2f
S
3f
S
4f
S
5f
S
6f
S
7f
S
NO INTERPOLATION
8f
S
2x INTERPOLATION
8f
S
FILTER
4f
S
4f
S
RESPONSE
IMAGE
5f
S
6f
S
7f
S
8f
S
4x INTERPOLATION
5f
S
6f
S
7f
S
8f
S
IMAGE
f
S
f
S
2f
S
2f
S
3f
S
3f
S
SIGNAL
OUTPUT
LOWER
SIDEBAND
UPPER
SIDEBAND
IMAGE
SPECTRUM
OF THE
MODULATOR
f
S
2f
S
3f
S
4f
S
5f
S
6f
S
7f
S
8f
S
FOR COMPLEX MODULATION THE MODULATION SIGN (BIT 1, ADDRESS 01h) SELECTS UPPER OR LOWER SIDEBAND
Figure 12. Spectral Representation of 8x Interpolation Filter with fIM/4 Modulation and Highpass Mode Enabled (Output Frequencies
are Relative to the Data Input Frequency, f
S
)
INPUT
SPECTRUM
AND FIRST
FILTER
RESPONSE
SIGNAL
FILTER
IMAGE
f
S
2f
S
RESPONSE
3f
S
4f
S
5f
S
6f
S
7f
S
NO INTERPOLATION
8f
S
OUTPUT
SPECTRUM
OF THE
FIRST
FILTER
INPUT
SPECTRUM
AND
SECOND
FILTER
RESPONSE
OUTPUT
SPECTRUM
OF THE
SECOND
FILTER
OUTPUT
SPECTRUM
OF THE
MODULATOR
SIGNAL
SIGNAL
SIGNAL
f
S
f
S
f
S
IMAGE
2f
S
IMAGE
2f
S
3f
S
4f
S
5f
S
6f
S
FILTER
RESPONSE
3f
S
4f
S
5f
S
6f
S
IMAGE
2f
S
3f
S
4f
S
5f
S
6f
S
SIGNAL
LOWER
SIDEBAND
f
S
UPPER
SIDEBAND
IMAGE
2f
S
3f
S
4f
S
5f
S
6f
S
FOR COMPLEX MODULATION THE MODULATION SIGN (BIT 1, ADDRESS 01h) SELECTS UPPER OR LOWER SIDEBAND
2x INTERPOLATION
7f
S
7f
S
8f
S
8f
S
4x INTERPOLATION
7f
S
7f
S
8f
S
8f
S
INPUT
SPECTRUM
SIGNAL
IMAGE
FILTER
RESPONSE
AND THIRD
FILTER
RESPONSE
OUTPUT
SPECTRUM
f
S
2f
S
3f
S
SIGNAL
4f
S
5f
S
IMAGE
6f
S
7f
S
8f
S
8x INTERPOLATION
OF THE
THIRD
FILTER
f
S
2f
S
3f
S
4f
S
5f
S
6f
S
7f
S
8f
S
MAX5893
Digital Modulator
The MAX5893 features digital modulation at frequencies of fIM/2 and fIM/4, where fIMis the data rate at the
input to the modulator. fIMequals f
DAC
in 1x, 2x, and 4x
interpolation modes. In 8x interpolation mode, f
IM
equals f
DAC
/2. The output rate of the modulator is
always the same as the input data rate to the modulator, f
IM
.
In complex modulation mode, data from the second
interpolation filter is frequency mixed with the on-chip
in-phase and quadrature (I/Q) local oscillator (LO).
Complex modulation provides the benefit of image
sideband rejection when combined with an external
quadrature modulator commonly found in wireless
communication systems.
In the f
LO
= fIM/4 mode, real or complex modulation can
be used. The modulator multiplies successive input data
samples by the sequence [1, 0, -1, 0] for a cos(ωt). The
modulator modulates the input signal up to fIM/4, creating upper and lower images around fIM/4. The quadrature LO sin(ωt) is realized by delaying the cos(ωt)
sequence by one clock cycle. Using complex modulation, complex IF is generated. The complex IF combined
with an external quadrature modulator provides image
rejection. The sign of the LO can be changed to allow
the user to select whether the upper or the lower image
should be rejected (bit 1 of register 01h).
When f
IM
/2 is chosen as the LO frequency, the input
signal is multiplied by [-1, 1] on both channels. This produces images around f
IM
/2. The complex image-reject
modulation mode is not available for this LO frequency.
The outputs of the modulator can be expressed as:
in complex modulation, e
+jwt
in complex modulation, e
-jwt
where ω = 2 x π x fLO.
For real modulation, the outputs of the modulator can
be expressed as:
If more than one MAX5893 is used, their LO phases
can be synchronized by simultaneously releasing
RESET. This sets the MAX5893 to its predefined initial
phase.
Device Reset
The MAX5893 can be reset by holding the RESET pin
low for 10ns. This will program the control registers to
their default values in Table 2. During power-on, RESET
must be held low until all power supplies have stabilized. Alternatively, programming bit 5 of address 00h
to a logic-high also resets the MAX5893 after power-up.
12-Bit, 500Msps Interpolating and Modulating
Dual DAC with CMOS Inputs
Figure 13. (a) Modulator in Complex Modulation Mode; (b) Modulator in Real Modulation Mode
It Att Btt
()=()×() ()×()
=
Qt Att Btt
()
sin cos
()×()+()×()
It Att Btt
()=()×()+()×()
Qt Att Btt
cos sin
=
sin cos
()×()+()×()
()
− cos sin
ωω
ωω
ωω
ωω
It Att
()=()×()
Qt Att
()
cos
=
cosωω
()×()
I-CHANNEL
INPUT DATA
cos(ωt)
sin(ωt)
sin(ωt)
Q-CHANNEL
INPUT DATA
cos(ωt)
(a)
∑
∑
I-CHANNEL
OUTPUT DATA
TO
FIR3
Q-CHANNEL
OUTPUT DATA
I-CHANNEL
INPUT DATA
Q-CHANNEL
INPUT DATA
cos(ωt)
sin(ωt)
sin(ωt)
cos(ωt)
I-CHANNEL
∑
OUTPUT DATA
TO
FIR3
Q-CHANNEL
∑
OUTPUT DATA
(b)
Power-Down Mode
The MAX5893 features three power-saving modes.
Each DAC can be individually powered down through
bits 2 and 3 of address 00h. The interpolation filters can
also be powered down through bit 4 of address 00h,
preserving the output level of each DAC (the DACs
remain powered). Powering down both DACs will automatically put the MAX5893 into full power-down, including the interpolation filters.
Applications Information
Frequency Planning
System designers need to take the DAC into account
during frequency planning for high-performance applications. Proper frequency planning can ensure that
optimal system performance is achieved. The
MAX5893 is designed to deliver excellent dynamic performance across wide bandwidths, as required for
communication systems. As with all DACs, some combinations of output frequency and update rate produce
better performance than others.
Harmonics are often folded down into the band of interest. Specifically, if the DAC outputs a frequency close
to fS/N, the Mth harmonic of the output signal will be
aliased down to:
Thus, if N ≈ (M + 1), the Mth harmonic will be close to
the output frequency. SFDR performance of a currentsteering DAC is often dominated by third-order harmonic distortion. If this is a concern, placing the output
signal at a different frequency other than fS/4 should be
considered.
Common to interpolating DACs are images near the
divided clocks. In a DAC configured for 4x interpolation
this applies to images around fS/4 and fS/2. In a DAC
configured for 8x interpolation this applies to images
around fS/8, fS/4, and fS/2. Most of these images are
not part of the in-band (0 to f
DATA
/2) SFDR specification, though they are a consideration for out-of-band
(f
DATA
/2 - f
DAC
/2) SFDR and may depend on the rela-
tionship of the DATACLK to DAC update clock (see the
Data Clock
section). When specifying the output reconstruction filter for other than baseband signals, these
images should not be ignored.
Data Clock
The MAX5893 features synchronizers that allow for
arbitrary phase alignment between DATACLK and
CLKP/CLKN. The DATACLK causes internal switching
in the MAX5893 and the phase between DATACLK
(input mode) to CLKP/CLKN will influence the images
at DATACLK. Optimum image rejection is achieved
when DATACLK transitions are aligned with the falling
edge of CLKP. Figure 14 shows the image level near
DATACLK as a function of the DATACLK (input mode)
to CLKP/CLKN phase at 500Msps, 4x interpolation for a
10MHz, -6dBFS output signal.
Clock Interface
The MAX5893 features a flexible differential clock input
(CLKP, CLKN) with a separate supply (AV
CLK
) to
achieve optimum jitter performance. It uses an ultra-low
jitter clock to achieve the required noise density. Clock
jitter must be less than 0.5ps
RMS
to meet the specified
noise density. For that reason, the CLKP/CLKN input
source must be designed carefully. The differential
clock (CLKN and CLKP) input can be driven from a single-ended or a differential clock source. Differential
clock drive is required to achieve the best dynamic
performance from the DAC. For single-ended operation, drive CLKP with a low noise source and bypass
CLKN to GND with a 0.1µF capacitor.
The CLKP and CLKN pins are internally biased to
AV
Figure 14. Effect of CLKP/CLKN to DATACLK Phase on fS/4
Images
ff Mff
=×=
−
SOUTS
−
NM
⎡
⎢
N
⎣
fS/4 IMAGES vs. CLKP/CLKN to DATACLK DELAY
= 125MWps, 4x INTERPOLATION
f
DATA
-50
-60
-70
-80
IMAGE LEVEL (dBc)
-90
-100
-110
08.0
fS/4 - f
OUT
fS/4 + f
OUT
CLKP/CLKN DELAY (ns)
f
OUT
A
OUT
6.04.02.0
= 10MHz
= -6dBFS
MAX5893
sources directly to the device without external resistors
to define the DC level. The input resistance of CLKP
and CLKN is 5kΩ.
A convenient way to apply a differential signal is with a
balun transformer as shown in Figure 15. Alternatively,
these inputs may be driven from a CMOS-compatible
clock source, however it is recommended to use
sine-wave or AC-coupled differential ECL/PECL drive for
best dynamic performance.
Output Interface (OUTI, OUTQ)
The MAX5893 outputs complementary currents (OUTIP,
OUTIN) and (OUTQP, OUTQN), that can be utilized in a
differential configuration. Load resistors convert these
two output currents into a differential output voltage.
The differential output between OUTIP (OUTQP) and
OUTIN (OUTQN) can be converted to a single-ended
output using a transformer or a differential amplifier.
Figure 16 shows a typical transformer-based application circuit for generation of IF output signals. In this
configuration, the MAX5893 operates in differential
mode, which reduces even-order harmonics, and
increases the available output power. Pay close attention to the transformer core saturation characteristics
when selecting a transformer. Transformer core saturation can introduce strong second harmonic distortion,
especially at low output frequencies and high signal
12-Bit, 500Msps Interpolating and Modulating
Dual DAC with CMOS Inputs
Figure 15. Single-Ended-to-Differential Clock Conversion Using
a Balun Transformer
Figure 16. Differential-to-Single-Ended Conversion Using Wideband RF Transformers
MINI-CIRCUITS
SINGLE-ENDED
IINPUT
ADTL1-12
1:1 RATIO
100nF
CLKP
24.9Ω
MAX5893
24.9Ω
100nF
CLKN
OUTIP
50Ω
1:1
, SINGLE-ENDED
V
IOUT
IDAC
12
OUTIN
MAX5893
OUTQP
QDAC
12
OUTQN
100Ω
50Ω
50Ω
100Ω
50Ω
1:1
V
, SINGLE-ENDED
QOUT
1:1
1:1
amplitudes. It is recommended to connect the transformer center tap to ground.
If a transformer is not used, the outputs must have a
resistive termination to ground. Figure 17 shows the
MAX5893 output configured for differential DC-coupled
mode. The DC-coupled configuration can be used to
eliminate waveform distortion due to highpass filter
effects. Applications include communication systems
employing analog quadrature upconverters and requiring a high-speed DAC for baseband I/Q synthesis.
If a single-ended DC-coupled unipolar output is desirable, OUTIP (OUTQP) should be selected as the output, and connect OUTIN (OUTQN) to ground. Using the
MAX5893 output single-ended is not recommended
because it introduces additional noise and distortion.
The distortion performance of the DAC also depends
on the load impedance. The MAX5893 is optimized for
a 50Ω double termination. It can be used with a transformer output as shown in Figure 16 or just one 25Ω
resistor from each output to ground and one 50Ω resistor between the outputs (Figure 17). Higher output termination resistors may be used, as long as each output
voltage does not exceed +1V with respect to GND, but
at the cost of degraded distortion performance and
increased output noise voltage.
Reference Input/Output
The MAX5893 supports operation with the on-chip 1.2V
bandgap reference or an external reference voltage
source. REFIO serves as the input for an external, lowimpedance reference source, and as the output if the
DAC is operating with the internal reference.
Figure 17. The DC-Coupled Differential Output Configuration
25Ω
OUTIP
IDAC
12
OUTIN
MAX5893
OUTQP
QDAC
12
OUTQN
50Ω
25Ω
25Ω
50Ω
25Ω
MAX5893
For stable operation with the internal reference, REFIO
should be decoupled to GND with a 1µF capacitor.
REFIO must be buffered with an external amplifier, if
heavy loading is required, due to its 10kΩ output resistance.
Alternatively, apply a temperature-stable external reference to REFIO (Figure 18). The internal reference is overdriven by the external reference. For improved accuracy
and drift performance, choose a fixed output voltage reference such as the MAX6520 bandgap reference.
The MAX5893’s reference circuit (Figure 19) employs a
control amplifier, designed to regulate the full-scale
current I
OUT
for the differential current outputs of the
DAC. The output current can be calculated as:
I
OUTFS
= 32 x I
REFIO
- 1LSB
I
OUTFS
= 32 x I
REFIO
- (I
OUT
/212)
where I
REFIO
is the reference output current (I
REFIO
=
V
REFIO/RSET
) and I
OUT
is the full-scale output current
of the DAC. Located between FSADJ and DACREF,
R
SET
is the reference resistor, which determines the
amplifier’s output current for the DAC. Use Table 5 for a
matrix of different I
OUTFS
and R
SET
selections.
12-Bit, 500Msps Interpolating and Modulating
Dual DAC with CMOS Inputs
Grounding and power-supply decoupling strongly influence the MAX5893 performance. Unwanted digital
crosstalk can couple through the input, reference,
power-supply, and ground connections, which can
affect dynamic specifications like signal-to-noise ratio
or spurious-free dynamic range. In addition, electromagnetic interference (EMI) can either couple into or
be generated by the MAX5893. Observe the grounding
and power-supply decoupling guidelines for highspeed, high-frequency applications. Follow the powersupply and filter configuration guidelines to achieve
optimum dynamic performance.
Using a multilayer PCB with separate ground and
power-supply planes, run high-speed signals on lines
directly above the ground plane. Since the MAX5893
has separate analog and digital sections, the PCB
should include separate analog and digital ground sections with only one point connecting the three planes at
the exposed pad under the MAX5893. Run digital signals above the digital ground plane and analog/clock
signals above the analog/clock ground plane. Keep
digital signals as far away from sensitive analog inputs,
reference lines, and clock inputs as practical. Use a
symmetric design of clock input and the analog output
lines to minimize 2nd-order harmonic distortion components, thus optimizing the dynamic performance of the
DAC. Keep digital signal paths short and run lengths
matched to avoid propagation delay and data skew
mismatches.
The MAX5893 requires five separate power-supply
inputs for the analog (AV
DD1.8
and AV
DD3.3
), digital
(DV
DD1.8
and DV
DD3.3
), and clock (AV
CLK
) circuitry.
Decouple each voltage supply pin with a separate
0.1µF capacitor as close to the device as possible and
with the shortest possible connection to the appropriate
ground plane. Minimize the analog and digital load
capacitances for optimized operation. Decouple all
power-supply voltages at the point they enter the PCB
with tantalum or electrolytic capacitors. Ferrite beads
with additional decoupling capacitors forming a pi-network could also improve performance.
The exposed pad (EP) MUST be soldered to the
ground. Use multiple vias, an array of at least 4 x 4
vias, directly under the EP to provide a low thermal and
electrical impedance path for the IC.
Static Performance Parameter
Definitions
Integral Nonlinearity (INL)
Integral nonlinearity is the deviation of the values on an
actual transfer function from either a best straight-line fit
(closest approximation to the actual transfer curve) or a
line drawn between the end points of the transfer function, once offset and gain errors have been nullified.
For a DAC, the deviations are measured at every individual step.
Differential Nonlinearity (DNL)
Differential nonlinearity is the difference between an
actual step height and the ideal value of 1 LSB. A DNL
error specification of less than 1 LSB guarantees no
missing codes and a monotonic transfer function.
Offset Error
The offset error is the difference between the ideal and
the actual offset current. For a DAC, the offset point is
the average value at the output for the two midscale
digital input codes with respect to the full-scale of the
DAC. This error affects all codes by the same amount.
Gain Error
A gain error is the difference between the ideal and the
actual full-scale output voltage on the transfer curve,
after nullifying the offset error. This error alters the slope
of the transfer function and corresponds to the same
percentage error in each step.
Dynamic Performance
Parameter Definitions
Settling Time
The settling time is the amount of time required from the
start of a transition until the DAC output settles its new
output value to within the specified accuracy.
Noise Spectral Density
The DAC output noise is the sum of the quantization
noise and thermal noise. Noise spectral density is the
noise power in 1Hz bandwidth, specified in dBFS/Hz.
Signal-to-Noise Ratio (SNR)
For a waveform perfectly reconstructed from digital
samples, the theoretical maximum SNR is the ratio of
the full-scale analog output (RMS value) to the RMS
quantization error (residual error). The ideal, theoretical
maximum SNR can be derived from the DAC’s resolution (N bits):
SNR
dB
= 6.02dBx N + 1.76
dB
MAX5893
However, noise sources such as thermal noise, reference noise, clock jitter, etc. affect the ideal reading.
Therefore, SNR is computed by taking the ratio of the
RMS signal to the RMS noise, which includes all spectral components minus the fundamental, the first four
harmonics, and the DC offset.
Spurious-Free Dynamic Range (SFDR)
SFDR is the ratio of the RMS amplitude of the carrier
frequency (maximum signal components) to the RMS
value of their next largest distortion component. SFDR
is usually measured in dBc and with respect to the carrier frequency amplitude or in dBFS with respect to the
DAC’s full-scale range. Depending on its test condition,
SFDR is observed within a predefined window or
to Nyquist.
Two-/Four-Tone Intermodulation
Distortion (IMD)
The two-tone IMD is the ratio expressed in dBc (or
dBFS) of the worst 3rd-order (or higher) IMD products
to either output tone.
Adjacent Channel Leakage
Power Ratio (ACLR)
Commonly used in combination with WCDMA (wideband code-division multiple-access), ACLR reflects the
leakage power ratio in dB between the measured powers within a channel relative to its adjacent channel.
ACLR provides a quantifiable method of determining
out-of-band spectral energy and its influence on an
adjacent channel when a bandwidth-limited RF signal
passes through a nonlinear device.
12-Bit, 500Msps Interpolating and Modulating
Dual DAC with CMOS Inputs
For the latest package outline information and land patterns, go to www.maxim-ic.com/packages.
CLKP
CLKN
N.C.
N.C.
N.C.
D
VDD1.8
A11
A10
D
VDD3.3
DATACLK
TOP VIEW
A9
10
A8
A7
11
12
A6
13
14
15
A5
16
A4
A3 17
DD1.8
CLK
AV
68
1
2
3
4
5
6
7
8
9
EXPOSED PAD
DD3.3
GND
GND
AV
OUTIP
64
656667
AV
OUTIN
GND
MAX5893
DD3.3
AV
GND
OUTQP
58596061625455565763
OUTQN
GND
DD3.3
AV
GND
DD1.8
AV
5253
FSADJ
51
DACREF
50
49
48 CS
47
46
45
44
43
42
41
40
39
38
37 DV
36
35
REFIO
RESET
SCLK
SDI
SDO
DV
DD3.3
N.C.
N.C.
N.C.
N.C.
B0
B1
DD1.8
B2
B3
232221201927262524182928323130
A1
A0
A2
DD1.8
DV
N.C.
N.C.
N.C.
N.C.
SELIQ/B11
B8B9B7
DATACLK/B10
DD1.8
DV
3433
B6
B5
B4
QFN
MAX5893
12-Bit, 500Msps Interpolating and Modulating
Dual DAC with CMOS Inputs
Maxim cannot assume responsibility for use of any circuitry other than circuitry entirely embodied in a Maxim product. No circuit patent licenses are
implied. Maxim reserves the right to change the circuitry and specifications without notice at any time.
32
____________________Maxim Integrated Products, 120 San Gabriel Drive, Sunnyvale, CA 94086 408-737-7600