The MAX2140 complete receiver is designed for satellite
digital audio radio services (SDARS). The device
includes a fully monolithic VCO and only needs a SAW at
the IF and a crystal to generate the reference frequency.
To form a complete SDARS radio, the MAX2140
requires only a low-noise amplifier (LNA), which can be
controlled by a baseband controller. The small number
of external components needed makes the MAX2140based platform the lowest cost and the smallest solution for SDARS.
The receiver includes a self-contained RF AGC loop
and baseband-controlled IF AGC loop, effectively providing a total dynamic range of over 92dB.
Channel selectivity is ensured by the SAW filter and by
on-chip monolithic lowpass filters.
The fractional-N PLL allows a very small frequency
step, making possible the implementation of an AFC
loop. Additionally, the reference is provided by an
external XTAL and on-chip oscillator. A reference buffer
output is also provided.
A 2-wire interface (I
2
C-bus compatible) programs the
circuit for a wide variety of conditions, providing features such as:
•Programmable gains
•Lowpass filters tuning
•Individual functional block shutdown
The MAX2140 minimizes the requirement on the baseband controller. No compensation or calibration procedures are required. The device is available in a 7mm
(VCC= 3.1V to 3.6V; VINANT ≥ VCC, VOUTANT in open circuit, TA= -40°C to +85°C. Typical values are at VCC= 3.3V, VINANT =
3.3V, and T
A
= +25°C, unless otherwise noted.) (Note 1)
Stresses beyond those listed under “Absolute Maximum Ratings” may cause permanent damage to the device. These are stress ratings only, and functional
operation of the device at these or any other conditions beyond those indicated in the operational sections of the specifications is not implied. Exposure to
absolute maximum rating conditions for extended periods may affect device reliability.
V
CC_XX
to GND..................................................... -0.3V to +4.3V
VINANT to GND.................................................... -0.3V to +5.6V
AGCPWM to GND ................................................ -0.3V to +3.0V
Digital Input Current ........................................................ ±10mA
Maximum VSWR Without Damage ........................................ 4:1
Maximum VSWR Without Oscillations ................................... 4:1
All Other Pins ............................................... -0.3V to V
= 150mA max, VCC= 3.1V to 3.6V, VINANT = 3.1V to 5.3V, fRF= 2320MHz
to 2345MHz, f
LO
= 2076MHz, TA= -40°C to +85°C. Typical values are at VCC= VINANT = 3.3V, fRF= 2338MHz, TA= +25°C, unless
otherwise noted.) (Note 2)
Interstage (IF) 259MHz SAW filter specification: insertion loss = 19dB max, 9.3MHz to 12MHz from center attenuation = 24dB min,
beyond 12MHz from center attenuation = 40dB min.
GENERAL RECEIVER
Minimum Input RF Power to
Produce 20mV
I and Q Baseband Outputs
Maximum Input RF Power to
Produce 400mV
at I and Q Baseband Outputs
LO to RF Input Leakage
Noise Figure (Notes 3, 5)NF
In-Band Input IP3 (Notes 5, 6)I_IIP3
Out-of-Band Input IP3
(Notes 5, 7)
PARAMETERSYMBOLCONDITIONSMINTYPMAXUNITS
(Differential) at
P-P
(Differential)
P-P
P
P
P
P
O_IIP3
MIN
MAX
LK_H
LK_L
IF AGC is set at maximum gain,
bit HPF = 0 (Note 4)
RF AGC threshold: RF_AGC_TRIP =
-17dBm; IF AGC is set at minimum gain, bit
HPF = 0
LO-related spurious > 2GHz-66
LO-related spurious < 2GHz-38
RF AGC is at maximum gain,
IF AGC is at reference gain
RF AGC is at maximum gain,
IF AGC is at reference gain -10dB
RF AGC is at maximum gain -5dB,
IF AGC is at reference gain
RF AGC is at maximum gain -10dB,
IF AGC is at reference gain
RF AGC is at maximum gain,
IF AGC is at reference gain
RF AGC is at maximum gain,
IF AGC is at reference gain -5dB
RF AGC is at maximum gain -30dB,
IF AGC is at reference gain -43dB
RF AGC is at maximum gain -20dB,
IF AGC is at reference gain -53dB
RF AGC is at maximum gain,
IF AGC is at reference gain
RF AGC is at maximum gain -7dB,
IF AGC is at reference gain
RF AGC is at maximum gain -25dB,
IF AGC is at reference gain
= 150mA max, VCC= 3.1V to 3.6V, VINANT = 3.1V to 5.3V, fRF= 2320MHz
to 2345MHz, f
LO
= 2076MHz, TA= -40°C to +85°C. Typical values are at VCC= VINANT = 3.3V, fRF= 2338MHz, TA= +25°C, unless
otherwise noted.) (Note 2)
Interstage (IF) 259MHz SAW filter specification: insertion loss = 19dB max, 9.3MHz to 12MHz from center attenuation = 24dB min,
beyond 12MHz from center attenuation = 40dB min.
= 150mA max, VCC= 3.1V to 3.6V, VINANT = 3.1V to 5.3V, fRF= 2320MHz
to 2345MHz, f
LO
= 2076MHz, TA= -40°C to +85°C. Typical values are at VCC= VINANT = 3.3V, fRF= 2338MHz, TA= +25°C, unless
otherwise noted.) (Note 2)
Interstage (IF) 259MHz SAW filter specification: insertion loss = 19dB max, 9.3MHz to 12MHz from center attenuation = 24dB min,
beyond 12MHz from center attenuation = 40dB min.
IF AGC Gain-Control Range
INTERNAL BASEBAND LOWPASS FILTERS
LPF In-Band RippleLPFA_rip
LPF Out-of-Band Rejection
(Note 4)
INTERNAL OUTPUT STAGE
Gain IncreaseBB_DGFrom bit HPF = 0 to HPF = 14dB
Maximum I/QOUT± Pin LoadingIQ_loadPer each of the four pins10//10kΩ//pF
FREQUENCY GENERATION: VCO AND PLL
VCO Frequency Range
VCO Tuning GainVCO_Gain (Note 4)240MHz/V
Synthesized VCO Phase NoiseVCO_PN
Synthesized VCO Phase-Noise
Jitter
Charge-Pump Voltage RangeV
Charge-Pump CurrentI
Pin CHP Leakage CurrentCHP_leak Across V
PLL Reference Division RatioPLLref12
Synthesized VCO Smallest
Fractional Step
PARAMETERSYMBOLCONDITIONSMINTYPMAXUNITS
IFAGC_
LPFrej
LPFrej
VCO_
Range
VCO_jit
PLLstepProgrammable through I
Rge
CHP
CHP
(Note 4)4764dB
From 0 to 6.3MHz with respect to the
amplitude at 100kHz
At 10.25MHz with respect to the amplitude
at 2MHz
At 16MHz with respect to the amplitude at
2MHz
Over V
At 1kHz within PLL band-79
At 10kHz outside PLL band-80
At 100kHz outside PLL band-101
Integrated from 100Hz to 100kHz,
LO frequency = 2079MHz
= 150mA max, VCC= 3.1V to 3.6V, VINANT = 3.1V to 5.3V, fRF= 2320MHz
to 2345MHz, f
LO
= 2076MHz, TA= -40°C to +85°C. Typical values are at VCC= VINANT = 3.3V, fRF= 2338MHz, TA= +25°C, unless
otherwise noted.) (Note 2)
Interstage (IF) 259MHz SAW filter specification: insertion loss = 19dB max, 9.3MHz to 12MHz from center attenuation = 24dB min,
beyond 12MHz from center attenuation = 40dB min.
Note 1: At TA= -40°C, minimum and maximum values are guaranteed by design and characterization.
Note 2: Minimum and maximum values are guaranteed by design and characterization, unless otherwise noted.
Note 3: At T
A
= +25°C, minimum and maximum values are guaranteed by design and characterization.
Note 4: At T
A
= +25°C and TA= +85°C, parameters are production tested.
Note 5: IF AGC reference level is defined as being the required voltage applied on pin AGCPWM, and the corresponding receiver
IF gain, to measure 20mV
P-P
at each I/Q differential output when the RF input power is -91dBm. If even for zero volts
applied on pin AGCPWM the I/Q differential outputs are below 20mV
P-P
when the RF input power is -91dBm, then the refer-
ence level is defined as zero volts.
Note 6: In-band IP2 and IP3 are measured with two CW tones at RF input: f
1
= 2339.55MHz, f2= 2339.75MHz.
Note 7: Out-of-band IP2 and IP3 are measured with two CW tones at RF input: f
1
= 2326.25MHz, f2= 2330.25MHz.
Note 8: Error computed using a crystal with no error.
Note 9: No spur in the offset frequency range.
TIMING CHARACTERISTICS
Synthesized VCO SpursVCOspur
XTAL Oscillator Frequency
Range
XTAL Oscillator Frequency ErrorXTALerror Using an external XTAL (Note 8)-16+16ppm
XTAL Oscillator Input VoltageXTALswing Using an external TCXO0.8V
XTAL Oscillator Input Duty CycleXTALdutyUsing an external TCXO475053%
Reference Buffer Output VoltageREFV
PARAMETERSYMBOLCONDITIONSMINTYPMAXUNITS
XTALrge2449MHz
0Hz < f
10kHz < f
1MHz < f
Using the REFOUT pin loading specified
below (Note 4)
< 10kHz(Note 9)
offset
< 1MHz(Note 9)
offset
< 10MHz-47
offset
0.951.10V
CC
dBc
V
P-P
P-P
Reference Buffer Output Duty
Cycle
Maximum REFOUT Pin LoadingREFOUT_1d
SERIAL INTERFACE (Note 2)
Serial Clock Frequencyf
PARAMETERSYMBOLCONDITIONSMINTYPMAXUNITS
REFduty
SCL
Using an external XTAL, not overdriven;
bit RFD = 0, using the REFOUT pin loading
specified below
The front end of the MAX2140, which downconverts the
RF signal to IF, is defined from the differential RF inputs
(pins RFIN+ and RFIN-) to the output (pins IFOUT+ and
IFOUT-) to the SAW filter.
The front end includes a self-contained analog RF AGC
loop. The engagement threshold of the loop can be
programmed from -35dBm to -15dBm referred to the
RF input in 1dB steps using the RF4–RF0 programming
bits. The time constant of the loop is set externally by
the capacitor connected to RFAGC_C.
The image reject first mixer ensures a good image and
half IF rejection.
The front-end gain can be reduced by programming
bits PM3–PM0 over a 22dB range, with a step of 2dB.
This allows the selections of SAW filters with different
insertion loss.
The IF output is nominally 900Ω differentially and requires
pullup inductors to VCC, which can be used as part of the
matching network to the SAW filter impedance.
Back End
The back end, which downconverts the IF signal to
quadrature baseband, is defined from the SAW filter
inputs (pins IFIN+ and IFIN-) to the baseband outputs
(pins IOUT+, IOUT-, QOUT+, QOUT-).
The back end contains an IF AGC loop, which is closed
by the baseband controller. The IF AGC control voltage
is applied at the AGCPWM pin. The gain can be
reduced over 53dB (typ) and exhibits a log-linear characteristic.
The back end also contains individual lowpass filters on
each channel. The lowpass-filter bandwidth is the useful SDARS downconverted bandwidth (6.25MHz). The
lowpass-filter performance is factory trimmed. The bit
IOT switches between the factory-trimmed set and the
control through the I2C-compatible bus using bits
B4–B1. Even when using the factory-trimmed set, the
user can still slightly modify the cutoff frequency (by
±250kHz) by varying bits LP1/LP0.
Highpass filters are also inserted in the back-end signal
paths. Their purpose is to remove the DC offset. They
are designed for a low corner frequency so as not to
degrade the SDARS content. Their exact cutoff frequency is set by the external capacitors connected between
IF2 access pins, given by the following equation:
f
cutoff
= 1/(2 x π x R x C) [Hz]
where R = 8000Ω, C = external capacitor to be
connected.
Finally, the HPF bit allows an increase to the back-end
gain by 4dB at the slight expense of a degraded inband linearity.
Frequency Generation
An on-chip VCO and a low-step fractional-N PLL
ensure the necessary frequency generation. The 1st
mixer’s LO is at the VCO frequency itself, while the 2nd
mixer’s LO is the VCO frequency divided by 4 or by 8
(bit D48). Hence, the two possible IF frequencies for
SDARS are 467MHz and 259MHz. Typical applications
are based on 259MHz IF frequency.
The reference divider path in the PLL can either use an
external crystal and the on-chip crystal oscillator or an
external TCXO that can overdrive the on-chip crystal
oscillator. A reference division ratio of 1 or 2 is set by
the REF bit. The crystal oscillator (or TCXO) signal is
available at pin REFOUT. The output is either at the
same frequency as the reference signal, or divided by
two, based on the setting of bit RFD.
The VCO main division ratio is set by bits N6–N0 (for
the integer part) and bits F19–F00 (for the fractional
part). The minimum step is below 30Hz, small enough
for effective AFC to be implemented by the baseband.
The charge-pump (pin CPOUT) is to be connected to
the VCO tuning input (pin VTUNE) through an appropriate loop filter.
Overcurrent Protection
This DC function allows external circuitry consuming up
to 150mA and connected to the pin VOUTANT to sink
current from a VCCline (pin VINANT) through overcurrent-protection circuitry.
When no overcurrent is present, a low dropout voltage
exists between pins VINANT and VOUTANT. In overcurrent conditions (including short-circuit from
VOUTANT to GND), the current is limited to approximately 300mA and bit ACP in the READ byte status
goes high.
This circuit also senses if the current drawn at the pin
VOUTANT is typically larger than 20mA, in which case
the bit AND from the READ byte status goes high (the
purpose is to inform the baseband controller if there is
any device drawing current from VOUTANT).
The MAX2140 conforms to the Philips I2C standard,
400kbps (fast mode), and operates as a slave.
The MAX2140 addresses can be selected from three
values, which are determined by the logic state of the
two address-select pins I2CA1 and I2CA2. In all cases,
the MSB is transmitted (and read) first.
This is the standard I2C protocol. The first byte is either
C6, C4, C2 (hex) dependent on the state of the I
2
CA_
pins, for a write-to-device operation and either C7, C5,
C3 (hex) for a read-from operation (again dependent
on the state of pins I
2
CA_).
Write Operation:
The first byte is the device address plus the direction
bit (R/W = 0).
The second byte contains the internal address command of the first address to be accessed.
The third byte is written to the internal register directed
by the command address byte.
The following bytes (if any) are written into successive
internal registers.
The transfer lasts until stop conditions are encountered.
The MAX2140 acknowledges every byte transfer.
Read Operation:
When either address C3, C5, C7 is sent, the MAX2140
sends back first the status byte then the reserved byte.
See Table 5 and Table 6 for read/write register operations.
Layout Issues
The MAX2140 EV kit can be used as a starting point for
layout. For best performance, take into consideration
power-supply issues, as well as the RF, LO, and IF layout.
Power-Supply Layout
To minimize coupling between different sections of the
IC, the ideal power-supply layout is a star configuration,
which has a large decoupling capacitor at a central
V
CC
node. The VCCtraces branch out from this node,
each going to a separate V
CC
node in the MAX2140
circuit. At the end of each trace is a bypass capacitor
with impedance to ground less than 1Ω at the frequency of interest. This arrangement provides local decoupling at each V
CC
pin. Use at least one via per bypass
capacitor for a low-inductance ground connection.
Matching Network Layout
The layout of a matching network can be very sensitive
to parasitic circuit elements. To minimize parasitic
inductance, keep all traces short and place components as close to the IC as possible. To minimize parasitic capacitance, a cutout in the ground plane (and
any other planes) below the matching network components can be used. On the high-impedance ports (e.g.,
IF inputs and outputs), keep traces short to minimize
shunt capacitance.
Chip Information
TRANSISTOR COUNT: 22,000
PROCESS: BiCMOS
Table 5. Example: Write Registers 1 to 3 with 0E, D8, 26
Table 6. Example: Read from Status Registers (Sending an NACK Terminate Slave
Transmit Mode
Maxim cannot assume responsibility for use of any circuitry other than circuitry entirely embodied in a Maxim product. No circuit patent licenses are
implied. Maxim reserves the right to change the circuitry and specifications without notice at any time.
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