General Description
The MAX2010 adjustable RF predistorter is designed to
improve power amplifier (PA) adjacent-channel power
rejection (ACPR) by introducing gain and phase expansion in a PA chain to compensate for the PA’s gain and
phase compression. With its +23dBm maximum input
power level and wide adjustable range, the MAX2010
can provide up to 12dB of ACPR improvement for
power amplifiers operating in the 500MHz to 1100MHz
frequency band. Higher frequencies of operation can
be achieved with this IC’s counterpart, the MAX2009.
The MAX2010 is unique in that it provides up to 6dB of
gain expansion and 21° of phase expansion as the input
power is increased. The amount of expansion is configurable through two independent sets of control: one set
adjusts the gain expansion breakpoint and slope, while
the second set controls the same parameters for phase.
With these settings in place, the linearization circuit can
be run in either a static set-and-forget mode, or a more
sophisticated closed-loop implementation can be
employed with real-time software-controlled distortion
correction. Hybrid correction modes are also possible
using simple lookup tables to compensate for factors
such as PA temperature drift or PA loading.
The MAX2010 comes in a 28-pin thin QFN exposed
pad (EP) package (5mm x 5mm) and is specified for
the extended (-40°C to +85°C) temperature range.
Applications
cdma2000™, GSM/EDGE, and iDEN Base Stations
Feed-Forward PA Architectures
Digital Baseband Predistortion Architectures
Military Applications
Features
♦ Up to 12dB ACPR Improvement*
♦ Independent Gain and Phase Expansion Controls
♦ Gain Expansion Up to 6dB
♦ Phase Expansion Up to 21°
♦ 500MHz to 1100MHz Frequency Range
♦ Exceptional Gain and Phase Flatness
♦ Group Delay <2.4ns (Gain and Phase Sections
Combined)
♦ ±0.03ns Group Delay Ripple Over a 100MHz Band
♦ Capable of Handling Input Drives Up to +23dBm
♦ On-Chip Temperature Variation Compensation
♦ Single +5V Supply
♦ Low Power Consumption: 75mW (typ)
♦ Fully Integrated into Small 28-Pin Thin QFN
Package
*Performance dependent on amplifier, bias, and modulation.
MAX2010
500MHz to 1100MHz Adjustable
RF Predistorter
________________________________________________________________ Maxim Integrated Products 1
Functional Diagram/
Pin Configuration
Ordering Information
19-2930; Rev 0; 8/03
For pricing, delivery, and ordering information, please contact Maxim/Dallas Direct! at
1-888-629-4642, or visit Maxim’s website at www.maxim-ic.com.
*EP = Exposed paddle.
cdma2000 is a trademark of Telecommunications Industry
Assoc.
PART TEMP RANGE PIN-PACKAGE
MAX2010ETI-T -40°C to +85°C 28 Thin QFN-EP*
GND*
OUTG
GND*
GCS
GFS
28 27 26 25 24 23 22
1
GND*
2
GND*
3
ING
4
GND*
5
GND*
6
OUTP
7
GND*
*INTERNALLY CONNECTED TO EXPOSED GROUND PADDLE.
MAX2010
8 9 10 11 12 13 14
INP
GND*
GND*
CONTROL
PFS1
GAIN
PHASE
CONTROL
PFS2
GBP
PDCS1
GND*
PDCS2
21
V
CCG
20
GND*
PBRAW
19
18
PBEXP
17
PBIN
16
GND*
15
V
CCP
MAX2010
500MHz to 1100MHz Adjustable
RF Predistorter
2 _______________________________________________________________________________________
ABSOLUTE MAXIMUM RATINGS
DC ELECTRICAL CHARACTERISTICS
(MAX2010 EV kit; V
CCG
= V
CCP
= +4.75V to +5.25V; no RF signal applied; INP, ING, OUTP, OUTG are AC-coupled and terminated to
50Ω. V
PF_S1
= open; PBEXP shorted to PBRAW; V
PDCS1
= V
PDCS2
= 0.8V; V
PBIN
= V
GBP
= V
GCS
= GND; V
GFS
= V
CCG;TA
= -40°C to
+85°C. Typical values are at V
CCG
= V
CCP
= +5.0V, TA= +25°C, unless otherwise noted.)
Stresses beyond those listed under “Absolute Maximum Ratings” may cause permanent damage to the device. These are stress ratings only, and functional
operation of the device at these or any other conditions beyond those indicated in the operational sections of the specifications is not implied. Exposure to
absolute maximum rating conditions for extended periods may affect device reliability.
V
CCG
, V
CCP
to GND ..............................................-0.3V to +5.5V
ING, OUTG, GCS, GFS, GBP to GND......-0.3V to (V
CCG
+ 0.3V)
INP, OUTP, PFS_, PDCS_, PBRAW,
PBEXP, PBIN to GND ............................-0.3V to (V
CCP
+ 0.3V)
Input (ING, INP, OUTP, OUTG) Level ............................+23dBm
PBEXP Output Current ........................................................±1mA
Continuous Power Dissipation (T
A
= +70°C)
28-Pin Thin QFN-EP
(derate 21mW/°C above +70°C)...............................1667mW
Operating Temperature Range ...........................-40°C to +85°C
Junction Temperature......................................................+150°C
Storage Temperature Range .............................-65°C to +150°C
Lead Temperature (soldering 10s) ..................................+300°C
Supply Voltage V
Supply Current
Analog Input Voltage Range
Logic-Input High Voltage PDCS1, PDCS2 (Note 1) 2.0 V
Logic-Input Low Voltage PDCS1, PDCS2 (Note 1) 0.8 V
Logic Input Current -2 +2 µA
PARAMETER CONDITIONS MIN TYP MAX UNITS
, V
CCG
CCP
V
CCP
V
CCG
PBIN, PBRAW 0 V
GBP, GFS, GCS 0 V
V
= V
GFS
GCS
V
= 0 to +5V -100 +170Analog Input Current
GBP
= 0 to +5V -100 +220
V
PBIN
= V
PBRAW
= 0V -2 +2
4.75 5.25 V
5.8 7
10 12.1
CCP
CCG
mA
V
µA
MAX2010
500MHz to 1100MHz Adjustable
RF Predistorter
_______________________________________________________________________________________ 3
AC ELECTRICAL CHARACTERISTICS
(MAX2010 EV kit, V
CCG
= V
CCP
= +4.75V to +5.25V, 50Ω environment, PIN= -20dBm, fIN= 500MHz to 1100MHz, V
GCS
= +1.0V,
V
GFS
= +5.0V, V
GBP
= +1.2V, V
PBIN
= V
PDCS1
= V
PDCS2
= 0V, V
PF_S1
= +5V, V
PBRAW
= V
PBEXP,TA
= -40°C to +85°C. Typical val-
ues are at f
IN
= 880MHz, V
CCG
= V
CCP
= +5V, TA= +25°C, unless otherwise noted.) (Notes 1, 2)
PARAMETER CONDITIONS MIN TYP MAX UNITS
Operating Frequency Range 500 1100 MHz
VSWR ING, INP, OUTG, OUTP 1.3:1
PHASE CONTROL SECTION
Nominal Gain -5.5 dB
Gain Variation Over Temperature TA = -40°C to +85°C-1.7dB
Gain Flatness Over a 100MHz band ±0.1 dB
Phase-Expansion Breakpoint
Maximum
Phase-Expansion Breakpoint
Minimum
Phase-Expansion Breakpoint
Variation Over Temperature
Phase Expansion
V
= +5V 23 dBm
PBIN
V
= 0V 0.7 dBm
PBIN
= -40°C to +85°C ±1.5 dB
T
A
V
= +5V,
PF_S1
= V
V
PDCS1
P
= -20 dBm to +23 dBm
IN
V
= 5V,
PDCS1
V
= 0V,
PDCS2
= +1.5V
V
PF_S1
V
= 0V,
PDCS1
V
= 5V,
PDCS2
= +1.5V
V
PF_S1
PDCS2
= 0V,
21
16
14
Degrees
V
= 0V,
PF_S1
Phase-Expansion Slope
Maximum
Phase-Expansion Slope Minimum
Phase-Slope Variation Over
Temperature
= V
V
PDCS1
P
= -20dBm to +23dBm
IN
= +9dBm 1.4
P
IN
= 0V,
V
PF_S1
V
= V
PDCS1
= +9dBm
P
IN
= +9dBm, TA = -40°C to +85°C 0.05
P
IN
PDCS2
PDCS2
= +5V,
= +5V,
6
0.6
Degrees
/dB
Degrees
/dB
Degrees
/dB
Phase Ripple Over a 100MHz band, deviation from linear phase ±0.02 Degrees
Noise Figure 5.5 dB
Absolute Group Delay Interconnects de-embedded 1.3 ns
Group Delay Ripple Over a 100MHz band ±0.01 ns
Parasitic Gain Expansion PIN = -20dBm to +23dBm +0.4 dB
MAX2010
500MHz to 1100MHz Adjustable
RF Predistorter
4 _______________________________________________________________________________________
Note 1: Guaranteed by design and characterization.
Note 2: All limits reflect losses and characteristics of external components shown in the Typical Application Circuit, unless otherwise
noted.
AC ELECTRICAL CHARACTERISTICS (continued)
(MAX2010 EV kit, V
CCG
= V
CCP
= +4.75V to +5.25V, 50Ω environment, PIN= -20dBm, fIN= 500MHz to 1100MHz, V
GCS
= +1.0V,
V
GFS
= +5.0V, V
GBP
= +1.2V, V
PBIN
= V
PDCS1
= V
PDCS2
= 0V, V
PF_S1
= +5V, V
PBRAW
= V
PBEXP,TA
= -40°C to +85°C. Typical val-
ues are at f
IN
= 880MHz, V
CCG
= V
CCP
= +5V, TA= +25°C, unless otherwise noted.) (Notes 1, 2)
GAIN CONTROL SECTION
Nominal Gain
PARAMETER CONDITIONS MIN TYP MAX UNITS
Gain Variation Over Temperature TA = -40°C to +85°C-1.4dB
Gain Flatness Over a 100MHz band ±0.2 dB
Gain-Expansion Breakpoint
Maximum
Gain-Expansion Breakpoint
Minimum
Gain-Expansion Breakpoint
Variation Over Temperature
Gain-Expansion
Gain-Expansion Slope
Gain-Slope Variation Over
Temperature
Noise Figure 14.9 dB
Absolute Group Delay Interconnects de-embedded 1.12 ns
Group Delay Ripple Over a 100MHz band ±0.02 ns
Phase Ripple Over a 100MHz band, deviation from linear phase ±0.09 Degrees
Parasitic Phase Expansion PIN = -20dBm to +23dBm +3 Degrees
V
GCS
V
GCS
V
GBP
V
GBP
T
= -40°C to +85°C-0.5dB
A
V
GFS
V
GFS
V
GFS
V
GFS
P
IN
= 0V, V
GFS
= +5V, V
= +5V 23 dBm
= +0.5V -2.5 dBm
= +5V, PIN = -20dBm to +23dBm 5.3
= 0V, PIN = -20dBm to +23dBm 3.1
= +5V, PIN = +15dBm 0.43
= +0V, PIN = +15dBm 0.23
= +15dBm, TA = -40°C to +85°C -0.01 dB/dB
= +5V -24.3
= 0V -7.6
GFS
-14.9
dB
dB
dB/dB
MAX2010
500MHz to 1100MHz Adjustable
RF Predistorter
_______________________________________________________________________________________ 5
Typical Operating Characteristics
Phase Control Section
(MAX2010 EV kit, V
CCP
= +5.0V, PIN= -20dBm, V
PBIN
= 0V, V
PF_S1
= +5.0V, V
PDCS1
= V
PDCS2
= 0V, fIN= 880MHz, TA= +25°C
unless otherwise noted.)
SUPPLY CURRENT
vs. SUPPLY VOLTAGE
6.6
6.5
6.4
6.3
TA = +85°C
6.2
6.1
6.0
5.9
SUPPLY CURRENT (mA)
5.8
5.7
5.6
4.75 4.954.85 5.05 5.15 5.25
TA = +25°C
TA = -40°C
SUPPLY VOLTAGE (V)
LARGE-SIGNAL INPUT RETURN LOSS
vs. FREQUENCY
0
0
MAX2010 toc01
10
20
30
INPUT RETURN LOSS (dB)
40
50
0.5 0.6 0.7
A = V
B = V
C = V
D = V
0
SMALL-SIGNAL INPUT RETURN LOSS
vs. FREQUENCY
FREQUENCY (GHz)
= V
PDCS1
PDCS2
= V
PDCS1
PDCS2
= V
PDCS1
PDCS2
= V
PDCS1
PDCS2
LARGE-SIGNAL OUTPUT RETURN LOSS
vs. FREQUENCY
D
= V
= 0V, V
= 5V, V
= V
B
0.9 1.0 1.1
0.8
= 0V
PF_S1
PF_S1
PF_S1
= 5V
PF_S1
C
= 5V
= 0V
A
0
MAX2010 toc02
10
20
30
OUTPUT RETURN LOSS (dB)
40
50
0.5 0.6 0.7
-4.0
SMALL-SIGNAL OUTPUT RETURN LOSS
A = V
B = V
C = V
D = V
vs. FREQUENCY
FREQUENCY (GHz)
= V
= V
= V
= V
PDCS2
PDCS2
PDCS2
PDCS2
= V
= 0V, V
= 5V, V
= V
PDCS1
PDCS1
PDCS1
PDCS1
SMALL-SIGNAL GAIN
vs. FREQUENCY
A
0.8
PF_S1
D
PF_S1
PF_S1
PF_S1
B
C
0.9 1.0 1.1
= 0V
= 5V
= 0V
= 5V
MAX2010 toc03
10
20
30
INPUT RETURN LOSS (dB)
40
50
0.5 0.6 0.7
PIN = +15dBm
= V
A = V
PDCS1
= V
B = V
PDCS1
= V
C = V
PDCS1
= V
D = V
PDCS1
-4.5
MAX2010 toc05
-5.0
-5.5
GAIN (dB)
-6.0
-6.5
-7.0
0.5 1.1
TA = -40°C
TA = +25°C
TA = +85°C
FREQUENCY (GHz)
1.00.90.80.70.6
B
D
0.8
FREQUENCY (GHz)
= V
PDCS2
PF_S1
= 0V, V
PDCS2
PDCS2
PDCS2
= 5V, V
= V
PF_S1
PF_S1
PF_S1
A
C
0.9 1.0 1.1
= 0V
= 5V
= 0V
= 5V
MAX2010 toc04
10
20
30
OUTPUT RETURN LOSS (dB)
40
50
0.5 0.6 0.7
PIN = +15dBm
A = V
B = V
C = V
D = V
PDCS1
PDCS1
PDCS1
PDCS1
FREQUENCY (GHz)
= V
= V
PDCS2
= V
= 0V, V
PDCS2
= V
= 5V, V
PDCS2
= V
= V
PDCS2
0.8
D
PF_S1
PF_S1
B
= 0V
PF_S1
PF_S1
= 5V
A
C
0.9 1.0 1.1
= 5V
= 0V
MAX2010 toc06
MAX2010
500MHz to 1100MHz Adjustable
RF Predistorter
6 _______________________________________________________________________________________
Typical Operating Characteristics (continued)
Phase Control Section (continued)
(MAX2010 EV kit, V
CCP
= +5.0V, PIN= -20dBm, V
PBIN
= 0V, V
PF_S1
= +5.0V, V
PDCS1
= V
PDCS2
= 0V, fIN= 880MHz, TA= +25°C
unless otherwise noted.)
-4.0
-4.5
-5.0
-5.5
GAIN (dB)
-6.0
SMALL-SIGNAL GAIN
V
vs. FREQUENCY
= 4.75V, 5.0V, 5.25V
CCP
MAX2010 toc07
-4.0
-4.5
-5.0
-5.5
GAIN (dB)
-6.0
SMALL-SIGNAL GAIN
vs. COARSE SLOPE
V
= 1.5V
PF_S1
V
= 5V
PF_S1
V
PF_S1
= 0V
MAX2010 toc08
SMALL-SIGNAL GAIN
vs. COARSE SLOPE
-4.0
-4.5
-5.0
-5.5
GAIN (dB)
-6.0
TA = -40°C
= +25°C
T
A
= +85°C
T
A
MAX2010 toc09
-6.5
-7.0
0.5 1.1
FREQUENCY (GHz)
GROUP DELAY vs. FREQUENCY
1.50
1.45
1.40
1.35
DELAY (ns)
1.30
1.25
1.20
0.5 1.1
A = V
= V
PDCS1
= V
B = V
PDCS1
= V
C = V
PDCS1
= V
D = V
PDCS1
INTERCONNECTS DE-EMBEDDED
D
FREQUENCY (GHz)
= V
PDCS2
PF_S1
= 0V, V
PDCS2
PDCS2
PDCS2
= 5V, V
= V
PF_S1
PF_S1
PF_S1
= 0V
= 5V
C
= 5V
= 0V
-6.5
-7.0
1.00.90.80.70.6
PDCS1 = 0
PDCS2 = 0
PDCS1 = 5
PDCS2 = 0
COARSE SLOPE (V)
PDCS1 = 0
PDCS2 = 5
PDCS1 = 5
PDCS2 = 5
NOISE FIGURE vs. FREQUENCY
7.0
6.8
MAX2010 toc10
6.6
6.4
6.2
6.0
A
B
1.00.90.80.70.6
5.8
NOISE FIGURE (dB)
5.6
5.4
5.2
5.0
0.5 1.1
A = V
B = V
C = V
D = V
A
PDCS1
PDCS1
PDCS1
PDCS1
D
B
FREQUENCY (GHz)
= V
= V
PDCS2
= V
= 0V, V
PDCS2
= V
= 5V, V
PDCS2
= V
= V
PDCS2
PF_S1
PF_S1
= 0V
PF_S1
PF_S1
= 5V
= 5V
= 0V
C
1.00.90.80.70.6
-6.5
-7.0
PDCS1 = 0
PDCS2 = 0
6.00
5.95
MAX2010 toc11
5.90
5.85
5.80
SUPPLY CURRENT (mA)
5.75
5.70
PDCS1 = 5
PDCS2 = 0
COARSE SLOPE (V)
PDCS1 = 0
PDCS2 = 5
PDCS1 = 5
PDCS2 = 5
SUPPLY CURRENT vs. INPUT POWER
MAX2010 toc12
B
C
D = V
E = V
D
E
161284
20
= 1.5V
PBIN
= 3.0V
PBIN
A
024
PBIN
PBIN
PBIN
= 0V
= 0.5V
= 1.0V
INPUT POWER (dBm)
A = V
B = V
C = V
MAX2010
500MHz to 1100MHz Adjustable
RF Predistorter
_______________________________________________________________________________________ 7
Typical Operating Characteristics (continued)
Phase Control Section (continued)
(MAX2010 EV kit, V
CCP
= +5.0V, PIN= -20dBm, V
PBIN
= 0V, V
PF_S1
= +5.0V, V
PDCS1
= V
PDCS2
= 0V, fIN= 880MHz, TA= +25°C
unless otherwise noted.)
GAIN EXPANSION vs. INPUT POWER
-4.5
-4.7
-4.9
-5.1
GAIN (dB)
-5.3
-5.5
-5.7
-7
A = V
B = V
C = V
D
C
B
38-2 13 18 23
INPUT POWER (dBm)
D = V
= 0V
PBIN
PBIN
PBIN
= 0.5V
= 1.0V
E = V
F = V
F
E
MAX2010 toc13
PHASE (DEGREES)
-10
-15
-20
PBIN
PBIN
PBIN
A
= 1.5V
= 2.0V
= 2.5V
PHASE EXPANSION vs. INPUT POWER
15
10
5
0
A
-5
-7
PBIN
PBIN
PBIN
= 0V
= 0.5V
= 1.0V
INPUT POWER (dBm)
A = V
B = V
C = V
B
38-2 13 18 23
= 1.5V
D = V
PBIN
= 2.0V
E = V
PBIN
= 2.5V
F = V
PBIN
C
D
E
F
MAX2010 toc14
GAIN EXPANSION vs. INPUT POWER
-4.5
-4.7
-4.9
-5.1
GAIN (dB)
-5.3
-5.5
-5.7
-7 3 8-2 13 18 23
= V
PDCS2
= 5V, V
PDCS2
INPUT POWER (dBm)
= 0V
A = V
B = V
PDCS1
PDCS1
= 0V
C = V
D = V
A
D
PDCS1
PDCS1
B
C
= 0V, V
= V
PDCS2
PDCS2
= 5V
MAX2010 toc15
= 5V
GAIN EXPANSION vs. INPUT POWER
-4.5
-4.8
-5.1
GAIN (dB)
-5.4
-5.7
-7 3 8-2 13 18 23
A = V
B = V
C = V
D = V
PF_S1
PF_S1
PF_S1
PF_S1
= 0V
= 0.5V
= 1.0V
= 1.5V
F
INPUT POWER (dBm)
E
E = V
F = V
V
PDCS1
D
PF_S1
PF_S1
= 5.0V
C
= 2.0V
= 5.0V
A
PHASE EXPANSION vs. INPUT POWER
15
10
MAX2010 toc16
5
0
B
-5
PHASE (DEGREES)
-10
-15
-20
-7
A = V
PF_S1
B = V
PF_S1
C = V
PF_S1
38-2 13 18 23
INPUT POWER (dBm)
= 0V
= 0.5V
= 1.0V
D
D = V
E = V
F = V
V
PDCS1
PF_S1
PF_S1
PF_S1
= 5.0V
C
F
E
= 1.5V
= 2.0V
= 5.0V
B
MAX2010 toc17
A
PHASE EXPANSION vs. INPUT POWER
15
10
5
0
-5
PHASE (DEGREES)
-10
-15
-20
-7
A = V
PDCS1
B = V
PDCS1
C = V
PDCS1
D = V
PDCS1
B
A
38-2 13 18 23
INPUT POWER (dBm)
= V
= 0V
PDCS2
= 5V, V
= 0V, V
= V
PDCS2
PDCS2
PDCS2
= 5V
= 0V
= 5V
MAX2010 toc18
D
C
MAX2010
500MHz to 1100MHz Adjustable
RF Predistorter
8 _______________________________________________________________________________________
Typical Operating Characteristics
Gain Control Section
(MAX2010 EV kit, V
CCG
= +5.0V, PIN= -20dBm, V
GBP
= +1.2V, V
GFS
= +5.0V, V
GCS
= +1.0V, fIN= 880MHz, TA= +25°C, unless
otherwise noted.)
Typical Operating Characteristics (continued)
Phase Control Section (continued)
(MAX2010 EV kit, V
CCP
= +5.0V, PIN= -20dBm, V
PBIN
= 0V, V
PF_S1
= +5.0V, V
PDCS1
= V
PDCS2
= 0V, fIN= 880MHz, TA= +25°C
unless otherwise noted.)
-4.0
-4.2
-4.4
-4.6
-4.8
-5.0
GAIN (dB)
-5.2
-5.4
-5.6
-5.8
GAIN EXPANSION vs. INPUT POWER
V
= 5.0, V
PDCS1
TA = -40°C
= +25°C
T
A
= +85°C
T
A
-7 3 8-2 13 18 23
= 1.5V
PF_S1
INPUT POWER (dBm)
MAX2010 toc19
0
-5
-10
-15
PHASE (DEGREES)
-20
-25
-7 3 8-2 13 18 23
PHASE EXPANSION vs. INPUT POWER
V
= 5.0, V
PDCS1
T
A
= +25°C
PF_S1
T
= -40°C
A
INPUT POWER (dBm)
= 1.5V
MAX2010 toc20
= +85°C
T
A
SUPPLY CURRENT vs. SUPPLY VOLTAGE
6.6
6.5
6.4
6.3
TA = +85°C
6.2
6.1
6.0
5.9
SUPPLY CURRENT (mA)
5.8
5.7
5.6
4.75 4.954.85 5.05 5.15 5.25
TA = +25°C
SUPPLY VOLTAGE (V)
TA = -40°C
0
MAX2010 toc21
10
20
30
INPUT RETURN LOSS (dB)
40
50
0.5 1.1
A = V
B = V
SMALL-SIGNAL INPUT RETURN LOSS
vs. FREQUENCY
A, B
FREQUENCY (GHz)
= 0V, V
= 0V, V
GFS
GFS
= 0V
= 5V
GCS
GCS
C, D
C = V
D = V
1.00.90.80.70.6
= 5V, V
GCS
GFS
= 5V, V
GCS
GFS
= 0V
= 5V
0
MAX2010 toc22
10
20
30
OUTPUT RETURN LOSS (dB)
40
50
0.5 1.1
A = V
B = V
SMALL-SIGNAL OUTPUT RETURN LOSS
GCS
GCS
= 0V, V
= 0V, V
vs. FREQUENCY
C, D
A, B
FREQUENCY (GHz)
= 0V
= 5V
C = V
D = V
GFS
GFS
0.90.80.70.6
GCS
GCS
1.0
= 5V, V
= 5V, V
GFS
GFS
= 0V
= 5V
MAX2010 toc23
MAX2010
500MHz to 1100MHz Adjustable
RF Predistorter
_______________________________________________________________________________________ 9
Typical Operating Characteristics (continued)
Gain Control Section (continued)
(MAX2010 EV kit, V
CCP
= +5.0V, PIN= -20dBm, V
PBIN
= 0V, V
PF_S1
= +5.0V, V
PDCS1
= V
PDCS2
= 0V, fIN= 880MHz, TA= +25°C
unless otherwise noted.)
LARGE-SIGNAL INPUT RETURN LOSS
vs. FREQUENCY
0
PIN = +15dBm
10
20
30
INPUT RETURN LOSS (dB)
40
50
A
0.5 1.1
= 0V, V
= 0V, V
FREQUENCY (GHz)
= 0V
C = V
GFS
= 5V
D = V
GFS
A = V
B = V
GCS
GCS
LARGE-SIGNAL OUTPUT RETURN LOSS
vs. FREQUENCY
0
PIN = +15dBm
MAX2010 toc24
10
D
C
B
1.0
0.90.80.70.6
= 5V, V
= 5V, V
GFS
GFS
= 0V
= 5V
GCS
GCS
20
30
OUTPUT RETURN LOSS (dB)
40
50
A
0.5 1.1
A = V
= 0V, V
GCS
GFS
= 0V, V
B = V
GCS
GFS
D
FREQUENCY (GHz)
= 0V
C = V
= 5V
D = V
C
0.90.80.70.6
GCS
GCS
B
1.0
= 5V, V
= 5V, V
= 0V
GFS
= 5V
GFS
MAX2010 toc25
SMALL-SIGNAL GAIN vs. FREQUENCY
-12
-13
-14
-15
-16
GAIN (dB)
-17
-18
-19
-20
TA = +85°C
TA = -40°C
TA = +25°C
FREQUENCY (GHz)
MAX2010 toc26
1.00.90.80.70.60.5 1.1
SMALL-SIGNAL GAIN vs. FREQUENCY
-12
V
= 4.75V, 5.0V, 5.25V
CCG
-13
-14
-15
-16
GAIN (dB)
-17
-18
-19
-20
FREQUENCY (GHz)
1.00.90.80.70.60.5 1.1
MAX2010 toc27
SMALL-SIGNAL GAIN vs. V
0
V
= 0V, 1.5V, 5.0V
GFS
-5
-10
-15
GAIN (dB)
-20
-25
-30
034215
V
(V)
GCS
GCS
MAX2010 toc28
0
-5
-10
-15
GAIN (dB)
-20
-25
-30
034215
SMALL-SIGNAL GAIN vs. V
TA = -40°C
TA = +25°C
V
GCS
(V)
TA = +85°C
V
GFS
GCS
MAX2010 toc29
= +1.5V
MAX2010
500MHz to 1100MHz Adjustable
RF Predistorter
10 ______________________________________________________________________________________
Typical Operating Characteristics (continued)
Gain Control Section (continued)
(MAX2010 EV kit, V
CCP
= +5.0V, PIN= -20dBm, V
PBIN
= 0V, V
PF_S1
= +5.0V, V
PDCS1
= V
PDCS2
= 0V, fIN= 880MHz, TA= +25°C
unless otherwise noted.)
GROUP DELAY vs. FREQUENCY
MAX2010 toc30
FREQUENCY (GHz)
INTERCONNECTS DE-EMBEDDED
DELAY (ns)
A = V
GCS
= 0V, V
GFS
= 0V
B = V
GCS
= 0V, V
GFS
= 5V
C = V
GCS
= 5V, V
GFS
= 0V
D = V
GCS
= 5V, V
GFS
= 5V
1.00.90.80.70.6
0.9
1.0
1.1
1.2
1.3
1.4
1.5
0.8
0.5 1.1
C, D
A
B
NOISE FIGURE vs. FREQUENCY
30
SUPPLY CURRENT vs. INPUT POWER
30
GAIN EXPANSION vs. INPUT POWER
-5
-8
D
A
-11
GAIN (dB)
-14
-17
A
25
20
15
NOISE FIGURE (dB)
10
5
0.5 1.1
A = V
= 0V, V
GCS
= 0V, V
B = V
GCS
= 1.5V, V
C = V
GCS
C
B
E
G
F
B
FREQUENCY (GHz)
= 0V
GFS
= 5V
GFS
= 5V
GFS
MAX2010 toc33
H
C
E
D = V
GCS
E = V
GCS
-5
-7
-9
-11
PHASE (DEGREES)
-13
MAX2010 toc31
25
20
C
04812 2016 24
A = V
GBP
B = V
GBP
C = V
GBP
1.00.90.80.70.6
= 5V, V
= 5V, V
GFS
GFS
D
= 0V
= 5V
15
SUPPLY CURRENT (mA)
10
5
PHASE EXPANSION vs. INPUT POWER
B
A
F
G
H
D
E
B
A
INPUT POWER (dBm)
= 0V
= 0.5V
= 1.0V
C
MAX2010 toc34
D = V
E = V
GBP
GBP
D
= 1.5V
= 3.0V
MAX2010 toc32
E
-20
-7 -2
3
INPUT POWER (dBm)
A = V
= 0V
GBP
= 0.5V
B = V
GBP
= 1.0V
C = V
GBP
= 1.5V
D = V
GBP
81813 23
= 2.0V
E = V
GBP
= 2.5V
F = V
GBP
= 3.5V
G = V
GBP
= 5.0V
H = V
GBP
-15
-7 -2
3
INPUT POWER (dBm)
A = V
= 0V
GBP
= 0.5V
B = V
GBP
= 1.0V
C = V
GBP
= 1.5V
D = V
GBP
81813 23
E = V
= 2.0V
GBP
= 2.5V
F = V
GBP
= 3.5V
G = V
GBP
= 5.0V
H = V
GBP
MAX2010
500MHz to 1100MHz Adjustable
RF Predistorter
______________________________________________________________________________________ 11
Typical Operating Characteristics (continued)
Gain Control Section (continued)
(MAX2010 EV kit, V
CCP
= +5.0V, PIN= -20dBm, V
PBIN
= 0V, V
PF_S1
= +5.0V, V
PDCS1
= V
PDCS2
= 0V, fIN= 880MHz, TA= +25°C
unless otherwise noted.)
GAIN EXPANSION vs. INPUT POWER
-5
-8
-11
GAIN (dB)
-14
-17
-20
-7 -2
3
INPUT POWER (dBm)
A = V
= 0V
GFS
= 0.5V
B = V
GFS
= 1.0V
C = V
GFS
PHASE EXPANSION vs. INPUT POWER
-5
-6
-7
-8
-9
-10
-11
PHASE (DEGREES)
-12
-13
-14
-15
-7 -2
A = V
B = V
C = V
A, B
3
INPUT POWER (dBm)
= 0V
GFS
= 0.5V
GFS
= 1.0V
GFS
E
MAX2010 toc35
F
D
C
A, B
81813 23
D = V
= 1.5V
GFS
= 2.0V
E = V
GFS
= 5.0V
F = V
GFS
F
E
D
C
81813 23
= 1.5V
D = V
GFS
= 2.0V
E = V
GFS
= 5.0V
F = V
GFS
GAIN (dB)
MAX2010 toc38
GAIN (dB)
GAIN EXPANSION vs. INPUT POWER
-5
F
-7
-9
-11
-13
-15
-17
-19
-21
-23
-25
-7 -2
A = V
B = V
C = V
D
A, B
GCS
GCS
GCS
GAIN EXPANSION vs. INPUT POWER
-8
-9
-10
-11
-12
TA = -40°C
-13
-14
= +25°C
T
A
-15
= +85°C
T
A
-16
-17
-7 -2
E
C
81813 23
3
INPUT POWER (dBm)
= 0V
= 0.5V
= 1.0V
3
INPUT POWER (dBm)
D = V
E = V
F = V
81813 23
GCS
GCS
GCS
= 1.5V
= 2.0V
= 2.5V
MAX2010 toc36
MAX2010 toc39
PHASE EXPANSION vs. INPUT POWER
30
20
A, B
10
0
PHASE (DEGREES)
-10
-20
-7 -2
A = V
B = V
C = V
C
D
81813 23
3
INPUT POWER (dBm)
= 0V
GCS
= 0.5V
GCS
= 1.0V
GCS
PHASE EXPANSION vs. INPUT POWER
-5
-6
-7
-8
-9
TA = -40°C
-10
TA = +25°C
-11
PHASE (DEGREES)
-12
-13
-14
-15
-7 -2
TA = +85°C
3
INPUT POWER (dBm)
81813 23
D = V
E = V
F = V
E
GCS
GCS
GCS
= 1.5V
= 2.0V
= 5.0V
F
MAX2010 toc37
MAX2010 toc40
MAX2010
500MHz to 1100MHz Adjustable
RF Predistorter
12 ______________________________________________________________________________________
Detailed Description
The MAX2010 adjustable predistorter can provide up to
12dB of ACPR improvement for high-power amplifiers
by introducing gain and phase expansion to compensate for the PA’s gain and phase compression. The
MAX2010 enables real-time software-controlled distortion correction, as well as set-and-forget tuning through
the adjustment of the expansion starting point (breakpoint) and the rate of expansion (slope). The gain and
phase breakpoints can be set over a 20dB input power
range. The phase expansion slope is variable from
0.3°/dB to 2.0°/dB and can be adjusted for a maximum
of 21° of phase expansion. The gain expansion slope is
variable from 0.1dB/dB to 0.53dB/dB and can be
adjusted for a maximum of 6dB gain expansion.
The following sections describe the tuning methodology
best implemented with a class A amplifier. Other classes
of operation may require significantly different settings.
Pin Description
PIN NAME FUNCTION
1, 2, 4, 5, 7,
8, 10, 16, 20,
22, 26, 28
3 ING
6 OUTP
9 INP RF Phase Input. Connect INP to a coupling capacitor. This pin is interchangeable with OUTP.
11 PFS1 Fine Phase-Slope Control Input 1. See the Typical Application Circuit.
12 PFS2 Fine Phase-Slope Control Input 2. See the Typical Application Circuit.
13 PDCS1 Digital Coarse Phase-Slope Control Range Input 1. Set to logical zero for the steepest slope.
14 PDCS2 Digital Coarse Phase-Slope Control Range Input 2. Set to logical zero for the steepest slope.
15 V
17 PBIN Phase Breakpoint Control Input
18 PBEXP Phase Expansion Output. Connect PBEXP to PBRAW to use PBIN as the breakpoint control voltage.
19 PBRAW Uncompensated Phase Breakpoint Input
21 V
23 GBP Gain Breakpoint Control Input
GND Ground. Internally connected to the exposed paddle.
RF Gain Input. Connect ING to a coupling capacitor if it is not connected to OUTP. ING is
interchangeable with OUTG.
RF Phase Output. Connect OUTP to a coupling capacitor if it is not connected to INP. OUTP is
interchangeable with INP.
CCP
CCG
Phase-Control Supply Voltage. Bypass with a 0.01µF capacitor to ground as close to the device as
possible. Phase section can operate without V
Gain-Control Supply Voltage. Bypass with a 0.01µF capacitor to ground as close to the device as
possible. Gain section can operate without V
CCP
CCG
.
.
24 GFS Fine Gain-Slope Control Input
25 GCS Coarse Gain-Slope Control Input
27 OUTG RF Gain Output. Connect OUTG to a coupling capacitor. OUTG is interchangeable with ING.
EP GND Exposed Ground Paddle. Solder EP to the ground plane.
MAX2010
500MHz to 1100MHz Adjustable
RF Predistorter
______________________________________________________________________________________ 13
Phase Expansion Circuitry
Figure 1 shows a typical PA’s phase behavior with
respect to input power. For input powers less than the
breakpoint level, the phase remains relatively constant.
As the input power becomes greater than the breakpoint level, the phase begins to compress and deteriorate the power amplifier’s linearity. To compensate for
this AM-PM distortion, the MAX2010 provides phase
expansion, which occurs at the same breakpoint level
but with the opposite slope. The overall result is a flat
phase response.
Phase Expansion Breakpoint
The phase expansion breakpoint is typically controlled
by a digital-to-analog converter (DAC) connected
through the PBIN pin. The PBIN input voltage range of
0V to VCCcorresponds to a breakpoint input power
range of 0.7dBm to 23dBm. To achieve optimal performance, the phase expansion breakpoint of the
MAX2010 must be set to equal the phase compression
breakpoint of the PA.
Phase Expansion Slope
The phase expansion slope of the MAX2010 must also
be adjusted to equal the opposite slope of the PA’s
phase compression curve. The phase expansion slope
of the MAX2010 is controlled by the PFS1, PFS2, PDCS1,
and PDCS2 pins. With pins PFS1 and PFS2 AC-coupled
and connected to a variable capacitor or varactor diode,
the PFS1 and PFS2 pins perform the task of fine tuning
the phase expansion slope. Since off-chip varactor
diodes are recommended for this function, they must
be closely matched and identically biased. A minimum
effective capacitance of 2pF to 6pF is required
to achieve the full phase slope range as specified in
the Electrical Characteristics tables.
As shown in Figure 2, the varactors connected to PFS1
and PFS2 are in series with three internal capacitors on
each pin. By connecting and disconnecting these internal capacitors, a larger change in phase expansion
slope can be achieved through the logic levels presented at the PDCS1 and PDCS2 pins. The phase expansion slope is at its maximum when both V
PDCS1
and
V
PDCS2
equal 0V. The phase tuning has a minimal
effect on the small-signal gain.
Gain Expansion Circuitry
In addition to phase compression, the PA also suffers
from gain compression (AM-AM) distortion, as shown in
Figure 3. The PA gain curve remains flat for input powers below the breakpoint level, and begins to compress
at a given rate (slope) for input powers greater than the
breakpoint level. To compensate for such gain compression, the MAX2010 generates a gain expansion,
which occurs at the same breakpoint level with the
opposite slope. The overall result is a flat gain response
at the PA output.
Figure 1. PA Phase Compression Canceled by MAX2010 Phase Expansion
PA PHASE
COMPRESSION
BREAKPOINT
SLOPE
PA PHASE (DEGREES)
P
(dBm) P
IN
MAX2010 PHASE (DEGREES)
MAX2010
PHASE EXPANSION
(dBm) P
IN
IMPROVED
PHASE DISTORTION
COMBINED PHASE (DEGREES)
(dBm)
IN
MAX2010
500MHz to 1100MHz Adjustable
RF Predistorter
14 ______________________________________________________________________________________
Figure 2. Simplified Phase Slope Internal Circuitry
Figure 3. PA Gain Compression Canceled by MAX2010 Gain Expansion
PFS1
PF_S1
PFS2
2
PDCS1
PHASE-CONTROL
CIRCUITRY
SWITCH
PDCS2
CONTROL
PA GAIN (dB)
PA GAIN
COMPRESSION
BREAKPOINT
SLOPE
P
(dBm) P
IN
MAX2010 GAIN (dB)
MAX2010
GAIN EXPANSION
(dBm) P
IN
MAX2010
COMBINED GAIN (dB)
IMPROVED
GAIN DISTORTION
(dBm)
IN
MAX2010
500MHz to 1100MHz Adjustable
RF Predistorter
______________________________________________________________________________________ 15
Gain Expansion Breakpoint
The gain expansion breakpoint is usually controlled by
a DAC connected through the GBP pin. The GBP input
voltage range of 0.5V to 5V corresponds to a breakpoint input power range of -2.5dBm to 23dBm. To
achieve the optimal performance, the gain expansion
breakpoint of the MAX2010 must be set to equal the
gain compression point of the PA. The GBP control has
a minimal effect on the small-signal gain when operated from 0.5V to 5V.
Gain Expansion Slope
In addition to properly setting the breakpoint, the gain
expansion slope of the MAX2010 must also be adjusted
to compensate for the PA’s gain compression. The
slope should be set using the following equation:
where:
MAX2010_SLOPE = MAX2010 gain section’s slope in
dB/dB.
PA_SLOPE = PA’s gain slope in dB/dB, a negative
number for compressive behavior.
To modify the gain expansion slope, two adjustments
must be made to the biases applied on pins GCS and
GFS. Both GCS and GFS have an input voltage range of
0V to VCC, corresponding to a slope of approximately
0.1dB/dB to 0.53dB/dB. The slope is set to maximum
when V
GCS
= 0V and V
GFS
= +5V, and the slope is at its
minimum when V
GCS
= +5V and V
GFS
= 0V.
Unlike the GBP pin, modifying the gain expansion slope
bias on the GCS pin causes a change in the part’s insertion loss and noise figure. For example, a smaller slope
caused by GCS results in a better insertion loss and
lower noise figure. The GFS does not affect the insertion
loss. It can provide up to -30% or +30% total slope variation around the nominal slope set by GCS.
Large amounts of GCS bias adjustment can also lead to
an undesired (or residual) phase expansion/compression behavior. There exists an optimal bias voltage that
minimizes this parasitic behavior (typically GCS = 1.0V).
Control voltages higher than the optimal result in parasitic phase expansion, lower control voltages result in
phase compression. GFS does not contribute to the
phase behavior and is preferred for slope control.
Applications Information
The following section describes the tuning methodology
best implemented with a class A amplifier. Other classes
of operation may require significantly different settings.
Gain and Phase Expansion Optimization
The best approach to improve the ACPR of a PA is to
first optimize the AM-PM response of the phase section. For most high-frequency LDMOS amplifiers,
improving the AM-PM response provides the bulk of the
ACPR improvement. Figure 4 shows a typical configuration of the phase tuning circuit. A power sweep on a
network analyzer allows quick real-time tuning of the
AM-PM response. First, tune PBIN to achieve the phase
expansion starting point (breakpoint) at the same point
where the PA’s phase compression begins. Next, use
control pins PF_S1, PDCS1, and PDCS2 to obtain the
optimal AM-PM response. The typical values for these
pins are shown in Figure 4.
To further improve the ACPR, connect the phase output to the gain input through a preamplifier. The preamplifier is used to compensate for the high insertion
loss of the gain section. Figure 5 shows a typical application circuit of the MAX2010 with the phase section
cascaded to the gain section for further ACPR optimization. Similar to tuning the phase section, first tune
the gain expansion breakpoint through the GBP pin
and adjust for the desired gain expansion with pins
GCS and GFS. To minimize the effect of GCS on the
parasitic phase response, minimize the control voltage
to around 1V. Some retuning of the AM-PM response
may be necessary.
Layout Considerations
A properly designed PC board is an essential part of any
high-frequency circuit. In order to minimize external components, the PC board can be designed to incorporate
small values of inductance and capacitance to optimize
the input and output VSWR (refer to the MAX2009/
MAX2010 EV Kit). The phase section’s PFS1 and PFS2
pins are sensitive to external parasitics. Minimize trace
lengths and keep varactor diodes close to the pins.
Remove the ground plane underneath the traces can further help reduce the parasitic capacitance. For best performance, route the ground pin traces directly to the
grounded EP underneath the package. Solder the EP on
the bottom of the device package evenly to the board
ground plane to provide a heat transfer path along with
signal grounding.
MAX SLOPE
20101_
PA SLOPE
_
−
=
PA SLOPE
_
+
MAX2010
500MHz to 1100MHz Adjustable
RF Predistorter
16 ______________________________________________________________________________________
Power-Supply Bypassing
Bypass each VCCpin with a 0.01µF capacitor.
Exposed Pad RF
The exposed paddle (EP) of the MAX2010’s 28-pin thin
QFN-EP package provides a low inductance path to
ground. It is important that the EP be soldered to the
ground plane on the PC board, either directly or
through an array of plated via holes.
Figure 4. AM-PM Response Tuning Circuit
Table 1. Suggested Components of
Typical Application Circuit
V
PF_S1
= 1.5V
V
V
V
PBIN
PDCS1
PDCS2
PREAMPLIFIER
P
IN
= 0.8V
= 0V
= 5V
= 14dBm
9
INP
11
PFS1
12
PFS2
19
PBRAW
18
PBEXP
= 7dBm
P
OUT
63
OUTP ING
PHASE
CONTROL
POWER
AMPLIFIER
MAX2010
GAIN
CONTROL
141317 25
27
OUTG
23GBP
24GFS
GCSPDCS2PDCS1PBIN
DESIGNATION VALUE TYPE
C1, C2, C3, C10 100pF ±5% 0402 ceramic capacitors
C4, C5 0.01µF ±10% 0603 ceramic capacitors
C6, C8 15pF ±5% 0402 ceramic capacitors
C11, C12 2.2pF ±0.1pF 0402 ceramic capacitors
L1, L2 5.6nH ±0.3nH 0402 ceramic inductors
R1, R2 1kΩ ±5% 0402 resistors
VR1, VR2
Skyworks
SMV1232-079
Hyperabrupt varactor
diodes
MAX2010
500MHz to 1100MHz Adjustable
RF Predistorter
______________________________________________________________________________________ 17
Figure 5. MAX2010 Phase and Gain Optimization Circuit
V
PF_S1
= 1.5V
V
V
V
PBIN
PDCS1
PDCS2
PREAMPLIFIER
P
IN
= 0.8V
= 0V
= 5V
= 14dBm
PREAMPLIFIER
GAIN = 7dB
63
OUTP ING
MAX2010
9
INP
11
PFS1
12
PFS2
19
PBRAW
18
PBEXP
PHASE
CONTROL
GAIN
CONTROL
GCSPDCS2PDCS1PBIN
141317 25
OUTG
27
23GBP
24GFS
POWER
AMPLIFIER
V
= 1V
GBP
= 1.5V
V
GFS
V
= 1V
GCS
MAX2010
500MHz to 1100MHz Adjustable
RF Predistorter
18 ______________________________________________________________________________________
Typical Application Circuit
28 27 26 25 24 23 22
7
6
5
4
3
2
1
15
16
17
18
19
20
21
8 9 10 11 12 13 14
MAX2010
GAIN
CONTROL
PHASE
CONTROL
GND*
GND*
ING
GND*
GND*
OUTP
GND*
V
CCG
GND*
PBRAW
PBEXP
PBIN
GND*
V
CCP
GND*
INP
GND*
PFS1
PFS2
PDCS1
PDCS2
GND*
OUTG
GND*
GCS
GFS
GBP
GND*
C12
C8
C10
PREAMPLIFER
OPTIONAL MATCH COMPENSATION
C5
C4
CONTROL
UNIT
C11
VR2
R1
R2
C3
C2
VR1
C1
L1
L2
PREAMPLIFER
C6
POWER
AMPLIFER
*INTERNALLY CONNECTED TO EXPOSED GROUND PADDLE.
Chip Information
TRANSISTOR COUNT:
Bipolar: 160
CMOS: 240
PROCESS: BiCMOS
MAX2010
500MHz to 1100MHz Adjustable
RF Predistorter
Maxim cannot assume responsibility for use of any circuitry other than circuitry entirely embodied in a Maxim product. No circuit patent licenses are
implied. Maxim reserves the right to change the circuitry and specifications without notice at any time.
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© 2003 Maxim Integrated Products Printed USA is a registered trademark of Maxim Integrated Products.
Package Information
(The package drawing(s) in this data sheet may not reflect the most current specifications. For the latest package outline information
go to www.maxim-ic.com/packages
.)
PIN # 1
I.D.
D
C
0.15 C A
D/2
0.15
C B
E/2
E
0.10
C
A
0.08 C
A3
A1
(NE-1) X e
DETAIL A
L
D2
C
k
e
(ND-1) X e
L
e e
PROPRIETARY INFORMATION
TITLE:
PACKAGE OUTLINE
16, 20, 28, 32L, QFN THIN, 5x5x0.8 mm
APPROVAL
L
D2/2
b
0.10 M
E2/2
L
DOCUMENT CONTROL NO.
21-0140
C A B
PIN # 1 I.D.
0.35x45
C
E2
L
k
QFN THIN.EPS
CC
L
L
REV.
1
C
2
COMMON DIMENSIONS
NOTES:
1. DIMENSIONING & TOLERANCING CONFORM TO ASME Y14.5M-1994.
2. ALL DIMENSIONS ARE IN MILLIMETERS. ANGLES ARE IN DEGREES.
3. N IS THE TOTAL NUMBER OF TERMINALS.
4. THE TERMINAL #1 IDENTIFIER AND TERMINAL NUMBERING CONVENTION SHALL CONFORM TO JESD 95-1
SPP-012. DETAILS OF TERMINAL #1 IDENTIFIER ARE OPTIONAL, BUT MUST BE LOCATED WITHIN THE
ZONE INDICATED. THE TERMINAL #1 IDENTIFIER MAY BE EITHER A MOLD OR MARKED FEATURE.
5. DIMENSION b APPLIES TO METALLIZED TERMINAL AND IS MEASURED BETWEEN 0.25 mm AND 0.30 mm
FROM TERMINAL TIP.
6. ND AND NE REFER TO THE NUMBER OF TERMINALS ON EACH D AND E SIDE RESPECTIVELY.
7. DEPOPULATION IS POSSIBLE IN A SYMMETRICAL FASHION.
8. COPLANARITY APPLIES TO THE EXPOSED HEAT SINK SLUG AS WELL AS THE TERMINALS.
9. DRAWING CONFORMS TO JEDEC MO220.
10. WARPAGE SHALL NOT EXCEED 0.10 mm.
EXPOSED PAD VARIATIONS
PROPRIETARY INFORMATION
TITLE:
PACKAGE OUTLINE
16, 20, 28, 32L, QFN THIN, 5x5x0.8 mm
21-0140
REV.DOCUMENT CONTROL NO.APPROVAL
2
C
2
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