Available in the 8-Pin SO and 5-Pin Low Profile
(1mm) ThinSOTTM Packages
■
Operating Temperature Range: –40°C to 85°C
LT1800
80MHz, 25V/µs Low Power
Rail-to-Rail Input and Output
Precision Op Amp
U
DESCRIPTIO
The LT®1800 is a low power, high speed rail-to-rail input
and output operational amplifier with excellent DC performance. The LT1800 features reduced supply current, lower
input offset voltage, lower input bias current and higher
DC gain than other devices with comparable bandwidth.
The LT1800 has an input range that includes both supply
rails and an output that swings within 20mV of either supply rail to maximize the signal dynamic range in low supply
applications.
The LT1800 maintains its performance for supplies from
2.3V to 12.6V and is specified at 3V, 5V and ±5V supplies.
The inputs can be driven beyond the supplies without
damage or phase reversal of the output.
U
APPLICATIO S
■
Low Voltage, High Frequency Signal Processing
■
Driving A/D Converters
■
Rail-to-Rail Buffer Amplifiers
■
Active Filters
■
Video Line Driver
U
TYPICAL APPLICATIO
Single Supply 1A Laser Driver Amplifier
5V
DO NOT FLOAT
V
IN
+
–
LT1800
R3
10
C1
39pF
330
Q1
Ω
ZETEX
FMMT619
IR LASER
INFINEON
R1
Ω
1
1800 TA01
SFH495
R2
Ω
The LT1800 is available in the 8-pin SO package with the
standard op amp pinout and in the 5-pin SOT-23 package.
For dual and quad versions of the LT1800, see the LT1801/
LT1802 data sheet. The LT1800 can be used as a plug-in
replacement for many op amps to improve input/output
range and performance.
, LTC and LT are registered trademarks of Linear Technology Corporation.
ThinSOT is a trademark of Linear Technology Corporation.
Laser Driver Amplifier
500mA Pulse Response
100mA/DIV
50ns/DIV
1800 TA02
sn1800 1800fs
1
LT1800
V
OUT
1
V
S
–
2
TOP VIEW
S5 PACKAGE
5-LEAD PLASTIC SOT-23
+IN 3
5 V
S
+
4 –IN
+
–
WWWU
ABSOLUTE AXI U RATI GS
Total Supply Voltage (V
–
S
Input Current (Note 2) ........................................±10mA
Large-Signal Voltage GainVO = –4V to 4V, RL = 1k2570V/mV
Input Common Mode RangeV
Output Voltage Swing Low (Note 7)No Load1560mV
Output Voltage Swing High (Note 7)No Load1770mV
Short-Circuit Current3050mA
Supply Current per Amplifier1.82.75mA
Settling Time0.01%, V
= 0V, unless otherwise noted.
OUT
V
= –2V to 2V, RL = 100Ω2.57V/mV
O
–
to 3.5V85109dB
S
+
= 2.5V to 10V, V
S
I
= 5mA85170mV
SINK
I
= 20mA225450mV
SINK
I
= 5mA130260mV
SOURCE
I
= 20mA450900mV
SOURCE
P-P
= 5V, AV = 1V, RL = 1k300ns
STEP
–
–
= 0V8097dB
S
S
+
V
S
0.9MHz
, fC = 500kHz–75dBc
P-P
V
The ● denotes the specifications which apply over the temperature range of 0°C ≤ TA ≤ 70°C. VS = ±5V, VCM = 0V, V
= 0V, unless
OUT
otherwise noted.
SYMBOL PARAMETERCONDITIONSMINTYPMAXUNITS
V
OS
Input Offset VoltageVCM = V
VCM = V
V
VCM = V
∆V
Input Offset ShiftVCM = V
OS
VOS TCInput Offset Voltage Drift (Note 8)●1.55µV/°C
I
B
Input Bias CurrentVCM = V
VCM = V
I
OS
Input Offset CurrentVCM = V
V
A
VOL
Large-Signal Voltage GainVO = –4V to 4V, RL = 1k●2055V/mV
VO = –2V to 2V, RL = 100Ω●25V/mV
CMRRCommon Mode Rejection RatioVCM = V
Input Common Mode Range●V
PSRRPower Supply Rejection RatioV
V
OL
Output Voltage Swing Low (Note 7)No Load●1770mV
I
I
V
OH
Output Voltage Swing High (Note 7)No Load●2590mV
I
I
–
S
–
(SOT-23)●4501500µV
S
+
= V
CM
S
+
(SOT-23)●15 mV
S
–
+
to V
S
S
S
S
= V
CM
S
S
+
= 2.5V to 10V, V
S
= 5mA●105210mV
SINK
= 20mA●250575mV
SINK
= 5mA●150310mV
SOURCE
= 20mA●6001100mV
SOURCE
– 1.5V●45675µV
S
–
+ 1V●30400nA
+
– 0.2V●4501750nA
–
+ 1V●25300nA
+
– 0.2V●25300nA
–
to 3.5V●82105dB
–
= 0V●7491dB
S
●200800µV
●0.754mV
–
S
+
V
S
sn1800 1800fs
V
5
LT1800
ELECTRICAL CHARACTERISTICS
of 0°C ≤ TA ≤ 70°C. VS = ±5V, VCM = 0V, V
= 0V, unless otherwise noted.
OUT
The ● denotes the specifications which apply over the temperature range
SYMBOL PARAMETERCONDITIONSMINTYPMAXUNITS
I
SC
I
S
Short-Circuit Current●2545mA
Supply Current per Amplifier●2.43.5mA
GBWGain Bandwidth ProductFrequency = 2MHz●70MHz
SRSlew RateAV = –1, RL = 1k, VO = ±4V, Measured at VO = ±2V●20V/µs
The ● denotes the specifications which apply over the temperature range of –40°C ≤ TA ≤ 85°C. VS = ±5V, VCM = 0V, V
OUT
= 0V,
unless otherwise noted.
SYMBOL PARAMETERCONDITIONSMINTYPMAXUNITS
V
OS
Input Offset VoltageVCM = V
V
VCM = V
V
∆V
Input Offset ShiftVCM = V
OS
VOS TCInput Offset Voltage Drift (Note 8)●1.55µV/°C
I
B
Input Bias CurrentVCM = V
V
I
OS
Input Offset CurrentVCM = V
VCM = V
A
VOL
Large-Signal Voltage GainVO = –4V to 4V, RL = 1k●1655V/mV
V
CMRRCommon Mode Rejection RatioVCM = V
Input Common Mode Range●V
PSRRPower Supply Rejection RatioV
V
OL
Output Voltage Swing Low (Note 7)No Load●1580mV
I
I
V
OH
Output Voltage Swing High (Note 7)No Load●25100mV
I
I
I
SC
I
S
Short-Circuit Current●12.530mA
Supply Current per Amplifier●2.64mA
GBWGain Bandwidth ProductFrequency = 2MHz●65MHz
SRSlew RateAV = –1, RL = 1k, VO = ±4V, Measured at VO = ±2V●15V/µs
–
S
–
= V
CM
CM
CM
O
S
SINK
SINK
SOURCE
SOURCE
(SOT-23)●5002250µV
S
+
S
+
= V
(SOT-23)●15.5mV
S
–
+
to V
– 1.5V●50750µV
S
–
+ 1V●50450nA
+
– 0.2V●4502000nA
–
+ 1V●25350nA
+
– 0.2V●25350nA
= V
S
S
S
S
S
= –1V to 1V, RL = 100Ω●25V/mV
–
to 3.5V●81104dB
S
+
= 2.5V to 10V, V
–
= 0V●7390dB
S
= 5mA●105220mV
= 10mA●170400mV
= 5mA●150350mV
= 10mA●300700mV
●350900µV
●0.754.5mV
–
S
+
V
S
V
Note 1: Absolute Maximum Ratings are those values beyond which the life
of the device may be impaired.
Note 2: The inputs are protected by back-to-back diodes and by ESD
diodes to the supply rails. If the differential input voltage exceeds 1.4V or
either input goes outside the rails, the input current should be limited to
less than 10mA.
Note 3: A heat sink may be required to keep the junction temperature
below the absolute maximum rating when the output is shorted
indefinitely.
Note 4: The LT1800C/LT1800I are guaranteed functional over the
temperature range of –40°C to 85°C.
6
Note 5: The LT1800C is guaranteed to meet specified performance from
0°C to 70°C. The LT1800C is designed, characterized and expected to
meet specified performance from –40°C to 85°C but is not tested or QA
sampled at these temperatures. The LT1800I is guaranteed to meet
specified performance from –40°C to 85°C.Note 6: Minimum supply voltage is guaranteed by power supply rejection
ratio test.
Note 7: Output voltage swings are measured between the output and
power supply rails.
Note 8: This parameter is not 100% tested.
sn1800 1800fs
UW
TYPICAL PERFOR A CE CHARACTERISTICS
LT1800
VOS Distribution, VCM = 0V
(SO-8, PNP Stage)
45
VS = 5V, 0V
V
= 0V
40
CM
35
30
25
20
15
PERCENT OF UNITS (%)
10
5
0
–150–50250
–250
INPUT OFFSET VOLTAGE (µV)
VOS Distribution, VCM = 5V
(SOT-23, NPN Stage)
35
VS = 5V, 0V
= 5V
V
CM
30
25
20
15
10
PERCENT OF UNITS (%)
5
0
–2500
–5002500–15005001500
INPUT OFFSET VOLTAGE (µV)
50150
1800 G01
1800 G39
VOS Distribution, VCM = 5V
(SO-8, NPN Stage)
45
VS = 5V, 0V
V
= 5V
40
CM
35
30
25
20
15
PERCENT OF UNITS (%)
10
5
0
–1200–4002000
–2000
INPUT OFFSET VOLTAGE (µV)
4001200
Supply Current vs Supply Voltage
4
3
2
SUPPLY CURRENT (mA)
1
0
3579102468 11
10
TOTAL SUPPLY VOLTAGE (V)
TA = 125°C
TA = 25°C
TA = –55°C
1800 G02
1800 G03
VOS Distribution, VCM = 0V
(SOT-23, PNP Stage)
40
VS = 5V, 0V
= 0V
V
CM
35
30
25
20
15
PERCENT OF UNITS (%)
10
5
0
–750–2502501250
–1250
INPUT OFFSET VOLTAGE (µV)
750
1800 G38
Offset Voltage
vs Input Common Mode Voltage
500
400
300
200
100
0
–100
–200
OFFSET VOLTAGE (µV)
–300
–400
–500
12
0
TA = –55°C
TA = 25°C
TA = 125°C
1
2
INPUT COMMON MODE VOLTAGE (V)
VS = 5V, 0V
TYPICAL PART
3
4
5
1800 G04
Input Bias Current
vs Common Mode Voltage
1.0
VS = 5V, 0V
= 25°C
T
A
= 125°C
T
A
= –55°C
T
A
0
0
–1
INPUT COMMON MODE VOLTAGE (V)
1
23
INPUT BIAS CURRENT (µA)
0.8
0.6
0.4
0.2
–0.2
–0.4
–0.6
–0.8
–1.0
Input Bias Current
vs Temperature
0.8
0.7
NPN ACTIVE
0.6
V
= 5V, 0V
S
V
= 5V
0.5
0.4
0.3
INPUT BIAS (µA)
0.2
0.1
0
4
5
6
1800 G05
–0.1
CM
PNP ACTIVE
= 5V, 0V
V
S
V
= 1V
CM
–40 –20020
–60
TEMPERATURE (°C)
406080
1800 G06
Output Saturation Voltage
vs Load Current (Output Low)
10
VS = 5V, 0V
1
0.1
TA = 125°C
0.01
TA = –55°C
OUTPUT SATURATION VOLTAGE (V)
0.001
0.01 0.1
TA = 25°C
110100
LOAD CURRENT (mA)
1800 G07
sn1800 1800fs
7
LT1800
POWER SUPPLY VOLTAGE (±V)
1.5
–70
OUTPUT SHORT-CIRCUIT CURRENT (mA)
–50
–30
–10
70
30
2
3
3.55
50
10
–60
–40
–20
60
20
40
0
2.5
4
4.5
TA = 125°C
TA = 125°C
TA = –55°CSINKING
VS = 5V, 0V
SOURCINGTA = –55°C
TA = 25°C
TA = 25°C
1800 G10
OUTPUT VOLTAGE (V)
–5
CHANGE IN OFFSET VOLTAGE (µV)
400
1200
2000
3
1800 G13
–400
–1200
0
800
1600
–800
–1600
–2000
–3–4
–1–2
124
0
5
VS = ±5V
R
L
TO GND
RL = 1k
RL = 100Ω
FREQUENCY (kHz)
20
NOISE VOLTAGE (nV/√Hz)
40
60
10
30
50
0.01110100
1800 G16
0
0.1
VS = 5V, 0V
NPN ACTIVE
V
CM
= 4.25V
PNP ACTIVE
V
CM
= 2.5V
UW
TYPICAL PERFOR A CE CHARACTERISTICS
Output Saturation Voltage
vs Load Current (Output High)
10
VS = 5V, 0V
1
0.1
TA = 125°C
0.01
TA = –55°C
OUTPUT SATURATION VOLTAGE (V)
0.001
0.01 0.1
TA = 25°C
110100
LOAD CURRENT (mA)
Open-Loop Gain
2000
1600
1200
800
400
0
–400
–800
–1200
CHANGE IN OFFSET VOLTAGE (µV)
–1600
–2000
0
0.5
RL = 100Ω
1.52
1
OUTPUT VOLTAGE (V)
RL = 1k
1800 G08
VS = 3V, 0V
TO GND
R
L
2.5
1800 G11
Minimum Supply Voltage
0.6
0.4
0.2
0
–0.2
–0.4
CHANGE IN OFFSET VOLTAGE (mV)
–0.6
1.52.5
0
Open-Loop GainOpen-Loop Gain
2000
1600
1200
800
400
0
–400
–800
–1200
CHANGE IN OFFSET VOLTAGE (µV)
–1600
–2000
3
0
TA = –55°C
TA = 25°C
TA = 125°C
2
TOTAL SUPPLY VOLTAGE (V)
10.5
OUTPUT VOLTAGE (V)
3.55.5
3
RL = 100Ω
21.5
2.5
4.5
4
VS = 5V, 0V
R
RL = 1k
3 3.54.5
TO GND
L
4
Output Short-Circuit Current
vs Power Supply Voltage
5
1800 G09
5
1800 G12
Offset Voltage vs Output Current
2.0
VS = ±5V
1.5
1.0
0.5
0
–0.5
TA = 25°C
–1.0
CHANGE IN OFFSET VOLTAGE (mV)
–1.5
–2.0
–45
–60
8
TA = –55°C
TA = 125°C
–30
–15
OUTPUT CURRENT (mA)
0
15
Warm-Up Drift vs Time
(LT1800S8)
120
110
100
90
80
70
OFFSET VOLTAGE (µV)
60
50
45
1800 G14
60
30
40
VS = ±5V
VS = ±2.5V
VS = ±1.5V
204080
0
TIME AFTER POWER-UP (SECONDS)
60
TYPICAL PART
100 120 140
1800 G15
Input Noise Voltage vs Frequency
sn1800 1800fs
UW
FREQUENCY (MHz)
0.01
10
OPEN-LOOP GAIN (dB)
PHASE (DEG)
20
30
40
50
0.1110100 300
1800 G22
0–40
–10
–20
–30
60
70
–20
0
20
40
60
–60
–80
–100
80
100
VS = ±2.5V
V
S
= ±5V
PHASE
GAIN
FREQUENCY (MHz)
0.1
0.001
OUTPUT IMPEDANCE (Ω)
0.1
600
100
110100500
1800 G25
0.01
1
10
VS = ±2.5V
AV = 10
AV = 1
AV = 2
TYPICAL PERFOR A CE CHARACTERISTICS
LT1800
0.1Hz to 10Hz Output Voltage
Input Current Noise vs Frequency
3.0
2.5
2.0
= 4.25V
0.1
PNP ACTIVE
V
= 2.5V
CM
FREQUENCY (kHz)
1.5
1.0
NOISE CURRENT (pA/√Hz)
NPN ACTIVE
0.5
V
CM
0
0.01110100
VS = 5V, 0V
1800 G17
Noise
2000
VS = 5V, 0V
1000
0
–1000
OUTPUT NOISE VOLTAGE (nV)
–2000
246 1071359
0
TIME (SECONDS)
Gain Bandwidth and Phase
Margin vs TemperatureSlew Rate vs Temperature
100
90
80
70
60
50
GAIN BANDWIDTH (MHz)
–355
–55
GBW PRODUCT
PHASE MARGIN
V
PHASE MARGIN
V
S
–15
TEMPERATURE (°C)
GBW PRODUCT
= ±2.5V
V
S
= ±5V
V
S
= ±2.5V
S
= ±5V
45125
65
25
60
50
40
30
20
105
1800 G20
10
85
35
AV = –1
= RG = 1k
R
F
= 1k
R
L
30
PHASE MARGIN (DEG)
25
20
SLEW RATE (V/µs)
15
10
–355
–55
–15
25
TEMPERATURE (°C)
VS = ±2.5V
V
8
1800 G18
= ±5V
S
85
45125
105
65
1800 G21
Gain Bandwidth and Phase
Margin vs Supply Voltage
100
90
GAIN BANDWIDTH
80
70
6060
GAIN BANDWIDTH (MHz)
0
PRODUCT
PHASE MARGIN
246 1071359
TOTAL SUPPLY VOLTAGE (V)
TA = 25°C
8
1800 G19
Gain and Phase vs Frequency
PHASE MARGIN (DEG)
50
40
30
20
Gain vs Frequency (AV = 1)
12
RL = 1k
= 10pF
C
L
9
= 1
A
V
6
3
0
GAIN (dB)
–3
–6
–9
–12
0.110100 300
1
VS = ±5V
FREQUENCY (MHz)
VS = ±2.5V
1800 G23
Gain vs Frequency (AV = 2)
18
RL = 1k
= 10pF
C
L
15
= 2
A
V
12
9
6
GAIN (dB)
3
0
–3
–6
0.110100 300
Output Impedance vs Frequency
VS = ±2.5V
VS = ±5V
1
FREQUENCY (MHz)
1800 G24
sn1800 1800fs
9
LT1800
UW
TYPICAL PERFOR A CE CHARACTERISTICS
Common Mode Rejection Ratio
vs Frequency
120
VS = 5V, 0V
100
80
60
40
20
COMMON MODE REJECTION RATIO (dB)
0
0.01110100
0.1
FREQUENCY (MHz)
Series Output Resistor
vs Capacitive Load
60
VS = 5V, 0V
55
= 2
A
V
50
45
40
35
30
25
OVERSHOOT (%)
20
15
10
5
ROS = RL = 50Ω
0
10
100100010000
CAPACITIVE LOAD (pF)
ROS = 10Ω
ROS = 20Ω
1800 G26
1800 G29
Power Supply Rejection Ratio
vs Frequency
90
80
70
NEGATIVE
60
SUPPLY
50
40
30
20
10
0
POWER SUPPLY REJECTION RATIO (dB)
–10
0.010.1110100
0.001
FREQUENCY (MHz)
POSITIVE
SUPPLY
Distortion vs Frequency
–40
VS = 5V, 0V
= 1
A
V
–50
–60
–70
–80
DISTORTION (dBc)
–90
–100
–110
0.01
V
OUT
= 2V
P-P
RL = 150Ω, 2ND
RL = 1k, 3RD
0.1110
FREQUENCY (MHz)
VS = 5V, 0V
= 25°C
T
A
1800 G27
RL = 1k, 2ND
RL = 150Ω, 3RD
1800 G30
Series Output Resistor
vs Capacitive Load
60
VS = 5V, 0V
55
= 1
A
V
50
45
40
35
30
25
OVERSHOOT (%)
20
15
10
5
0
10
ROS = 20Ω
ROS = RL = 50Ω
100100010000
CAPACITIVE LOAD (pF)
Distortion vs Frequency
–40
VS = 5V, 0V
= 2
A
V
–50
–60
–70
–80
DISTORTION (dBc)
–90
–100
–110
V
0.01
= 2V
OUT
P-P
RL = 150Ω, 2ND
RL = 1k, 3RD
0.1110
FREQUENCY (MHz)
ROS = 10Ω
1800 G28
RL = 1k,
2ND
RL = 150Ω,
3RD
1800 G31
Maximum Undistorted Output
Signal vs Frequency
4.6
4.5
)
P-P
4.4
4.3
4.2
4.1
OUTPUT VOLTAGE SWING (V
4.0
VS = 5V, 0V
= 1k
R
L
3.9
1k100k1M10M
10k
FREQUENCY (Hz)
AV = 2
AV = –1
10
1800 G32
5V Large-Signal Response
1V/DIV
0V
= 5V, 0V100ns/DIV1800 G33
V
S
AV = 1
R
= 1k
L
50mV/DIV
0V
5V Small-Signal Response
= 5V, 0V50ns/DIV1800 G34
V
S
AV = 1
R
= 1k
L
sn1800 1800fs
UW
TYPICAL PERFOR A CE CHARACTERISTICS
LT1800
±5V Large-Signal Response
2V/DIV
0V
= ±5V200ns/DIV1800 G35
V
S
AV = 1
R
= 1k
L
50mV/DIV
±5V Small-Signal Response
0V
= ±5V50ns/DIV1800 G36
V
S
AV = 1
= 1k
R
L
WUUU
APPLICATIO S I FOR ATIO
Circuit Description
The LT1800 has an input and output signal range that
covers from the negative power supply to the positive
power supply. Figure 1 depicts a simplified schematic of
the amplifier. The input stage is comprised of two differential amplifiers, a PNP stage Q1/Q2 and an NPN stage Q3/
Q4 that are active over the different ranges of common
mode input voltage. The PNP differential pair is active
between the negative supply to approximately 1.2V below
Output Overdriven Recovery
V
IN
1V/DIV
0V
V
OUT
2V/DIV
0V
V
= 5V, 0V100ns/DIV1800 G37
S
AV = 2
= 1k
R
L
the positive supply. As the input voltage moves closer
toward the positive supply, the transistor Q5 will steer the
tail current I1 to the current mirror Q6/Q7, activating the
NPN differential pair and the PNP pair becomes inactive
for the rest of the input common mode range up to the
positive supply. Also at the input stage, devices Q17 to
Q19 act to cancel the bias current of the PNP input pair.
When Q1-Q2 are active, the current in Q16 is controlled to
be the same as the current in Q1-Q2, thus the base current
+
V
R3R4R5
–
+
V
V
Q11
Q12
Q13Q15
C2
+
I
3
C
C
–
V
BUFFER
AND
OUTPUT BIAS
Q9
Q8
C1
R2R1
OUT
Q14
1800 F01
BIAS
+
I
1
Q2
Q1
D3
D4
Q10
+
I
2
+IN
–IN
Q16
Q18Q17
–
V
ESDD2ESDD1
D6D7D8
D5
ESDD3ESDD4
–
V+V
Q19
D1
D2
Q4
Q7
Q5V
Q3
Q6
Figure 1. LT1800 Simplified Schematic Diagram
sn1800 1800fs
11
LT1800
WUUU
APPLICATIO S I FOR ATIO
of Q16 is nominally equal to the base current of the input
devices. The base current of Q16 is then mirrored by
devices Q17-Q19 to cancel the base current of the input
devices Q1-Q2.
A pair of complementary common emitter stages Q14/Q15
that enable the output to swing from rail to rail constructs
the output stage. The capacitors C2 and C3 form the local
feedback loops that lower the output impedance at high
frequency. These devices are fabricated on Linear
Technology’s proprietary high-speed complementary bipolar process.
Power Dissipation
The LT1800 amplifier is offered in a small package, SOT-23,
which has a thermal resistance of 250°C/W, θJA. So there
is a need to ensure that the die’s junction temperature
should not exceed 150°C. Junction temperature TJ is
calculated from the ambient temperature TA, power dissipation PD and thermal resistance θJA:
TJ = TA + (PD • θJA)
The power dissipation in the IC is the function of the supply
voltage, output voltage and the load resistance. For a given
supply voltage, the worst-case power dissipation P
occurs at the maximum supply current and the output
voltage is at half of either supply voltage (or the maximum
swing is less than 1/2 supply voltage). P
P
DMAX
= (VS • I
) + (VS/2)2/R
SMAX
DMAX
L
DMAX
is given by:
the NPN input stage is activated for the remaining input
range up to the positive supply rail during which the PNP
stage remains inactive. The offset voltage is typically less
than 75µV in the range that the PNP input stage is active.
Input Bias Current
The LT1800 employs a patent-pending technique to trim
the input bias current to less than 250nA for the input
common mode voltage of 0.2V above negative supply rail
to 1.2V of the positive rail. The low input offset voltage
and low input bias current of the LT1800 provide the
precision performance especially for high source impedance applications.
Output
The LT1800 can deliver a large output current, so the
short-circuit current limit is set around 50mA to prevent
damage to the device. Attention must be paid to keep the
junction temperature of the IC below the absolute maximum rating of 150°C (refer to the Power Dissipation
section) when the output is continuously short circuited.
The output of the amplifier has reverse-biased diodes
connected to each supply. If the output is forced beyond
either supply, unlimited current will flow through these
diodes. If the current is transient and limited to several
hundred mA, and the total supply voltage is less than
12.6V, the absolute maximum rating, no damage will
occur to the device.
Example: An LT1800 in a SOT-23 package operating on
±5V supplies and driving a 50Ω load, the worst-case
power dissipation is given by:
P
The maximum ambient temperature that the part is allowed to operate is:
TA = TJ – (P
= 150°C – (0.165W • 250°C/W) = 108°C
Input Offset Voltage
The offset voltage will change depending upon which input
stage is active. The PNP input stage is active from the
negative supply rail to 1.2V of the positive supply rail, then
= (10 • 4mA) + (2.5)2/50 = 0.04 + 0.125 = 0.165W
DMAX
• 250°C/W)
DMAX
12
Overdrive Protection
When the input voltage exceeds the power supplies, two
pairs of crossing diodes D1 to D4 will prevent the output
from reversing polarity. If the input voltage exceeds either
power supply by 700mV, diode D1/D2 or D3/D4 will turn
on to keep the output at the proper polarity. For the phase
reversal protection to perform properly, the input current
must be limited to less than 10mA. If the amplifier is
severely overdriven, an external resistor should be used to
limit the overdrive current.
The LT1800’s input stages are also protected against a
large differential input voltage of 1.4V or higher by a pair
of back-back diodes D5/D8 to prevent the emitter-base
breakdown of the input transistors. The current in these
sn1800 1800fs
WUUU
APPLICATIO S I FOR ATIO
LT1800
diodes should be limited to less than 10mA when they are
active. The worst-case differential input voltage usually
occurs when the input is driven while the output is shorted
to ground in a unity gain configuration. In addition, the
amplifier is protected against ESD strikes up to 3kV on all
pins by a pair of protection diodes on each pin that are
connected to the power supplies as shown in Figure1.
Capacitive Load
The LT1800 is optimized for high bandwidth, low power
and precision applications. It can drive a capacitive load of
about 75pF in a unity gain configuration, and more for
higher gain. When driving a larger capacitive load, a
resistor of 10Ω to 50Ω should be connected between the
output and the capacitive load to avoid ringing or oscillation. The feedback should still be taken from the output so
that the resistor will isolate the capacitive load to ensure
WUUU
APPLICATIO S I FOR ATIO
stability. Graphs on capacitive loads indicate the transient
response of the amplifier when driving capacitive load with
a specified series resistor.
Feedback Components
When feedback resistors are used to set up gain, care must
be taken to ensure that the pole formed by the feedback
resistors and the total capacitance at the inverting input
does not degrade stability. For instance, the LT1800 in a
noninverting gain of 2, set up with two 5k resistors and a
capacitance of 5pF (part plus PC board) will probably ring
in transient response. The pole is formed at 12.7MHz that
will reduce phase margin by 32 degrees when the crossover frequency of the amplifier is around 20MHz. A capacitor of 5pF or higher connected across the feedback resistor will eliminate any ringing or oscillation.
Single Supply 1A Laser Driver Amplifier
The circuit in the front page of this data sheet shows the
LT1800 used in a 1A laser driver application. One of the
reasons the LT1800 is well suited to this control task is that
its 2.3V operation ensures that it will be awake during
power-up and operated before the circuit can otherwise
cause significant current to flow in the 2.1V threshold laser
diode. Driving the noninverting input of the LT1800 to a
voltage VIN will control the turning on of the high current
NPN transistor, FMMT619 and the laser diode. A current
equal to VIN/R1 flows through the laser diode. The LT1800
low offset voltage and low input bias current allows it to
control the current that flows through the laser diode
precisely. The overall circuit is a 1A per Volt V-to-I converter. Frequency compensation components R2 and C1
are selected for fast but zero-overshoot time domain
response to avoid overcurrent conditions in the laser. The
time domain response of this circuit, measured at R1 and
given a 500mV 230ns input pulse, is also shown in the
graphic on the front page. While the circuit is capable of 1A
operation, the laser diode and the transistor are thermally
limited due to power dissipation, so they must be operated
at low duty cycles.
Fast 1A Current Sense Amplifier
A simple, fast current sense amplifier in Figure 2 is suitable
for quickly responding to out-of-range currents. The circuit amplifies the voltage across the 0.1Ω sense resistor
by a gain of 20, resulting in a conversion gain of 2V/A. The
– 3dB bandwidth of the circuit is 4MHz, and the uncertainty
due to VOS and IB is less than 4mA. The minimum output
voltage is 60mV, corresponding to 30mA. The large-signal
response of the circuit is shown in Figure 3.
I
L
0A TO 1A
52.3
Ω
0.1
Ω
52.3
Ω
V
= 2 • I
OUT
= 4MHz
L
f
–3dB
UNCERTAINTY DUE TO V
Figure 2. Fast 1A Current Sense
+
–
3V
LT1800
OS, IB
1800 F02
< 4mA
V
OUT
0V TO 2V
1k
sn1800 1800fs
13
LT1800
U
TYPICAL APPLICATIO S
500mV/DIV
0V
= 3V50ns/DIV1800 F03
V
S
Figure 3. Current Sense Amplifier Large-Signal Response
Single 3V Supply, 1MHz, 4th Order Butterworth Filter
The circuit shown in Figure 4 makes use of the low voltage
operation and the wide bandwidth of the LT1800 to create
a DC accurate 1MHz 4th order lowpass filter powered from
a 3V supply. The amplifiers are configured in the inverting
mode for the lowest distortion and the output can swing
rail-to-rail for maximum dynamic range. Figure 5 displays
the frequency response of the filter. Stopband attenuation
is greater than 100dB at 50MHz. With a 2.25V
, 250kHz
P-P
input signal, the filter has harmonic distortion products of
less than –85dBc. Worst case output offset voltage is less
than 6mV.
V
VS/2
909
909
Ω
IN
2.67k
220pF
47pF
Ω
1.1k
1.1k
2.21k
470pF
–
LT1800
+
22pF
–
+
3V
LT1800
1800 F04
V
OUT
Figure 4. 3V, 1MHz, 4th Order Butterworth Filter
0
–20
–40
–60
GAIN (dB)
–80
–100
–120
1k100k1M10M100M
10k
FREQUENCY (Hz)
1800 F05
14
Figure 5. Frequency Response of Filter
sn1800 1800fs
PACKAGE DESCRIPTIO
LT1800
U
S5 Package
5-Lead Plastic TSOT-23
(Reference LTC DWG # 05-08-1635)
0.62
MAX
3.85 MAX
0.20 BSC
DATUM ‘A’
NOTE:
1. DIMENSIONS ARE IN MILLIMETERS
2. DRAWING NOT TO SCALE
3. DIMENSIONS ARE INCLUSIVE OF PLATING
4. DIMENSIONS ARE EXCLUSIVE OF MOLD FLASH AND METAL BURR
5. MOLD FLASH SHALL NOT EXCEED 0.254mm
6. JEDEC PACKAGE REFERENCE IS MO-193
2.62 REF
RECOMMENDED SOLDER PAD LAYOUT
PER IPC CALCULATOR
0.30 – 0.50 REF
0.95
REF
1.22 REF
1.4 MIN
0.09 – 0.20
(NOTE 3)
2.80 BSC
1.50 – 1.75
(NOTE 4)
1.00 MAX
PIN ONE
0.95 BSC
0.80 – 0.90
2.90 BSC
(NOTE 4)
1.90 BSC
0.30 – 0.45 TYP
5 PLCS (NOTE 3)
0.01 – 0.10
S5 TSOT-23 0302
0.010 – 0.020
(0.254 – 0.508)
0.008 – 0.010
(0.203 – 0.254)
*
DIMENSION DOES NOT INCLUDE MOLD FLASH. MOLD FLASH
SHALL NOT EXCEED 0.006" (0.152mm) PER SIDE
**
DIMENSION DOES NOT INCLUDE INTERLEAD FLASH. INTERLEAD
FLASH SHALL NOT EXCEED 0.010" (0.254mm) PER SIDE
× 45°
0°– 8° TYP
0.016 – 0.050
(0.406 – 1.270)
Information furnished by Linear Technology Corporation is believed to be accurate and reliable.
However, no responsibility is assumed for its use. Linear Technology Corporation makes no representation that the interconnection of its circuits as described herein will not infringe on existing patent rights.
S8 Package
8-Lead Plastic Small Outline (Narrow .150 Inch)
(Reference LTC DWG # 05-08-1610)
0.053 – 0.069
(1.346 – 1.752)
0.014 – 0.019
(0.355 – 0.483)
TYP
0.004 – 0.010
(0.101 – 0.254)
0.050
(1.270)
BSC
0.228 – 0.244
(5.791 – 6.197)
0.189 – 0.197*
(4.801 – 5.004)
7
8
1
2
5
6
0.150 – 0.157**
(3.810 – 3.988)
SO8 1298
3
4
sn1800 1800fs
15
LT1800
TYPICAL APPLICATIO
U
Low Power High Voltage Amplifier
Certain materials used in optical applications have characteristics that change due to the presence and strength of
a DC electric field. The voltage applied across these
materials should be precisely controlled to maintain desired properties, sometimes as high as 100’s of volts. The
materials are not conductive and represent a capacitive
load.
The circuit of Figure 6 shows the LT1800 used in an
amplifier capable of a 250V output swing and providing
130V
5V
0.1µF
R2
2k
V
IN
R1
2k
C2
8pF
150V
+
R3
200k
LT1800
–
5V
C1
39pF
Q1
Q3
Figure 6. Low Power, High Voltage Amplifier
10k
10k
Q5
R4
2k
R5
2k
Q7
4.99k1k
Q2
5V
R6
2k
R7
2k
Q4
4.99k
–130V
Q6
V
OUT
MATERIAL UNDER
ELECTRIC FIELD
100pF
AV = V
±130V SUPPLY I
Q8
OUTPUT SWING = ±128.8V
OUTPUT OFFSET
1k
OUTPUT SHORT-CIRCUIT CURRENT ≅ 3mA
10% TO 90% RISE TIME ≅ 8µs, 200V OUTPUT STEP
SMALL-SIGNAL BANDWIDTH ≅ 150kHz
Q1, Q2, Q7, Q8: ON SEMI MPSA42
Q3, Q4, Q5, Q6: ON SEMI MPSA92
1800 F06
OUT/VIN
= –100
Q
≅ 20mV
= 130µA
precise DC output voltage. When no signal is present, the
op amp output sits at about mid-supply. Transistors Q1
and Q3 create bias voltages for Q2 and Q4, which are
forced into a low quiescent current by degeneration resistors R4 and R5. When a transient signal arrives at VIN, the
op amp output moves and causes the current in Q2 or Q4
to change depending on the signal polarity. The current,
limited by the clipping of the LT1800 output and the 3kΩ
of total emitter degeneration, is mirrored to the output
devices to drive the capacitive load. The LT1800 output
then returns to near mid-supply, providing the precise DC
output voltage to the load. The attention to limit the current
of the output devices minimizes power dissipation thus
allowing for dense layout, and inherits better reliability.
Figure 7 shows the time domain response of the amplifier
providing a 200V output swing into a 100pF load.
V
IN
2V/DIV
V
OUT
50V/DIV
10µs/DIV1800 F07
Figure 7. Large-Signal Time Domain
Response of the Amplifier
RELATED PARTS
PART NUMBERDESCRIPTIONCOMMENTS
LT1399Triple 300MHz Current Feedback Amplifier0.1dB Gain Flatness to 150MHz, Shutdown
LT1498/LT1499Dual/Quad 10MHz, 6Vµs Rail-to-Rail Input and Output C-Load
Op AmpsMax Supply Current 2.2mA per Amp
LT1630/LT1631Dual/Quad 30MHz, 10V/µs Rail-to-Rail Input and Output Op AmpsHigh DC Accuracy, 525µV V
LT1801/LT180280MHz, 25V/µs Low Power Rail-to-Rail Input/Output Precision Op Amps Dual/Quad Version of the LT1800
LT1806/LT1807Single/Dual 325MHz, 140V/µs Rail-to-Rail Input and Output Op AmpsHigh DC Accuracy, 550µV V
LT1809/LT1810Single/Dual 180MHz Rail-to-Rail Input/Output Op Amps350V/µs Slew Rate, Low Distortion –90dBc at 5MHz,
C-Load is a trademark of Linear Technology Corporation.
Linear Technolog y Corporation
16
1630 McCarthy Blvd., Milpitas, CA 95035-7417
(408) 432-1900 ● FAX: (408) 434-0507
●
www.linear.com
TM
High DC Accuracy, 475µV V
, 4µV/°C Max Drift,
OS(MAX)
, 70mA Output Current,
OS(MAX)
Max Supply Current 4.4mA per Amplifier
, Low Noise 3.5nV/√Hz,
OS(MAX)
Low Distortion –80dB at 5MHz, Power-Down (LT1806)
Power-Down (LT1809)
sn1800 1800fs
LT/TP 0402 2K • PRINTED IN USA
LINEAR TECHNOLOGY CORPORATION 2001
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