The EL9110 is a single channel differential receiver and
equalizer. It contains a high speed differential receiver with 5
programmable poles. The outputs of these pole blocks are
then summed into an output buffer. The equalization length
is set with the voltage on a single pin. The EL9110 also
contains a three-statable output, enabling multiple devices to
be connected in parallel and used in a multiplexing
application.
The gain can be adjusted up or down by 6dB using the
V
control signal. In addition, a further 6dB of gain can
GAIN
be switched in to provide a matched drive into a cable.
The EL9110 has a bandwidth of 150MHz and consumes just
33mA on ±5V supply. A single input volt age is used to set the
compensation levels for the required length of cable.
The EL9110 is available in the 16 Ld QSOP package and is
specified for operation over the full -40°C to +85°C
temperature range.
(Note)
*Please refer to TB347 for details on reel specifications.
NOTE: These Intersil Pb-free plastic packaged products employ
special Pb-free material sets; molding compounds/die attach
materials and 100% matte tin plate PLUS ANNEAL - e3 termination
finish, which is RoHS compliant and compatible with both SnPb and
Pb-free soldering operations. Intersil Pb-free products are MSL
classified at Pb-free peak reflow temperatures that meet or exceed
the Pb-free requirements of IPC/JEDEC J STD-020.
PART
MARKINGPACKAGEPKG. DWG. #
9110IUZ16 Ld QSOP
(Pb-free)
9110IUZ16 Ld QSOP
(Pb-free)
9110IUZ16 Ld QSOP
(Pb-free)
MDP0040
MDP0040
MDP0040
Features
• 150MHz -3dB bandwidth
• CAT-5 compensation
- 75MHz @ 1000ft
- 125MHz @ 500ft
• 33mA supply current
• Differential input range 3.2V
• Common mode input range ±4.5V
• ±5V supply
• Output to within 1.5V of supplies
• Available in 16 Ld QSOP package
• Pb-free available (RoHS compliant)
Applications
• Twisted-pair receiving/equalizer
• KVM (Keyboard/Video/Mouse)
• VGA over twisted-pair
• Security video
Pinout
EL9110
(16 LD QSOP)
TOP VIEW
CTRL_REF
CMOUT
LOGIC_REF
1
VCTRL
2
3
VINP
VINM
4
VS-
5
6
VGAIN
7
89
16
15
14
13
12
11
10
FN7305.5
CMEXT
VS+
ENBL
VSA+
VOUT
VSA-
0V
X2
1
CAUTION: These devices are sensitive to electrostatic discharge; follow proper IC Handling Procedures.
1-888-INTERSIL or 1-888-468-3774
| Intersil (and design) is a registered trademark of Intersil Americas Inc.
Copyright Intersil Americas Inc. 2003, 2005, 2007. All Rights Reserved
All other trademarks mentioned are the property of their respective owners.
EL9110
Absolute Maximum Ratings (T
Supply Voltage between VS+ and VS-. . . . . . . . . . . . . . . . . . . . .12V
CAUTION: Do not operate at or near the maximum ratings listed for extended periods of time. Exposure to such conditions may adversely impact product reliability and
result in failures not covered by warranty.
IMPORTANT NOTE: All parameters having Min/Max specifications are guaranteed. Typ values are for information purposes only. Unless otherwise noted, all tests are
at the specified temperature and are pulsed tests, therefore: T
RMS
CMRRCommon-mode Rejection RatioMeasured at 10kHz60dB
CMRR+Common-mode Rejection RatioMeasured at 10MHz50dB
CMBWCM Amplifier Bandwidth10K || 10pF load50MHz
CM
C
INDIFF
R
INDIFF
C
INCM
R
INCM
+I
IN
-I
IN
V
INDIFF
SLEW
CM Slew RateMeasured @ +1V to -1V100V/µs
Differential Input CapacitanceCapacitance V
Differential Input ResistanceResistance V
CM Input CapacitanceCapacitance V
CM Input ResistanceResistance V
Positive Input CurrentDC bias @ V
Negative Input CurrentDC bias @ V
Differential Input RangeV
INP
- V
INM
INP
INP
INP
INP
INP
INP
to V
INM
to V
INM
= V
to ground1.2pF
INM
= V
to ground12.8MΩ
INM
= V
= 0V1µA
INM
= V
= 0V1µA
INM
12.4MΩ
600fF
when slope gain falls to 0.92.53.2V
OUTPUT CHARACTERISTICS
V
O
I
OUT
R
OUTCM
DiffGainDifferential GainV
Output Voltage SwingRL = 150Ω±3.5V
Output Drive CurrentRL = 10Ω, V
PSRRPower Supply Rejection RatioDC to 100kHz, ±5V supply60dB
LOGIC CONTROL PINS
V
HI
V
LOW
I
LOGICH
I
LOGICL
Logic High LevelVIN - V
Logic Low LevelVIN - V
LOGIC
LOGIC
Logic High Input CurrentVIN = 5V, V
Logic Low Input CurrentVIN = 0V, V
ref for guaranteed high level1.35V
ref for guaranteed low level0.8V
= 0V50µA
LOGIC
= 0V15µA
LOGIC
NOTE:
1. Parts are 100% tested at +25°C. Over-temperature limits established by characterization and are not production tested.
Pin Descriptions
PIN NUMBERPIN NAMEPIN TYPEPIN FUNCTION
1CTRL_REFInputReference voltage for V
2VCTRLInputControl voltage (0 to 1V) to set equalization
3VINPInputPositive differential input
4VINMInputNegative differential input
5VS-Power-5V to core of chip
6CMOUTOutputOutput of common mode voltage present at inputs
7VGAINInputControl voltage to set overall gain (0V to 1V)
8LOGIC_REFInputReference voltage for all logic signals
9X2Logic InputLogic signal; low - gain = 1, high - gain = 2
100V0V reference for output voltage
11VSA-Power-5V to output buffer
12VOUTOutputSingle-ended output voltage reference to pin 10
13VSA+Power+5V to output buffer
14ENBLLogic InputLogic signal to enable pin; low - disabled, high - enabled
15VS+Power+5V to core of chip
16CMEXTLogic InputLogic signal to enable CM range extension; active high
GAIN
and V
CTRL
pins
3
FN7305.5
November 30, 2007
Typical Performance Curves
EL9110
5
V
= 0V
GAIN
= 0V
V
CTRL
R
LOAD
X2 = OFF
= 150Ω
FREQUENCY (Hz)
3
1
-1
GAIN (dB)
-3
-5
1M10M100M
-40
V
= 0V
GAIN
= 0V
V
CTRL
V
-45
-50
-55
THD (dBc)
-60
-65
= +5V
SS
V
= -5V
EE
= 150Ω
R
LOAD
X2 = OFF
INPUT = 0dBm
0.1M1M10M100M
FREQUENCY (Hz)
FIGURE 1. FREQUENCY RESPONSEFIGURE 2. TOTAL HARMONIC DISTORTION
0
V
200mV/DIV
-20
-40
-60
CMRR (dBc)
CTR
V
GAIN
X2 = ON
= 0V
= 0.35V
-80
-100
2ns/DIV
100k1M10M100M
FREQUENCY (Hz)
FIGURE 3. RISE TIMEFIGURE 4. COMMON MODE REJECTION
4
V
= 0.35V
GAIN
= 0V
V
CTRL
R
LOAD
X2 = ON
= 150Ω
FREQUENCY (Hz)
2
0
-2
GAIN (dB)
-4
-6
100k1M10M100M
-20
V
= -5V
EE
= 0V
V
CTRL
= 0V
V
GAIN
-40
INPUTS ON GND
-60
-80
-PSRR (dB)
-100
-120
100100k1k1M
1010k10M 100M
FREQUENCY (Hz)
FIGURE 5. CM AMPLIFIER BANDWIDTHFIGURE 6. PSRR vs FREQUENCY
4
FN7305.5
November 30, 2007
Typical Performance Curves (Continued)
EL9110
0
V
= 5V
CC
= 0V
V
CTRL
-20
-40
-60
+PSRR (dB)
-80
-100
1010k10M 100M
= 0V
V
GAIN
INPUTS ON GND
100100k1k1M
FREQUENCY (Hz)
FIGURE 7. PSRR vs FREQUENCYFIGURE 8. GAIN AS THE FUNCTION OF V
50
10ns/DIV
30
V
= 0mV
CTRL
10
-10
GROUP DELAY (ns)
-30
V
= 900mV
CTRL
-50
1M100M
10M200M
FREQUENCY (Hz)
100mV STEP
FIGURE 9. GROUP DELAY AS THE FUNCTION OF THE
FREQUENCY REPONSE CONTROL VOLTAGE
(V
)
CTRL
10dB/DIV
60
GAIN (dB)
50
40
30
20
10
0
-10
-20
100mV STEP
1M
10M100M
FREQUENCY (Hz)
V
CTR
V
= 800mV
CTRL
= 0mV
CTRL
JEDEC JESD51-3 LOW EFFECTIVE THERMAL
CONDUCTIVITY TEST BOARD
1.4
1.2
1
791mW
0.8
0.6
0.4
POWER DISSIPATION (W)
0.2
0
0 255075100150
Q
S
O
P
θ
AMBIENT TEMPERATURE (°C)
1
J
6
A
=
1
5
8
°
C
/
W
12585
FIGURE 10. PACKAGE POWER DISSIPATION vs AMBIENT
TEMPERATURE
JEDEC JESD51-7 HIGH EFFECTIVE THERMAL
CONDUCTIVITY TEST BOARD
1.8
1.6
1.4
1.116W
1.2
1
0.8
0.6
0.4
POWER DISSIPATION (W)
0.2
0
0 255075100150
Q
S
O
θ
P
1
J
AMBIENT TEMPERATURE (°C)
6
A
=
1
1
2
°
C
/
W
12585
FIGURE 11. PACKAGE POWER DISSIPATION vs AMBIENT TEMPERATURE
5
FN7305.5
November 30, 2007
EL9110
Applications Information
Logic Control
The EL9110 has three logical input pins, Chip Enable
(ENBL), Common Mode Extend (CMEXT), and Switch Gain
(X2). The logic circuits all have a nominal threshold of 1.1V
above the potential of the logic reference pin. In most
applications it is expected that this chip will run from a +5V,
0V, -5V supply system with logic being run between 0V and
+5V . In this case the logic reference voltage should be tied to
the 0V supply. If the logic is referenced to the -5V rail, then
the logic reference should be connected to -5V. The logic
reference pin sources about 60µA and this will rise to about
200µA if all inputs are true (positive).
The logic inputs all source up to 10µA when they are held at
the logic reference level. When taken positive, the inputs
sink a current dependent on the high level, up to 50µA for a
high level 5V above the reference level.
The logic inputs, if not used, should be tied to the
appropriate voltage in order to define their state.
Control Reference and Signal Reference
Analog control voltages are required to set the equalizer and
contrast levels. These signals are voltages in the range 0V
to 1V, which are referenced to the control reference pin. It is
expected that the control reference pin will be tied to 0V and
the control voltage will vary from 0V to 1V. It is; however,
acceptable to connect the control reference to any potential
between -5V and 0V to which the control voltages are
referenced.
The control voltage pins themselves are high impedance.
The control reference pin will source between 0µA and
200µA depending on the control voltages being applied.
The control reference and logic reference effectively remove
the necessity for the 0V rail and operation from ±5V (or 0V
and 10V) only is possible. However we still need a further
reference to define the 0V level of the single ended output
signal. The reference for the output signal is provided by the
0V pin. The output stage cannot pull fully up or down to
either supply so it is important that the reference is
positioned to allow full output swing. The 0V reference
should be tied to a 'quiet ground' as any noise on this pin is
transferred directly to the output. The 0V pin is a high
impedance pin and draws dc bias currents of a few µA and
similar levels of AC current.
Common Mode Extension
The common mode extension circuitry extends the range of
input common mode voltage before the input differential
amplifier is overloaded. It does this by reducing the voltage
equally at both inputs of the first differential amplifier as the
common mode signal rises towards the supply. Similarly,
when the common mode input signal goes low, the inputs to
the first differential amplifier are raised whilst preserving the
differential signal and maintain the amplifier within its
common mode operating range.
This operation may not always be desirable. A problem
occurs because the EL9110 sinks or sources a common
mode current though its input pins to create the common
mode offset voltage. Assuming the system has been set up
so that the differential line has a well-balanced impedance,
then a problem will only occur when the common mode
impedance to ground is not low. This will occur in systems
where the inputs to the EL9110 are AC coupled. In such
systems it is recommended that the common mode
extension be disabled. In systems where the differential
input signal is directly coupled and has its common mode
level defined by a low impedance line driver, the common
mode extension circuitry can extend the total common mode
range by 2V to 3V.
Equalizing
When transmitting a signal across a twisted pair cable, it is
found that the high frequency (above 1MHz) information is
attenuated more significantly than the information at low
frequencies. The attenuation is predominantly due to
resistive skin effect losses and has a loss curve which
depends on the resistivity of the conductor, surface condition
of the wire and the wire diameter. For the range of high
performance twisted pair cables based on 24awg copper
wire (Cat 5 etc.) these parameters vary only a little between
cable types, and in general cables exhibit the same
frequency dependence of loss. (The lower loss cables can
be compared with somewhat longer lengths of their more
lossy brothers.) This enables a single equalizing law
equation to be built into the EL9110.
With a control voltage applied between pins 2 and 1, the
frequency dependence of the equalization is shown in
Figure 8. The equalization matches the cable loss up to
about 100MHz. Above this, system gain is rolled off rapidly
to reduce noise bandwidth. The roll-off occurs more rapidly
for higher control voltages, thus the system (cable +
equalizer) bandwidth reduces as the cable length increases.
This is desirable, as noise becomes an increasing issue as
the equalization increases.
The cable loss for 100m, 200m, and 300m of CAT 5 cable,
based on manufacturer's loss curves is shown in Figure 14.
Thus:
• 100m requires V
• 200m requires V
and:
• 300m requires V
= 0.2V
C
= 0.6V
C
= 1.0V approximately
C
Contrast
By varying the voltage between pins 7 and 1, the gain of the
signal path can be changed in the ratio 4:1. The gain change
varies almost linearly with control voltage. For normal
6
FN7305.5
November 30, 2007
operation it is anticipated the X2 mode will be selected and
the output load will be back matched. A unity gain to the
output load will then be achieved with a gain control voltage
of about 0.35V. This allows the gain to be trimmed up or
down by 6dB to compensate for any gain/loss errors that
affect the contrast of the video signal. Figure 12 shows an
example plot of the gain to the load with gain control voltage.
2.0
1.8
1.6
1.4
1.2
GAIN (V)
1.0
0.8
0.6
0.4
00.8
FIGURE 12. VARIATION OF GAIN WITH GAIN CONTROL
VOLTAGE
0.41.0
V
0.60.2
GAIN
Circuit and Layout Recommendation
The interconnection cable is a transmission line therefore for
proper function it should be treated like transmission line, a
refection-free termination is necessary.
A reflection-free termination is a real "ohmic" resistor with as
less as possible reactive parasitic.
The traces of the layout, up to the point where of the
termination resistor placed, are part of the transmission line
which also includes the cable's connector. A connector with
a better controlled impedance is an obligation for good
picture quality. The termination resistor should be placed
close to the inputs of the device's pins (pin 3 and pin 4.) The
small capacitance differential and common mode
capacitance of the input pins of the device makes it possible
to connect parallel to the termination resistor.
The cable will work as an antenna for all the RF spectrum
which is "in the air" where the cable is used. The spectrum,
particularly its common mode components, could and will
contain high energy level of transients which are above the
built-in protection level of the device and easily could
damage its inputs. Using a transient protection circuit
according to the given application is recommended.
1. Plastic or metal protrusions of 0.006” maximum per side are not
included.
2. Plastic interlead protrusions of 0.010” maximum per side are not
included.
3. Dimensions “D” and “E1” are measured at Datum Plane “H”.
4. Dimensioning and tolerancing per ASME Y14.5M-1994.
TOLERANCE NOTESQSOP16 QSOP24 QSOP28
Rev. F 2/07
GAUGE
PLANE
L
0.010
4°±4°
A2
A1
DETAIL X
All Intersil U.S. products are manufactured, assembled and tested utilizing ISO9000 quality systems.
Intersil Corporation’s quality certifications can be viewed at www.intersil.com/design/quality
Intersil products are sold by description only. Intersil Corporation reserves the right to make changes in circuit design, software and/or specifications at any time without
notice. Accordingly, the reader is cautioned to verify that data sheets are current before placing orders. Information furnished by Intersil is believed to be accurate and
reliable. However, no responsibility is assumed by Intersil or its subsidiaries for its use; nor for any infringements of patents or other rights of third parties which may result
from its use. No license is granted by implicat ion or oth erwise u nde r any p a tent or p at ent r ights of Intersil or its subsidiaries.
For information regarding Intersil Corporation and its products, see www.intersil.com
10
FN7305.5
November 30, 2007
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