Diodes AP6503 User Manual

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Page 1

P6503

340kHz 23V 3A SYNCHRONOUS DC/DC BUCK CONVERTER

high

Pin Assignments

( Top View )

GND

Applications

• Gaming Consoles

• Flat Screen TV sets and Monitors

• Set Top Boxes

• Distributed power systems

• Home Audio

• Consumer electronics

• Network Systems

• FPGA, DSP and ASIC Supplies

• Green Electronics

SO-8EP

COMP

Description

The AP6503 is a 340kHz switching frequency external compensated

synchronous DC/DC buck converter. It has integrated low R

DSON

and low side MOSFETs.

The AP6503 enables continues load current of up to 3A with

efficiency as high as 95%.

The AP6503 features current mode control operation, which enables

fast transient response times and easy loop stabilization.

The AP6503 simplifies board layout and reduces space requirements

with its high level of integration and minimal need for external

components, making it ideal for distributed power architectures.

The AP6503 is available in a standard Green SO-8EP package with

exposed PAD for improved thermal performance and is RoHS

compliant.

Features

• VIN 4.7V to 23V

• 3A continuous Output Current, 4A Peak

• V

• 340kHz switching frequency

• Programmable Soft-Start

• Enable pin

• Protection

• Totally Lead-Free & Fully RoHS Compliant (Notes 1 & 2)

• Halogen and Antimony Free. “Green” Device (Note 3)

Notes: 1. No purposely added lead. Fully EU Directive 2002/95/EC (RoHS) & 2011/65/EU (RoHS 2) compliant.

2. See http://www.diodes.com for more information about Diodes Incorporated’s definitions of Halogen- and Antimony-free, "Green" and Lead-free.

3. Halogen- and Antimony-free "Green” products are defined as those which contain <900ppm bromine, <900ppm chlorine (<1500ppm total Br + Cl) and <1000ppm antimony compounds

adjustable to 0.925 to 20V

OUT

 OCP

 Thermal Shutdown

Typical Applications Circuit

100

V = 5V

)

Y (

IEN

EFFI

V = 3.3V

OUT

L = 10µH

0123

AP6503

Document number: DS35077 Rev. 5 - 2

V = 12V

LOAD CURRENT (A)

Efficiency vs. Load Current

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Figure 1 Typical Application Circuit

January 2013

Page 2

Pin Descriptions

Number

1 BS

2 IN

3 SW

4 GND Ground (Connect the exposed pad to Pin 4).

5 FB

6 COMP

7 EN

8 SS

EP EP EP exposed thermal pad connect to Pin 4 GND

Name

High-Side Gate Drive Boost Input. BS supplies the drive for the high-side N-Channel MOSFET switch. Connect a 0.01µF or greater capacitor from SW to BS to power the high side switch.

Power Input. IN supplies the power to the IC, as well as the step-down converter switches. Drive IN with a

4.7V to 23V power source. Bypass IN to GND with a suitably large capacitor to eliminate noise on the input to the IC. See Input Capacitor.

Power Switching Output. SW is the switching node that supplies power to the output. Connect the output LC filter from SW to the output load. Note that a capacitor is required from SW to BS to power the high-side switch.c

Feedback Input. FB senses the output voltage and regulates it. Drive FB with a resistive voltage divider connected to it from the output voltage. The feedback threshold is 0.925V. See Setting the Output Voltage.

Compensation Node. COMP is used to compensate the regulation control loop. Connect a series RC network from COMP to GND. In some cases, an additional capacitor from COMP to GND is required. See Compensation Components.

Enable Input. EN is a digital input that turns the regulator on or off. Drive EN high to turn on the regulator; low to turn it off. Attach to IN with a 100k pull up resistor for automatic startup.

Soft-Start Control Input. SS controls the soft-start period. Connect a capacitor from SS to GND to set the soft-start period. A 0.1µF capacitor sets the soft-start period to 15ms. To disable the soft-start feature, leave SS floating.

Functional Block Diagram

P6503

Function

COMP

1.1V

0.3 V

0.923 V

0.9V

2.5V

ERROR

AMPLIFIER

LOCKOUT

COMPARATOR

OVP

OSCILLATOR

100/340 KHz

EN OK

SHUTDOWN

RAMP

CLK

6uA

CURRENT

SENSE

AMPLIFIER

Logic

CURRENT

COMPARATOR

INTERNAL

REGULATORS

IN < 4.10V

disable

100m

GND

Figure 2 Functional Block Diagram

AP6503

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P6503

Absolute Maximum Ratings (Note 4) (@T

Symbol Parameter Rating Unit

VIN

VSW

VBS

VFB

VEN

COMP

TST

ESD Susceptibility (Note 5)

HBM Human Body Model 3 kV

MM Machine Model 250 V

Notes: 4. Stresses greater than the 'Absolute Maximum Ratings' specified above, may cause permanent damage to the device. These are stress ratings only; functional operation of the device at these or any other conditions exceeding those indicated in this specification is not implied. Device reliability may be affected by exposure to absolute maximum rating conditions for extended periods of time.

5. Semiconductor devices are ESD sensitive and may be damaged by exposure to ESD events. Suitable ESD precautions should be taken when handling and transporting these devices.

Supply Voltage -0.3 to +26 V

Switch Node Voltage

Bootstrap Voltage

Feedback Voltage -0.3V to +6 V

Enable/UVLO Voltage -0.3V to +6 V

Comp Voltage -0.3V to +6 V

Storage Temperature -65 to +150 °C

Junction Temperature +150 °C

Lead Temperature +260 °C

= +25°C, unless otherwise specified.)

-1.0 to V

-0.3 to VSW +6

+0.3

Thermal Resistance (Note 6)

Symbol Parameter Rating Unit

JA

JC

Note: 6. Test condition for SO-8EP: Measured on approximately 1” square of 1 oz copper

Recommended Operating Conditions (Note 7) (@T

Symbol Parameter Min Max Unit

VIN

Note: 7. The device function is not guaranteed outside of the recommended operating conditions.

Operating Ambient Temperature Range -40 +85 °C

Junction to Ambient 74 °C/W

Junction to Case 16 °C/W

= +25°C, unless otherwise specified.)

Supply Voltage 4.7 23 V

AP6503

Document number: DS35077 Rev. 5 - 2

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P6503

Electrical Characteristics (V

Symbol Parameter Test Conditions Min Typ Max Unit

IIN IIN

DS(ON)1

DS(ON)2

Limi

High-Side Switch Leakage Current

AVEA

GEA Error Amplifier Transconductance

GCS

FSW

FFB

MAX

TON

VFB

Feedback Overvoltage Threshold 1.1 V

EN_Risin

EN Lockout Threshold Voltage 2.2 2.5 2.7 V EN Lockout Hysteresis 220 mV

INUV

HYS

Soft-Start Current Soft-Start Period

TSD

Note: 8. Guaranteed by design

Shutdown Supply Current Supply Current (Quiescent) High-Side Switch On-Resistance (Note 8) 100 m Low-Side Switch On-Resistance (Note 8) 100 m HS Current Limit Minimum duty cycle 5.5 A LS Current Limit From Drain to Source 0.9 A

Error Amplifier Voltage Gain (Note 8)

COMP to Current Sense Transconductance

Oscillator Frequency Fold-back Frequency Maximum Duty Cycle Minimum On Time 130 ns Feedback Voltage

EN Rising Threshold 0.7 0.8 0.9 V

Vth

Under Voltage Threshold Rising

VIN Under Voltage Threshold Hysteresis

Thermal Shutdown (Note 8) 160 °C

= 12V, TA = +25°C, unless otherwise specified.)

VEN = 0V VEN = 2.0V, VFB = 1.0V

= 0V, VSW = 0V,

=12V

800 V/V

I

= ±10µA

2.8 A/V

= 0.75V

= 0V

VFB = 800mV

TA = -40°C to +85°C

3.80 4.05 4.40 V 250 mV

= 0V

= 0.1µF

0.3 3.0 µA

0.6 1.5 mA

0 10 A

1000 µA/V

300 340 380 kHz

0.30

fSW

90 %

900 925 950 mV

6 A 15 ms

AP6503

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P6503

Typical Performance Graphs (V

0.6

0.58

0.56

0.54

0.52

0.5

QUIESCENT SUPPLY CURRENT (mA)

0.48 0 5 10 15 20 25

INPUT VOLTAGE (V)

Quiescent Supply Current vs. Input Voltage

6.2

5.8

5.6

5.4

= 12V, V

= 3.3V, TA = +25°C, unless otherwise noted)

OUT

0.074

0.064

0.054

0.044

0.034

0.024

0.014

SHUTDOWN SUPPLY CURRENT (µA)

0.004 0 5 10 15 20 25

3.33

3.329

3.328

3.327

3.326

3.325

3.324

Shutdown Supply Current vs. Input Voltage

INPUT VOLTAGE (V)

V = 12V

5.2

4.8

-60 -40 -20 0 20 40 60 80 100

TEMPERATURE (C)

Current Limit vs. Temperature

0.92

0.918

0.916

0.914

E (V)

0.912

LTA

0.91

K V

0.908

0.906

FEEDBA

0.904

0.902

0.9

-60 -40 -20 0 20 40 60 80 100

TEMPERATURE (°C)

Feedback Voltage vs. Temperature

3.323

OUTPUT VOLTAGE (V)

3.322

3.321

3.32

4.75 9.75 14.75 19.75 24.75

INPUT VOLTAGE (V)

Line Regulation

375

370

365

360

355

OSCILLATOR FREQUENCY (Khz)

350

TEMPERATURE (°C)

Oscillator Frequency vs. Temperature

AP6503

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P6503

Typical Performance Graphs (cont.) (V

EFFICIENCY (%)

100

V = 1.2V

OUT

L = 3.3µH

V = 5V

V = 12V

LOAD CURRENT (A)

Efficiency vs. Load Current

= 12V, V

= 3.3V, TA = +25°C, unless otherwise noted)

OUT

(%)

V = 5V

IEN

EFFI

V = 1.8V

OUT

L = 3.3µH

LOAD CURRENT (A)

Efficiency vs. Load Current

V = 12V

EFFICIENCY (%)

V = 12V

V = 5V

OUT

L = 10µH

0.2 0.6 1 1.4

1.8 2.2 2.6 3

LOAD CURRENT (A)

Efficiency vs. Load Current

AP6503

Document number: DS35077 Rev. 5 - 2

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Typical Performance Characteristics

(VIN = 12V, V

Steady State Test no load

= 3.3V ,L = 3.3µH, C1 = 22µF, C2 = 47µF, TA = +25°C, unless otherwise noted)

OUT

Steady State Test 3

P6503

Startup Through Enable_no load

Time -2µs/div

Startup Through Enable 3A

Time -10ms/div

Load Transient Test 1.5 to 3

Time -2µs/div

Shutdown Through Enable_no load

Time -10ms/div

Short Circuit Test

Time -10ms/div

Shutdown Through Enable 3

Time -5ms/div

Short Circuit Recovery

Time -100µs/div

AP6503

Document number: DS35077 Rev. 5 - 2

Time -20µs/div

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Time -20µs/div

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P6503

Application Information

Theory of Operation

The AP6503 is a 3A current mode control, synchronous buck regulator with built in power MOSFETs. Current mode control assures excellent

line and load regulation and a wide loop bandwidth for fast response to load transients. Figure 3 depicts the functional block diagram of AP6503.

The operation of one switching cycle can be explained as follows. At the beginning of each cycle, HS (high-side) MOSFET is off. The EA output

voltage is higher than the current sense amplifier output, and the current comparator’s output is low. The rising edge of the 340kHz oscillator

clock signal sets the RS Flip-Flop. Its output turns on HS MOSFET. The current sense amplifier is reset for every switching cycle.

When the HS MOSFET is on, inductor current starts to increase. The Current Sense Amplifier senses and amplifies the inductor current. Since

the current mode control is subject to sub-harmonic oscillations that peak at half the switching frequency, Ramp slope compensation is utilized.

This will help to stabilize the power supply. This Ramp compensation is summed to the Current Sense Amplifier output and compared to the

Error Amplifier output by the PWM Comparator. When the sum of the Current Sense Amplifier output and the Slope Compensation signal

exceeds the EA output voltage, the RS Flip-Flop is reset and HS MOSFET is turned off.

For one whole cycle, if the sum of the Current Sense Amplifier output and the Slope Compensation signal does not exceed the EA output, then

the falling edge of the oscillator clock resets the Flip-Flop. The output of the Error Amplifier increases when feedback voltage (VFB) is lower than

the reference voltage of 0.925V. This also increases the inductor current as it is proportional to the EA voltage.

If in one cycle the current in the power MOSFET does not reach the COMP set current value, the power MOSFET will be forced to turn off. When

the HS MOSFET turns off, the synchronous LS MOSFET turns on until the next clock cycle begins. There is a “dead time” between the HS turn

off and LS turn on that prevents the switches from “shooting through” from the input supply to ground.

The voltage loop is compensated through an internal transconductance amplifier and can be adjusted through the external compensation

components.

Enable

Above the ‘EN Rising Threshold’, the internal regulator is turned on and the quiescent current can be measured above this threshold. The enable

(EN) input allows the user to control turning on or off the regulator. To enable the AP6503, EN must be pulled above the ‘EN Lockout Threshold

Voltage’ and to disable the AP6503, EN must be pulled below ‘EN Lockout Threshold Voltage - EN Lockout Hysteresis’ (2.2V-0.22V =1.98V).

External Soft Start

Soft start is traditionally implemented to prevent the excess inrush current. This in turn prevents the converter output voltage from overshooting

when it reaches regulation. The AP6503 has an internal current source with a soft start capacitor to ramp the reference voltage from 0V to

0.925V. The soft start current is 6uA. The soft start sequence is reset when there is a Thermal Shutdown, Under Voltage Lockout (UVLO) or

when the part is disabled using the EN pin.

External Soft Start can be calculated from the formula below:

Where;

= Soft Start Current

C = External Capacitor

DV=change in feedback voltage from 0V to maximum voltage

DT = Soft Start Time

I =

Current Limit Protection

In order to reduce the total power dissipation and to protect the application, AP6503 has cycle-by-cycle current limiting implementation. The

voltage drop across the internal high-side MOSFET is sensed and compared with the internally set current limit threshold. This voltage drop is

sensed at about 30ns after the HS turns on. When the peak inductor current exceeds the set current limit threshold, current limit protection is

activated. During this time the feedback voltage (VFB) drops down. When the voltage at the FB pin reaches 0.3V, the internal oscillator shifts

the frequency from the normal operating frequency of 340Khz to a fold-back frequency of 102Khz. The current limit is reduced to 70% of nominal

current limit when the part is operating at 102Khz. This low Fold-back frequency prevents runaway current.

Under Voltage Lockout (UVLO)

Under Voltage Lockout is implemented to prevent the IC from insufficient input voltages. The AP6503 has a UVLO comparator that monitors the

input voltage and the internal bandgap reference. If the input voltage falls below 4.0V, the AP6503 will latch an under voltage fault. In this event

the output will be pulled low and power has to be re-cycled to reset the UVLO fault.

AP6503

Document number: DS35077 Rev. 5 - 2

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P6503

Application Information (cont.)

Over Voltage Protection

When the AP6503 FB pin exceeds 20% of the nominal regulation voltage of 0.925V, the over voltage comparator is tripped and the COMP pin

and the SS pin are discharged to GND, forcing the high-side switch off.

Thermal Shutdown

The AP6503 has on-chip thermal protection that prevents damage to the IC when the die temperature exceeds safe margins. It implements a

thermal sensing to monitor the operating junction temperature of the IC. Once the die temperature rises to approximately 160°C, the thermal

protection feature gets activated. The internal thermal sense circuitry turns the IC off thus preventing the power switch from damage.

A hysteresis in the thermal sense circuit allows the device to cool down to approximately +120°C before the IC is enabled again through soft

start. This thermal hysteresis feature prevents undesirable oscillations of the thermal protection circuit.

Setting the Output Voltage

The output voltage can be adjusted from 0.925V to 18V using an external resistor divider. Table 1 shows a list of resistor selection for common

output voltages. Resistor R1 is selected based on a design tradeoff between efficiency and output voltage accuracy. For high values of R1 there

is less current consumption in the feedback network. However the trade off is output voltage accuracy due to the bias current in the error

amplifier. R1 can be determined by the following equation:

⎛

⎜

0.925

⎝

OUT

−⋅= 1

⎞ ⎟

⎟ ⎠

Figure 3. Feedback Divider Network

When output voltage is low, network as shown in Figure 3 is recommended.

(V)

OUT

5 45.3 10

3.3 26.1 10

2.5 16.9 10

1.8 9.53 10

1.2 3 10

R1(KΩ) R2(KΩ)

Table 1 – Resistor Selection for Common Output Voltages

Compensation Components

The AP6503 has an external COMP pin through which system stability and transient response can be controlled. COMP pin is the output of the

internal trans-conductance error amplifier. A series capacitor-resistor combination sets a pole-zero combination to control the characteristics of the

control system. The DC gain of the voltage feedback loop is given by:

OUT

is the error

VEA

Where V

amplifier voltage gain.

is the feedback voltage (0.925V), R

A ×××=

LOAD

VDC

is the load resistor value, GCS is the current sense trans-conductance and A

LOAD

VEA

AP6503

Document number: DS35077 Rev. 5 - 2

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P6503

Application Information (cont.)

Compensation Components (cont.)

The control loop transfer function incorporates two poles one is due to the compensation capacitor (C3) and the output resistor of error amplifier,

and the other is due to the output capacitor and the load resistor. These poles are located at:

/C2

10 of 15

<×

××π

R2C2

××π

RC/R3

Where G

One zero is present due to the compensation capacitor (C3) and the compensation resistor (R3). This zero is located at:

The goal of compensation design is to shape the converter transfer function to get a desired loop gain. The system crossover frequency where

the feedback loop has the unity gain is crucial.

A rule of thumb is to set the crossover frequency to below one-tenth of the switching frequency. Use the following procedure to optimize the

compensation components:

1. Choose the compensation resistor (R3) to set the desired crossover frequency. Determine the R3 value by the following equation:

Where f

2. Choose the compensation capacitor (C3) to achieve the desired phase margin set the compensation zero, f

crossover frequency to provide sufficient phase margin. Determine the C3 value by the following equation:

is the error amplifier trans-conductance.

fc2C2

××π

3R ×

is the crossover frequency, which is typically less than one tenth of the switching frequency.

OUT

Where R3 is the compensation resistor value.

AP6503

Document number: DS35077 Rev. 5 - 2

CIN/C1

OUT

(V)

1.2 22 47 3.24 6.8 3.3

1.8 22 47 6.8 6.8 3.3

2.5 22 47 6.8 6.8 10

3.3 22 47 6.8 6.8 10

5 22 47 6.8 6.8 10

12 22 47 6.8 6.8 15

(µF)

Table 2 – Recommended Component Selection

OUT

(µF)

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A3C2

VEA

LOAD

××π

fc3R

(kΩ)

3R3C2

fs1.02C2

×××π

CC/C3

(nF)

OUT

(µH)

, to below one forth of the

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P6503

Application Information (cont.)

Inductor

Calculating the inductor value is a critical factor in designing a buck converter. For most designs, the following equation can be used to calculate

the inductor value;

)

OUT

I

Where

And

Choose the inductor ripple current to be 30% of the maximum load current. The maximum inductor peak current is calculated from:

Peak current determines the required saturation current rating, which influences the size of the inductor. Saturating the inductor decreases the

converter efficiency while increasing the temperatures of the inductor and the internal MOSFETs. Hence choosing an inductor with appropriate

saturation current rating is important.

A 1µH to 10µH inductor with a DC current rating of at least 25% percent higher than the maximum load current is recommended for most

applications.

For highest efficiency, the inductor’s DC resistance should be less than 200m. Use a larger inductance for improved efficiency under light load

conditions.

is the inductor ripple current.

f is the buck converter switching frequency.

I +=

L(MAX)

LOAD

−⋅

OUT

I

fLI

⋅⋅

Input Capacitor

The input capacitor reduces the surge current drawn from the input supply and the switching noise from the device. The input capacitor has to

sustain the ripple current produced during the on time on the upper MOSFET. It must hence have a low ESR to minimize the losses.

The RMS current rating of the input capacitor is a critical parameter that must be higher than the RMS input current. As a rule of thumb, select an

input capacitor which has an RMs rating that is greater than half of the maximum load current.

Due to large dI/dt through the input capacitors, electrolytic or ceramics should be used. If a tantalum must be used, it must be surge protected.

Otherwise, capacitor failure could occur. For most applications, a 4.7µF ceramic capacitor is sufficient.

Output Capacitor

The output capacitor keeps the output voltage ripple small, ensures feedback loop stability and reduces the overshoot of the output voltage. The

output capacitor is a basic component for the fast response of the power supply. In fact, during load transient, for the first few microseconds it

supplies the current to the load. The converter recognizes the load transient and sets the duty cycle to maximum, but the current slope is limited

by the inductor value.

Maximum capacitance required can be calculated from the following equation:

ESR of the output capacitor dominates the output voltage ripple. The amount of ripple can be calculated from the equation below:

ESR*

)

−+

V2)

out

January 2013

L(I

out

I

inductor

I

inductor

V V(

out

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Vout =

capacitor

An output capacitor with ample capacitance and low ESR is the best option. For most applications, a 22µF ceramic capacitor will be sufficient.

V

Where

AP6503

Document number: DS35077 Rev. 5 - 2

is the maximum output voltage overshoot.

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Page 12

P6503

Application Information (cont.)

PC Board Layout

This is a high switching frequency converter. Hence attention must be paid to the switching currents interference in the layout. Switching current

from one power device to another can generate voltage transients across the impedances of the interconnecting bond wires and circuit traces.

These interconnecting impedances should be minimized by using wide, short printed circuit traces.

34mm

AP6503 is exposed at the bottom of the package and must be soldered directly to a well designed thermal pad on the PCB. This will help to

increase the power dissipation.

52mm

External feedback resistor dividers must be placed close to the FB pin.

Input capacitor C1 must be placed as close as possible to the IC and to L1.

External Bootstrap Diode

It is recommended that an external bootstrap diode be added when the input voltage is no greater than 5V or the 5V rail is available in the

system. This helps to improve the efficiency of the regulator. This solution is also applicable for D > 65%. The bootstrap diode can be a low cost

one such as BAT54 or a schottky that has a low Vf.

BOOST

DIODE

BST

AP6503

Figure 7 – External Bootstrap

Compensation Components

10nF

Recommended Diodes:

Part Number

B130 30V, 1A Diodes Inc

SK13 30V, 1A Diodes Inc

Voltage/Current

Rating

Vendor

AP6503

Document number: DS35077 Rev. 5 - 2

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Page 13

Ordering Information

P6503

AP6503 SP - 13

Package

SP : SO-8EP

Packing

13 : Tape & Reel

Part Number

AP6503SP-13 SP SO-8EP 2500/Tape & Reel -13

Package

Code

Packaging

Quantity Part Number Suffix

13” Tape and Reel

Marking Information

Package Outline Dimensions (All dimensions in mm.)

SO-8EP

9° (All si des)

4° ± 3°

Bottom View

Exposed Pad

Gauge Plane

Seating Plane

SO-8EP (SOP-8L-EP)

Dim Min Max Typ

A 1.40 1.50 1.45

A1 0.00 0.13 -

b 0.30 0.50 0.40 C 0.15 0.25 0.20 D 4.85 4.95 4.90

E 3.80 3.90 3.85 E0 3.85 3.95 3.90 E1 5.90 6.10 6.00

e - - 1.27

F 2.75 3.35 3.05

H 2.11 2.71 2.41

L 0.62 0.82 0.72

N - - 0.35

Q 0.60 0.70 0.65

All Dimensions in mm

AP6503

Document number: DS35077 Rev. 5 - 2

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Page 14

Suggested Pad Layout

SO-8EP

AP6503

Document number: DS35077 Rev. 5 - 2

P6503

Dimensions

C 1.270

X 0.802

X1 3.502 X2 4.612

Y 1.505 Y1 2.613 Y2 6.500

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Value

(in mm)

January 2013

Page 15

P6503

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labeling can be reasonably expected to result in significant injury to the user.

B. A critical component is any component in a life support device or system whose failure to perform can be reasonably expected to cause the failure of the life support device or to affect its safety or effectiveness.

Customers represent that they have all necessary expertise in the safety and regulatory ramifications of their life support devices or systems, and acknowledge and agree that they are solely responsible for all legal, regulatory and safety-related requirements concerning their products and any use of Diodes Incorporated products in such safety-critical, life support devices or systems, notwithstanding any devices- or systems-related information or support that may be provided by Diodes Incorporated. Further, Customers must fully indemnify Diodes Incorporated and its representatives against any damages arising out of the use of Diodes Incorporated products in such safety-critical, life support devices or systems.

www.diodes.com

IMPORTANT NOTICE

LIFE SUPPORT

AP6503

Document number: DS35077 Rev. 5 - 2

15 of 15

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January 2013