Datasheet TNY268P, TNY268G, TNY267P, TNY266P, TNY267G Datasheet (Power Integrations)

TNY264/266-268

®

®

TinySwitch-II

Enhanced, Energy Efficient,
Low Power Off-line Switcher

Family

Product Highlights

TinySwitch-II

• Fully integrated auto-restart for short circuit and open
loop fault protection–saves external component costs

• Built-in circuitry practically eliminates audible noise with
ordinary varnished transformer

• Programmable line under-voltage detect feature prevents
power on/off glitches–saves external components

• Frequency jittering dramatically reduces EMI (~10 dB)
–minimizes EMI filter component costs

• 132 kHz operation reduces transformer size–allows use of

EF12.6 or EE13 cores for low cost and small size

• Very tight tolerances and negligible temperature variation
on key parameters eases design and lowers cost

• Lowest component count switcher solution

Better Cost/Performance over RCC & Linears

• Lower system cost than RCC, discrete PWM and other
integrated/hybrid solutions

• Cost effective replacement for bulky regulated linears

• Simple ON/OFF control–no loop compensation needed

• No bias winding–simpler, lower cost transformer

EcoSmart

• No load consumption < 50 mW with bias winding and
< 250 mW without bias winding at 265 VAC input

• Meets Blue Angel, Energy Star, and EC requirements

• Ideal for cell-phone charger and PC standby applications

High Performance at Low Cost

• High voltage powered–ideal for charger applications

• High bandwidth provides fast turn on with no overshoot

• Current limit operation rejects line frequency ripple

• Built-in current limit and thermal protection

Features Reduce System Cost

®

–Extremely Energy Efficient

Description

TinySwitch-II maintains the simplicity of the TinySwitch
topology, while providing a number of new enhancements to
further reduce system cost and component count, and to
practically eliminate audible noise. Like TinySwitch, a 700 V
power MOSFET, oscillator, high voltage switched current source,
current limit and thermal shutdown circuitry are integrated onto a
monolithic device. The start-up and operating power are derived
directly from the voltage on the DRAIN pin, eliminating the
need for a bias winding and associated circuitry. In addition, the

+

Optional

UV Resistor

Wide-Range
HV DC Input

TinySwitch-II

-

Figure 1. Typical Standby Application.

D

EN/UV
BP

S

+

DC Output

-

PI-2684-101700

OUTPUT POWER TABLE

230 VAC ±15%

PRODUCT

TNY264P or G
TNY266P or G
TNY267P or G
TNY268P or G

T able 1. Notes: 1. T ypical continuous power in a non-ventilated enclosed
adapter measured at 50 ˚C ambient. 2. Maximum practical continuous
power in an open frame design with adequate heat sinking, measured at
50 ˚C ambient (See key applications section for details). 3. Packages:
P: DIP-8B, G: SMD-8B. Please see part ordering information.

(3)

Adapter

(1)

Open

Frame

(2)

5.5 W 9 W 4 W 6 W
10 W 15 W 6 W 9.5 W
13 W 19 W 8 W 12 W
16 W 23 W 10 W 15 W

TinySwitch-II devices incorporate auto-restart, line under­voltage sense, and frequency jittering. An innovative design
minimizes audio frequency components in the simple ON/OFF
control scheme to practically eliminate audible noise with
standard taped/varnished transformer construction. The fully
integrated auto-restart circuit safely limits output power during
fault conditions such as output short circuit or open loop,
reducing component count and secondary feedback circuitry
cost. An optional line sense resistor externally programs a line
under-voltage threshold, which eliminates power down glitches
caused by the slow discharge of input storage capacitors present
in applications such as standby supplies. The operating frequency
of 132 kHz is jittered to significantly reduce both the quasi-peak
and average EMI, minimizing filtering cost.

85-265 VAC

Adapter

(1)

Open

Frame

(2)

July 2001

TNY264/266-268

BYPASS

(BP)

240 µA 50 µA

ENABLE

1.0 V + V

ENABLE/

UNDER-

VOLTAGE

(EN/UV)

1.0 V

DRAIN

REGULATOR

5.8 V

LINE UNDER-VOLTAGE

FAULT

RESET

MAX

PRESENT

CURRENT

LIMIT STATE

MACHINE

5.8 V

4.8 V

THERMAL

SHUTDOWN

SRQ

Q

AUTO-

RESTART

COUNTER

6.3 V

JITTER

CLOCK

T

DC

OSCILLATOR

BYPASS PIN
UNDER-VOLTAGE

+

-

V

I

LIMIT

CURRENT LIMIT
COMPARATOR

LEADING

EDGE

BLANKING

­+

(D)

Figure 2. Functional Block Diagram.

Pin Functional Description

DRAIN (D) Pin:

Power MOSFET drain connection. Provides internal operating
current for both start-up and steady-state operation.

BYPASS (BP) Pin:

Connection point for a 0.1 µF external bypass capacitor for the
internally generated 5.8 V supply.

ENABLE/UNDER-VOLTAGE (EN/UV) Pin:

This pin has dual functions: enable input and line under-voltage
sense. During normal operation, switching of the power
MOSFET is controlled by this pin. MOSFET switching is
terminated when a current greater than 240 µA is drawn from
this pin. This pin also senses line under-voltage conditions
through an external resistor connected to the DC line voltage.
If there is no external resistor connected to this pin,
TinySwitch-II detects its absence and disables the line under­voltage function.

SOURCE

(S)

PI-2643-030701

P Package (DIP-8B)

G Package (SMD-8B)

BP

1

S

2

S

3

EN/UV

4

Figure 3. Pin Configuration.

S (HV RTN)

8
7

S (HV RTN)

5

D

PI-2685-101600

SOURCE (S) Pin:

Control circuit common, internally connected to output
MOSFET source.

SOURCE (HV RTN) Pin:

Output MOSFET source connection for high voltage return.

B

2

7/01

TNY264/266-268

TinySwitch-II

Functional Description

TinySwitch-II combines a high voltage power MOSFET switch
with a power supply controller in one device. Unlike conventional
PWM (Pulse Width Modulator) controllers, TinySwitch-II uses
a simple ON/OFF control to regulate the output voltage.

The TinySwitch-II controller consists of an Oscillator, Enable
Circuit (Sense and Logic), Current Limit State Machine, 5.8 V
Regulator, Bypass pin Under-Voltage Circuit, Over
Temperature Protection, Current Limit Circuit, Leading Edge
Blanking and a 700 V power MOSFET. TinySwitch-II
incorporates additional circuitry for Line Under-Voltage Sense,
Auto-Restart and Frequency Jitter. Figure 2 shows the functional
block diagram with the most important features.

Oscillator

The typical oscillator frequency is internally set to an average
of 132 kHz. Two signals are generated from the oscillator: the
Maximum Duty Cycle signal (DC

) and the Clock signal that

MAX

indicates the beginning of each cycle.

The TinySwitch-II oscillator incorporates circuitry that
introduces a small amount of frequency jitter, typically 8 kHz
peak-to-peak, to minimize EMI emission. The modulation rate
of the frequency jitter is set to 1 kHz to optimize EMI reduction
for both average and quasi-peak emissions. The frequency jitter
should be measured with the oscilloscope triggered at the
falling edge of the DRAIN waveform. The waveform in Figure4
illustrates the frequency jitter of the TinySwitch-II.

Enable Input and Current Limit State Machine

The enable input circuit at the EN/UV pin consists of a low
impedance source follower output set at 1.0 V. The current
through the source follower is limited to 240 µA. When the
current out of this pin exceeds 240 µA, a low logic level

(disable) is generated at the output of the enable circuit. This
enable circuit output is sampled at the beginning of each cycle
on the rising edge of the clock signal. If high, the power
MOSFET is turned on for that cycle (enabled). If low, the power
MOSFET remains off (disabled). Since the sampling is done
only at the beginning of each cycle, subsequent changes in the
EN/UV pin voltage or current during the remainder of the cycle
are ignored.

The Current Limit State Machine reduces the current limit by
discrete amounts at light loads when TinySwitch-II is likely to
switch in the audible frequency range. The lower current limit
raises the effective switching frequency above the audio range
and reduces the transformer flux density including the associated
audible noise. The state machine monitors the sequence of
EN/UV pin voltage levels to determine the load condition and
adjusts the current limit level accordingly in discrete amounts.

Under most operating conditions (except when close to no­load), the low impedance of the source follower keeps the
voltage on the EN/UV pin from going much below 1.0 V in the
disabled state. This improves the response time of the optocoupler
that is usually connected to this pin.

5.8 V Regulator and 6.3 V Shunt Voltage Clamp

The 5.8 V regulator charges the bypass capacitor connected to
the BYPASS pin to 5.8 V by drawing a current from the voltage
on the DRAIN pin, whenever the MOSFET is off. The
BYPASS pin is the internal supply voltage node for the
TinySwitch-II. When the MOSFET is on, the TinySwitch-II
operates from the energy stored in the bypass capacitor.
Extremely low power consumption of the internal circuitry
allows TinySwitch-II to operate continuously from current it
takes from the DRAIN pin. A bypass capacitor value of 0.1 µF
is sufficient for both high frequency decoupling and energy
storage.

600

500

400

300
200

100

0

0

Figure 4. Frequency Jitter.

In addition, there is a 6.3 V shunt regulator clamping the
BYPASS pin at 6.3 V when current is provided to the BYPASS

V

DRAIN

PI-2741-041901

pin through an external resistor. This facilitates powering of
TinySwitch-II externally through a bias winding to decrease the
no load consumption to about 50 mW.

BYPASS Pin Under-Voltage

The BYPASS pin under-voltage circuitry disables the power
MOSFET when the BYPASS pin voltage drops below 4.8 V.
Once the BYPASS pin voltage drops below 4.8 V, it must rise
back to 5.8 V to enable (turn-on) the power MOSFET.

136 kHz
128 kHz

510

Time (µs)

7/01

B

3

TNY264/266-268

Over Temperature Protection

The thermal shutdown circuitry senses the die temperature. The
threshold is typically set at 135 °C with 70 °C hysteresis. When
the die temperature rises above this threshold the power
MOSFET is disabled and remains disabled until the die
temperature falls by 70 °C, at which point it is re-enabled. A
large hysteresis of 70 °C (typical) is provided to prevent
overheating of the PC board due to a continuous fault condition.

Current Limit

The current limit circuit senses the current in the power MOSFET.
When this current exceeds the internal threshold (I

LIMIT

), the
power MOSFET is turned off for the remainder of that cycle.
The current limit state machine reduces the current limit threshold
by discrete amounts under medium and light loads.

The leading edge blanking circuit inhibits the current limit
comparator for a short time (t

) after the power MOSFET is

LEB

turned on. This leading edge blanking time has been set so that
current spikes caused by capacitance and secondary-side rectifier
reverse recovery time will not cause premature termination of
the switching pulse.

Auto-Restart

In the event of a fault condition such as output overload, output
short circuit, or an open loop condition, TinySwitch-II enters
into auto-restart operation. An internal counter clocked by the
oscillator gets reset every time the EN/UV pin is pulled low. If
the EN/UV pin is not pulled low for 50 ms, the power MOSFET
switching is normally disabled for 850 ms (except in the case of
line under-voltage condition in which case it is disabled until
the condition is removed). The auto-restart alternately enables
and disables the switching of the power MOSFET until the fault
condition is removed. Figure 5 illustrates auto-restart circuit
operation in the presence of an output short circuit.

In the event of a line under-voltage condition, the switching of

the power MOSFET is disabled beyond its normal 850 ms time
until the line under-voltage condition ends.

Line Under-Voltage Sense Circuit

The DC line voltage can be monitored by connecting an
external resistor from the DC line to the EN/UV pin. During
power-up or when the switching of the power MOSFET is
disabled in auto-restart, the current into the EN/UV pin must
exceed 50 µA to initiate switching of the power MOSFET.
During power-up, this is implemented by holding the BYPASS
pin to 4.8 V while the line under-voltage condition exists. The
BYPASS pin then rises from 4.8 V to 5.8V when the line under­voltage condition goes away. When the switching of the power
MOSFET is disabled in auto-restart mode and a line under­voltage condition exists, the auto-restart counter is stopped.
This stretches the disable time beyond its normal 850ms until
the line under-voltage condition ends.

The line under-voltage circuit also detects when there is no
external resistor connected to the EN/UV pin (less than ~ 2 µA
into pin). In this case the line under-voltage function is disabled.

TinySwitch-II

Operation

TinySwitch-II devices operate in the current limit mode. When
enabled, the oscillator turns the power MOSFET on at the
beginning of each cycle. The MOSFET is turned off when the
current ramps up to the current limit or when the DC

MAX

limit is
reached. As the highest current limit level and frequency of a
TinySwitch-II design are constant, the power delivered to the
load is proportional to the primary inductance of the transformer
and peak primary current squared. Hence, designing the supply
involves calculating the primary inductance of the transformer
for the maximum output power required. If the TinySwitch-II is
appropriately chosen for the power level, the current in the
calculated inductance will ramp up to current limit before the
DC

limit is reached.

MAX

300

200

100

0

10

5

0

0

Figure 5. TinySwitch-II Auto-Restart Operation.

B

4

7/01

V

DRAIN

V

DC-OUTPUT

1000 2000

Time (ms)

Enable Function

TinySwitch-II senses the EN/UV pin to determine whether or
not to proceed with the next switch cycle as described earlier.

PI-2699-030701

The sequence of cycles is used to determine the current limit.
Once a cycle is started, it always completes the cycle (even
when the EN/UV pin changes state half way through the cycle).
This operation results in a power supply in which the output
voltage ripple is determined by the output capacitor, amount of
energy per switch cycle and the delay of the feedback.

The EN/UV pin signal is generated on the secondary by
comparing the power supply output voltage with a reference
voltage. The EN/UV pin signal is high when the power supply
output voltage is less than the reference voltage.

In a typical implementation, the EN/UV pin is driven by an
optocoupler. The collector of the optocoupler transistor
isconnected to the EN/UV pin and the emitter is connected to

TNY264/266-268

the SOURCE pin. The optocoupler LED is connected in series
with a Zener diode across the DC output voltage to be regulated.
When the output voltage exceeds the target regulation voltage
level (optocoupler LED voltage drop plus Zener voltage), the
optocoupler LED will start to conduct, pulling the EN/UV pin
low. The Zener diode can be replaced by a TL431 reference
circuit for improved accuracy.

ON/OFF Operation with Current Limit State Machine

The internal clock of the TinySwitch-II runs all the time. At the

V

EN

CLOCK

D

MAX

I

DRAIN

V

DRAIN

PI-2749-050301

Figure 6. TinySwitch-II Operation at Near Maximum Loading.

beginning of each clock cycle, it samples the EN/UV pin to
decide whether or not to implement a switch cycle, and based
on the sequence of samples over multiple cycles, it determines
the appropriate current limit. At high loads, when the EN/UV
pin is high (less than 240 µA out of the pin), a switching cycle
with the full current limit occurs. At lighter loads, when EN/UV
is high, a switching cycle with a reduced current limit occurs.

At near maximum load, TinySwitch-II will conduct during
nearly all of its clock cycles (Figure 6). At slightly lower load,
it will “skip” additional cycles in order to maintain voltage
regulation at the power supply output (Figure 7). At medium
loads, cycles will be skipped and the current limit will be
reduced (Figure8). At very light loads, the current limit will be
reduced even further (Figure 9). Only a small percentage of
cycles will occur to satisfy the power consumption of the power
supply.

The response time of the TinySwitch-II ON/OFF control scheme
is very fast compared to normal PWM control. This provides
tight regulation and excellent transient response.

Power Up/Down

The TinySwitch-II requires only a 0.1 µF capacitor on the
BYPASS pin. Because of its small size, the time to charge this
capacitor is kept to an absolute minimum, typically 0.6 ms. Due
to the fast nature of the ON/OFF feedback, there is no overshoot
at the power supply output. When an external resistor (2 MΩ) is
connected from the positive DC input to the EN/UV pin, the power
MOSFET switching will be delayed during power-up
until the DC line voltage exceeds the threshold (100 V). Figures
10 and 11 show the power-up timing waveform of TinySwitch-II

V

EN

CLOCK

D

MAX

I

DRAIN

V

DRAIN

PI-2667-090700

Figure 7. TinySwitch-II Operation at Moderately Heavy Loading.

V

EN

CLOCK

D

MAX

I

DRAIN

V

DRAIN

Figure 8. TinySwitch-II Operation at Medium Loading.

PI-2377-091100

B

5

7/01

TNY264/266-268

PI-2381-1030801

0

12

Time (ms)

0

200

400

5
0

10

0

100

200

V

DC-INPUT

V

BYPASS

V

DRAIN

PI-2348-030801

0

.5 1

Time (s)

0

100

200

300

0

100

200

400

V

DC-INPUT

V

DRAIN

V

EN

CLOCK

D

MAX

I

DRAIN

V

DRAIN

PI-2661-072400

Figure 9. TinySwitch-II Operation at Very Light Load.

in applications with and without an external resistor (2 MΩ)
connected to the EN/UV pin.

During power-down, when an external resistor is used, the
power MOSFET will switch for 50 ms after the output loses
regulation. The power MOSFET will then remain off without
any glitches since the under-voltage function prohibits restart
when the line voltage is low.

Figure 12 illustrates a typical power-down timing waveform of
TinySwitch-II. Figure 13 illustrates a very slow power-down
timing waveform of TinySwitch-II as in standby applications.
The external resistor (2 MΩ) is connected to the EN/UV pin in
this case to prevent unwanted restarts.

200

V

100

DC-INPUT

0

Figure 11. TinySwitch-II Power-up without Optional External UV

Resistor Connected to EN/UV Pin.

Figure 12. Normal Power-down Timing (without UV).

200

PI-2383-030801

100

V

DC-INPUT

PI-2395-030801

10

V

5
0

400

200

0

Figure 10. TinySwitch-II Power-up with Optional External UV

6

BYPASS

V

DRAIN

0

12

Time (ms)

Resistor (2 MΩ) Connected to EN/UV Pin.

B
7/01

0

400
300

200

100

0

0

V

DRAIN

2.5 5

Time (s)

Figure 13. Slow Power-down Timing with Optional External

Ω

) UV Resistor Connected to EN/UV Pin.

(2 M

85-265

VAC

D1

1N4005

RF1

8.2 Ω

Fusible

D3

1N4005

D2

1N4005

D4

1N4005

C1

3.3 µF
400 V

R1

1.2 kΩ

L1

2.2 mH

C3

R2

200 kΩ

C2

3.3 µF
400 V

2.2 nF

D6

1N4937

U1

TNY264

TinySwitch-II

TNY264/266-268

C8 680 pF

Y1 Safety

U2

LTV817

Shield

D5

1N5819

Q1

2N3904

R9

47 Ω

C7

10 µF

10 V

C5

330 µF

16 V

100 Ω

R3

22 Ω

R4

1.2 Ω

1/2 W

R7

R6

1 Ω

1/2 W

L2

3.3 µH

C6

100 µF

35 V
R8

270 Ω

VR1

BZX79-

B3V9

3.9 V

+ 5 V

500 mA

RTN

PI-2706-052301

T1

18

45

D

EN/UV
BP

S

C3

0.1 µF

Figure 14. 2.5 W Constant Voltage, Constant Current Battery Charger with Universal Input (85-265 VAC).

The TinySwitch-II does not require a bias winding to provide

Application Examples

power to the chip, because it draws the power directly from the
DRAIN pin (see Functional Description above). This has two
main benefits. First, for a nominal application, this eliminates
the cost of a bias winding and associated components.
Secondly, for battery charger applications, the current-voltage
characteristic often allows the output voltage to fall close to
zero volts while still delivering power. This type of application
normally requires a forward-bias winding which has many
more associated components. With TinySwitch-II, neither are
necessary. For applications that require a very low no-load
power consumption (50 mW), a resistor from a bias winding to
the BYPASS pin can provide the power to the chip. The
minimum recommended current supplied is 750 µA. The
BYPASS pin in this case will be clamped at 6.3 V. This method
will eliminate the power draw from the DRAIN pin, thereby
reducing the no-load power consumption and improving full­load efficiency.

The TinySwitch-II is ideal for low cost, high efficiency power
supplies in a wide range of applications such as cellular phone
chargers, PC standby, TV standby, AC adapters, motor control,
appliance control and ISDN or a DSL network termination. The
132 kHz operation allows the use of a low cost EE13 or EF12.6
core transformer while still providing good efficiency. The
frequency jitter in TinySwitch-II makes it possible to use a
single inductor (or two small resistors for under 3 W applications
if lower efficiency is acceptable) in conjunction with two input
capacitors for input EMI filtering. The auto-restart function
removes the need to oversize the output diode for short circuit
conditions allowing the design to be optimized for low cost and
maximum efficiency. In charger applications, it eliminates the
need for a second optocoupler and Zener diode for open loop
fault protection. Auto-restart also saves the cost of adding a fuse
or increasing the power rating of the current sense resistors to
survive reverse battery conditions. For applications requiring

Current Limit Operation

Each switching cycle is terminated when the DRAIN current
reaches the current limit of the TinySwitch-II. Current limit
operation provides good line ripple rejection and relatively
constant power delivery independent of input voltage.

under-voltage lock out (UVLO), such as PC standby, the

TinySwitch-II eliminates several components and saves cost.
TinySwitch-II is well suited for applications that require

constant voltage and constant current output. As TinySwitch-II
is always powered from the input high voltage, it therefore
does not rely on bias winding voltage. Consequently this greatly

BYPASS Pin Capacitor

The BYPASS pin uses a small 0.1 µF ceramic capacitor for

simplifies designing chargers that must work down to zero volts
on the output.

decoupling the internal power supply of the TinySwitch-II.

7/01

B

7

TNY264/266-268

2.5 W CV/CC Cell-Phone Charger

As an example, Figure 14 shows a TNY264 based 5 V, 0.5 A,
cellular phone charger operating over a universal input range
(85-265 VAC). The inductor (L1) forms a π-filter in conjunction
with C1 and C2. The resistor R1 damps resonances in the
inductor L1. Frequency jittering operation of TinySwitch-II
allows the use of a simple π-filter described above in combination
with a single low value Y1-capacitor (C8) to meet worldwide
conducted EMI standards. The addition of a shield winding in
the transformer allows conducted EMI to be met even with the
output capacitively earthed (which is the worst case condition
for EMI). The diode D6, capacitor C3 and resistor R2 comprise
the clamp circuit, limiting the leakage inductance turn-off
voltage spike on the TinySwitch-II DRAIN pin to a safe value.
The output voltage is determined by the sum of the optocoupler
U2 LED forward drop (~1 V), and Zener diode VR1 voltage.
Resistor R8 maintains a bias current through the Zener diode to
ensure it is operated close to the Zener test current.

A simple constant current circuit is implemented using the V
of transistor Q1 to sense the voltage across the current sense
resistor R4. When the drop across R4 exceeds the VBE of
transistor Q1, it turns on and takes over control of the loop by
driving the optocoupler LED. Resistor R6 assures sufficient
voltage to keep the control loop in operation down to zero volts
at the output. With the output shorted, the drop across R4 and
R6 (~1.2 V) is sufficient to keep the Q1 and LED circuit active.
Resistors R7 and R9 limit the forward current that could be
drawn through VR1 by Q1 under output short circuit conditions,
due to the voltage drop across R4 and R6.

10 and 15 W PC Standby Circuits

Figures 15 and 16 show examples of circuits for PC standby
applications. They both provide two outputs: an isolated 5 V
and a 12V primary referenced output. The first, using TNY266P,
provides 10W, and the second, using TNY267P, 15 W of
output power. Both operate from an input range of 140 to
375VDC, corresponding to a 230 VAC or 100/115 VAC with
doubler input. The designs take advantage of the line under­voltage detect, auto-restart and higher switching frequency of
TinySwitch-II. Operation at 132 kHz allows the use of a smaller
and lower cost transformer core, EE16 for 10 W and EE22 for
15 W. The removal of pin 6 from the 8 pin DIP TinySwitch-II
packages provides a large creepage distance which improves
reliability in high pollution environments such as fan cooled
PC power supplies.

Capacitor C1 provides high frequency decoupling of the high
voltage DC supply, only necessary if there is a long trace length
from the DC bulk capacitors of the main supply. The line sense
resistors R2 and R3 sense the DC input voltage for line under­voltage. When the AC is turned off, the under-voltage detect
feature of the TinySwitch-II prevents auto-restart glitches at the
output caused by the slow discharge of large storage capacitance
in the main converter. This is achieved by preventing the
TinySwitch-II from switching when the input voltage goes
below a level needed to maintain output regulation, and keeping
it off until the input voltage goes above the under-voltage
threshold, when the AC is turned on again. With R2 and R3,
giving a combined value of 4 MΩ, the power up under-voltage
threshold is set at 200 VDC, slightly below the lowest required
operating DC input voltage, for start-up at 170 VAC, with
doubler. This feature saves several components needed to
implement the glitch-free turn-off compared with discrete or
TOPSwitch-II based designs. During turn-on the rectified DC
input voltage needs to exceed 200 V under-voltage threshold

BE

for the power supply to start operation. But, once the power
supply is on it will continue to operate down to 140 V rectified
DC input voltage to provide the required hold up time for the
standby output.

The auxiliary primary side winding is rectified and filtered by
D2 and C2 to create a 12 V primary bias output voltage for the
main power supply primary controller. In addition, this voltage
is used to power the TinySwitch-II via R4. Although not
necessary for operation, supplying the TinySwitch-II externally
reduces the device quiescent dissipation by disabling the internal
drain derived current source normally used to keep the BYPASS
pin capacitor (C3) charged. An R4 value of 10 kΩ provides
600 µA into the BYPASS pin, which is slightly in excess of the
current consumption of TinySwitch-II. The excess current is
safely clamped by an on-chip active Zener diode to 6.3 V.

The secondary winding is rectified and filtered by D3 and C6.
For a 15W design an additional output capacitor, C7, is
required due to the larger secondary ripple currents compared
to the 10W PC standby design. The auto-restart function limits
output current during short circuit conditions, removing the
need to over rate D3. Switching noise filtering is provided by L1
and C8. The 5V output is sensed by U2 and VR1. R5 is used to
ensure that the Zener diode is biased at its test current.

The Zener regulation method provides sufficient accuracy (typ.
± 3%). This is possible because TinySwitch-II limits the
dynamic range of the optocoupler LED current, allowing the
Zener diode to operate at near constant bias current.

B

8

7/01

TNY264/266-268

PERFORMANCE SUMMARY
Continuous Output Power: 10.24 W

Efficiency: ≥ 75%

140-375

VDC

INPUT

0.01 µF

U1

TNY266P

+12 VDC
20 mA

C2

82 µF

35 V

0 V

Figure 15. 10 W PC Standby Supply.

C1

1 kV

1N4148

D

S

D2

10 kΩ

EN
BP

TinySwitch-II

R4

C3

0.1 µF
50 V

R1

200 kΩ

R2

2 MΩ

R3

2 MΩ

C5

2.2 nF
1 kV

D1

1N4005

C4

1 nF Y1

1

2

4

5

T1

D3

1N5822

10

8

U2

SFH615-2

C6

1000 µF

10 V

VR1
BZX79B3V9

L1

10 µH

2 A

C8

470 µF

10 V

R5

150 Ω

+5 V
(± 5%)
2 A

RTN

PI-2713-040901

PERFORMANCE SUMMARY
Continuous Output Power: 15.24 W

Efficiency: ≥ 78%

140-375

VDC

INPUT

U1

TNY267P

C1

0.01 µF
1 kV

+12 VDC
20 mA

C2

82 µF

35 V

0 V

Figure 16. 15 W PC Standby Supply.

1N4148

D

S

D2

10 kΩ

EN
BP

TinySwitch-II

R4

C3

0.1 µF
50 V

R1

100 kΩ

R2

2 MΩ

R3

2 MΩ

C5

2.2 nF
1 kV

D1

1N4005

C4

1 nF Y1

1

2

4

5

T1

D3

SB540

10

8

U2

SFH615-2

C6

1000 µF

10 V

VR1
BZX79B3V9

C7

1000 µF

10 V

R5

150 Ω

L1

10 µH

3 A

C8

470 µF

10 V

+5 V
(± 5%)
3 A

RTN

PI-2712-040901

7/01

B

9

TNY264/266-268

Key Application Considerations

TinySwitch-II

Table 2 compares the features and performance differences
between the TNY254 device of the TinySwitch family with the
TinySwitch-II family of devices. Many of the new features

Function

Switching Frequency 44 kHz ±10% (@25 °C) 132 kHz ±6% (@25 °C) • Smaller transformer for low cost
and Tolerance • Ease of design
Temperature Variation +8% +2% • Manufacturability
(0 - 100 °C)** • Optimum design for lower cost

Active Frequency Jitter N/A* ±4 kHz • Lower EMI minimizing filter

Transformer N/A* Yes - built into • Practically eliminates audible noise
Audible Noise controller with ordinary dip varnished
Reduction transformer – no special construction

Line UV Detect N/A* Single resistor • Prevents power on/off glitches

Current Limit Tolerance ± 11% (@25 °C) ± 7% (@25 °C) • Increases power capability and
Temperature Variation -8% 0% simplifies design for high volume
(0 - 100 °C)** manufacturing

vs.

TinySwitch

eliminate the need for or reduce the cost of circuit components.
Other features simplify the design and enhance performance.

TinySwitch TinySwitch-II TinySwitch-II

TNY254 TNY264/266-268

component costs

or gluing required

programmable

Advantages

Auto-Restart N/A* 6% effective on-time • Limits output short-circuit current to

less than full load current

- No output diode size penalty.

• Protects load in open loop fault
conditions

- No additional components

required

BYPASS Pin N/A* Internally clamped to • Allows TinySwitch-II to be powered
Zener Clamp 6.3 V from a low voltage bias winding to

improve efficiency and to reduce
on-chip power dissipation

DRAIN Creepage at 0.037” / 0.94 mm 0.137” / 3.48 mm • Greater immunity to arcing as a
Package result of dust, debris or other

contaminants build-up

*Not available. ** See typical performance curves.

Table 2. Comparison Between TinySwitch and TinySwitch-II.

Design

Output Power

Table 1 (front page) shows the practical maximum continuous
output power levels that can be obtained under the following
conditions:

1. The minimum DC input voltage is 90 V or higher for
85 VAC input, or 240 V or higher for 230 VAC input or
115 VAC input with a voltage doubler. This corresponds to
a filter capacitor of 3 µF/W for universal input and 1 µF/W
for 230 or 115 VAC with doubler input.

10

B
7/01

TNY264/266-268

2. A secondary output of 5 V with a Schottky rectifier diode.

3. Assumed efficiency of 77% (TNY267 & TNY268), 75%
(TNY266) and 73% (TNY264).

4. The parts are board mounted with SOURCE pins soldered
to sufficient area of copper to keep the die temperature at or
below 100 °C.

In addition to the thermal environment (sealed enclosure,
ventilated, open frame, etc.), the maximum power capability of
TinySwitch-II in a given application depends on transformer
core size and design (continuous or discontinuous), efficiency,
minimum specified input voltage, input storage capacitance,
output voltage, output diode forward drop, etc., and can be
different from the values shown in Table 1.

Audible Noise

The TinySwitch-II practically eliminates any transformer audio
noise using simple ordinary varnished transformer construction.
No gluing of the cores is needed. The audio noise reduction is
accomplished by the TinySwitch-II controller reducing the
current limit in discrete steps as the load is reduced. This
minimizes the flux density in the transformer when switching
at audio frequencies.

Worst Case EMI & Efficiency Measurement

Since identical TinySwitch-II supplies may operate at several
different frequencies under the same load and line conditions,
care must be taken to ensure that measurements are made under
worst case conditions. When measuring efficiency or EMI
verify that the TinySwitch-II is operating at maximum frequency
and that measurements are made at both low and high line input
voltages to ensure the worst case result is obtained.

Layout

Single Point Grounding

Use a single point ground connection at the SOURCE pin for
the BYPASS pin capacitor and the Input Filter Capacitor
(see Figure 17).

Thermal Considerations

Copper underneath the TinySwitch-II acts not only as a single
point ground, but also as a heatsink. The hatched areas shown
in Figure17 should be maximized for good heat sinking of
TinySwitch-II and the same applies to the output diode.

EN/UV pin

If a line under-voltage detect resistor is used then the resistor
should be mounted as close as possible to the EN/UV pin to
minimize noise pick up.

The voltage rating of a resistor should be considered for the
under-voltage detect (Figure 15: R2, R3) resistors. For 1/4W
resistors, the voltage rating is typically 200V continuous,
whereas for 1/2W resistors the rating is typically 400V
continuous.

Y-Capacitor

The placement of the Y-capacitor should be directly from the
primary bulk capacitor positive rail to the common/return
terminal on the secondary side. Such placement will maximize
the EMI benefit of the Y-capacitor and avoid problems in
common-mode surge testing.

Optocoupler

It is important to maintain the minimum circuit path from the
optocoupler transistor to the TinySwitch-II EN/UV and
SOURCE pins to minimize noise coupling.

The EN/UV pin connection to the optocoupler should be kept
to an absolute minimum (less than 12.7 mm or 0.5 in.), and
this connection should be kept away from the DRAIN pin
(minimum of 5.1 mm or 0.2 in.).

Output Diode

For best performance, the area of the loop connecting the
secondary winding, the Output Diode and the Output Filter
Capacitor, should be minimized. See Figure17 for optimized
layout. In addition, sufficient copper area should be provided
at the anode and cathode terminals of the diode for adequate
heatsinking.

Primary Loop Area

The area of the primary loop that connects the input filter
capacitor, transformer primary and TinySwitch-II together
should be kept as small as possible.

Primary Clamp Circuit

A clamp is used to limit peak voltage on the DRAIN pin at turn­off. This can be achieved by using an RCD clamp (as shown in
Figure 14). A Zener and diode clamp (200 V) across the
primary or a single 550V Zener clamp from DRAIN to SOURCE
can also be used. In all cases care should be taken to minimize
the circuit path from the clamp components to the transformer
and TinySwitch-II.

Input and Output Filter Capacitors

There are constrictions in the traces connected to the input and
output filter capacitors. These constrictions are present for two
reasons. The first is to force all the high frequency currents to
flow through the capacitor (if the trace were wide then it could
flow around the capacitor). Secondly, the constrictions minimize
the heat transferred from the TinySwitch-II to the input filter
capacitor and from the secondary diode to the output filter
capacitor. The common/return (the negative output terminal in
Figure17) terminal of the output filter capacitor should be
connected with a short, low impedance path to the secondary
winding. In addition, the common/return output connection

B

11

7/01

TNY264/266-268

+

Input Filter Capacitor

Safety Spacing

Y1-

Capacitor

Output Filter Capacitor

HV

—

PRI

T

r
a
n
s

f

D

S

o

r

m

TOP VIEW

C

BP

TinySwitch-II

BP

S

EN/UV

e

r

Opto-

coupler

DC

Out

Maximize hatched copper
areas ( ) for optimum
heat sinking

Figure 17. Recommended Circuit Board Layout for TinySwitch-II with Under-Voltage Lock Out Resistor.

should be taken directly from the secondary winding pin and not
from the Y-capacitor connection point.

PC Board Cleaning

Power Integrations does not recommend the use of “no clean”
flux.

SEC

+—

PI-2707-012901

For the most up-to-date information visit the
PI Web site at: www.powerint.com

B

12

7/01

TNY264/266-268

ABSOLUTE MAXIMUM RATINGS

DRAIN Voltage ....................................... - 0.3 V to 700 V

Peak DRAIN Current (TNY264) ...........................400 mA

Peak DRAIN Current (TNY266) ...........................560 mA

Peak DRAIN Current (TNY267) ...........................720 mA

Peak DRAIN Current (TNY268) ...........................880 mA

EN/UV Voltage............................................ - 0.3 V to 9 V

EN/UV Current ......................................................100 mA

THERMAL IMPEDANCE

Thermal Impedance: P/G Package:

(θJA) ........ 45 °C/W

(θJC)

(1)

.......................... 11 °C/W

(2)

; 35 °C/W

Conditions

Parameter

Symbol

SOURCE = 0 V; TJ = -40 to 125 °C

See Figure 18

(Unless Otherwise Specified)

CONTROL FUNCTIONS

(1)

BYPASS Voltage.......................................... -0.3 V to 9 V

Storage Temperature ..................................... -65 to 150 °C

Operating Junction Temperature
Lead Temperature

(3)

................................................ 260 °C

(2)

................-40 to 150 °C

Notes:

1. All voltages referenced to SOURCE, TA = 25 °C.

2. Normally limited by internal circuitry.

3. 1/16" from case for 5 seconds.

Notes:

(3)

1. Measured on the SOURCE pin close to plastic interface.

2. Soldered to 0.36 sq. inch (232 mm

2

), 2oz. (610 gm/m2) copper clad.

3. Soldered to 1 sq. inch (645 mm2), 2oz. (610 gm/m2) copper clad.

Min Typ Max

Units

Output
Frequency

Maximum
Duty Cycle

EN/UV Pin Turnoff
Threshold Current

EN/UV Pin
Voltage

DRAIN
Supply Current

BYPASS Pin
Charge Current

BYPASS Pin
Voltage

DC

f

I

V

I

I

V

OSC

DIS

EN

I

S1

I

S2

CH1

CH2

BP

MAX

TJ = 25 °C

See Figure 4

S1 Open

T

= -40 °C to 125 °C

J

I

EN/UV

I

EN/UV

V

EN/UV

EN/UV Open

(MOSFET

Switching)

See Note A, B

VBP = 0 V,

TJ = 25 °C

See Note C, D

VBP = 4 V,

TJ = 25 °C

See Note C, D

See Note C

Average

Peak-Peak Jitter

= -125 µA

= 25 µA

= 0 V

TNY264

TNY266
TNY267
TNY268

TNY264

TNY266-268

TNY264

TNY266-268

124 132 140

8

62 65 68

-300 -240 -170

0.4 1.0 1.5

1.3 2.3 2.7
320 430 500

170 225 270

200 265 320
240 315 380
285 380 460

-5.5 -3.3 -1.8

-7.5 -4.6 -2.5

-3.8 -2.0 -1.0

-4.5 -3.0 -1.5

5.6 5.85 6.15

kHz

%

µA

V

µA

µA

mA

V

BYPASS Pin
Voltage Hysteresis

V

BPH

0.80 0.95 1.20

7/01

V

B

13

TNY264/266-268

Parameter Symbol

CONTROL FUNCTIONS (cont.)

Conditions

SOURCE = 0 V; TJ = -40 to 125 °C

See Figure 18

(Unless Otherwise Specified)

Min

Typ Max

Units

EN/UV Pin Line
Under-voltage
Threshold

CIRCUIT PROTECTION

Current Limit

Initial Current
Limit

Leading Edge
Blanking Time

Current Limit
Delay

I

I

LIMIT

I

t

LUV

INIT

LEB

t

ILD

TNY264

TJ = 25 °C

TNY266

TJ = 25 °C

TNY267

TJ = 25 °C

TNY268

TJ = 25 °C

See Figure 21

See Note F, G

TJ = 25 °C

di/dt = 50 mA/µs

di/dt = 70 mA/µs

di/dt = 90 mA/µs

di/dt = 110 mA/µs

TJ = 25 °C
TJ = 25 °C

See Note F

TJ = 25 °C

See Note E

See Note E

See Note E

See Note E

49

233 250 267

325 350 375

419 450 481

512 550 588

0.65 x

I

LIMIT (MIN)

170 215

150

5444

µA

mA

mA

ns

ns

Thermal Shutdown
Temperature

Thermal Shutdown
Hysteresis

OUTPUT

ON-State
Resistance

OFF-State
Leakage

B

14

7/01

R

DS(ON)

I

DSS

TNY264

ID = 25 mA

TNY266

ID = 35 mA

TNY267

ID = 45 mA

TNY268

ID = 55 mA

VBP = 6.2 V,
V

= 0 V,

EN/UV

V

= 560 V,

DS

TJ = 125 °C

TJ = 25 °C

TJ = 100 °C

TJ = 25 °C

TJ = 100 °C

TJ = 25 °C

TJ = 100 °C

TJ = 25 °C

TJ = 100 °C

TNY264
TNY266

TNY267
TNY268

125 135 150

70

28 32

42 48
14 16
21 24

7.8 9.0

11.7 13.5

5.2 6.0

7.8 9.0

50

100

°C

°C

Ω

µA

Conditions

Parameter Symbol SOURCE = 0 V; T

See Figure 18

(Unless Otherwise Specified)

OUTPUT (cont.)

= -40 to 125 °C

J

Min

Typ

TNY264/266-268

Max

Units

Breakdown
Voltage

Rise Time

BV

t

DSS

R

I

VBP = 6.2 V, V

= 100 µA, TJ = 25 °C

DS

Measured in a Typical Flyback

Converter Application

Fall Time

t

F

Drain Supply
Voltage

Output EN/UV
Delay

Output Disable
Setup Time

Auto-Restart
ON-Time

Auto-Restart
Duty Cycle

NOTES:

A. Total current consumption is the sum of IS1 and I

and the sum of IS2 and I

t

EN/UV

t

DST

t

AR

DC

AR

when EN/UV pin is open (MOSFET switching).

DSS

See Figure 20

= 0 V,

EN/UV

700

50

50

50

10

0.5

TJ = 25 °C

See Note H

50

5.6

when EN/UV pin is shorted to ground (MOSFET not switching)

DSS

V

ns

ns

V

µs

µs

ms

%

B Since the output MOSFET is switching, it is difficult to isolate the switching current from the supply current at the

DRAIN. An alternative is to measure the BYPASS pin current at 6.1 V.
C. BYPASS pin is not intended for sourcing supply current to external circuitry.
D. See typical performance characteristics section for BYPASS pin start-up charging waveform.
E. For current limit at other di/dt values, refer to Figure 25.
F. This parameter is derived from characterization.
G. This parameter is derived from the change in current limit measured at 1X and 4X of the di/dt shown in the I

LIMIT

specification.
H. Auto-restart on time has the same temperature characteristics as the oscillator (inversely proportional to

frequency).

B

15

7/01

TNY264/266-268

EN/UV

D

S

S

S

BPS

NOTE: This test circuit is not applicable for current limit or output characteristic measurements.

Figure 18. TinySwitch-II General Test Circuit.

t

2

t

1

HV

90%

DRAIN

VOLTAGE

10%

0 V

Figure 19. TinySwitch-II Duty Cycle Measurement.

D =

0.1 µF

90%

t

1

t

2

PI-2048-033001

2 MΩ

470 Ω

5 W

S2

470 Ω

S1

50 V

10 V

150 V

DC

MAX

(internal signal)

t

P

EN/UV

t

V

DRAIN

1

tP =

f

OSC

Figure 20. TinySwitch-II Output Enable Timing.

EN/UV

PI-2686-101700

PI-2364-012699

16

B
7/01

t

(Blanking Time)

1.3

LEB

1.2

1.1

1.0

0.9

0.8

0.8

0.7

0.6

0.5

I

INIT(MIN)

I

LIMIT(MIN)

@ 100 °C

0.4

0.3

0.2

DRAIN Current (normalized)

0.1
0

012 6 83

45 7

Time (µs)

Figure 21. Current Limit Envelope.

PI-2362-052301

Typical Performance Characteristics

TNY264/266-268

1.1

1.0

Breakdown Voltage

(Normalized to 25 °C)

0.9

-50 -25 0 25 50 75 100 125 150

Junction Temperature (°C)

Figure 22. Breakdown vs. Temperature.

1.2

1

0.8

0.6

0.4

Current Limit

(Normalized to 25 °C)

0.2

TNY264/266
TNY267
TNY268

PI-2213-012301

PI-2714-031401

1.2

1.0

0.8

0.6

0.4

Output Frequency

Normalized to 25 °C

0.2

0

-50 -25 0 25 50 75 100 125

Junction Temperature (°C)

Figure 23. Frequency vs. Temperature.

1.4

1.2

1.0

0.8

Normalized

0.6

TNY264 50 mA/µs 250 mA

0.4

Normalized Current Limit

0.2

TNY266 70 mA/µs 350 mA
TNY267 90 mA/µs 450 mA
TNY268 110 mA/µs 550 mA

di/dt = 1

Normalized

Current

Limit = 1

PI-2680-012301

PI-2697-012301

0

-50

0 50 100 150

Temperature (°C)

Figure 24. Current Limit vs. Temperature.

7

6
5
4

3
2
1

BYPASS Pin Voltage (V)

0

0.2 0.4 0.6 0.8

0

Time (ms)

Figure 26. Bypass Pin Start-up Waveform.

1.0

PI-2240-012301

0

1234

Normalized di/dt

Figure 25. Current Limit vs. di/dt.

300

T

=25 °C

CASE

=100 °C

T

250

200

150

Scaling Factors:
TNY264 1.0

TNY266 2.0
TNY267 3.5
TNY268 5.5

CASE

100

Drain Current (mA)

50

0

0246810

Drain Voltage (V)

Figure 27. Output Characteristic.

PI-2221-031401

B

7/01

17

TNY264/266-268

Typical Performance Characteristics (cont.)

1000

100

10

Drain Capacitance (pF)

1

0 100 200 300 400 500 600

Drain Voltage (V)

Figure 28. C

vs. Drain Voltage.

OSS

Scaling Factors:

TNY264 1.0
TNY266 2.0
TNY267 3.5
TNY268 5.5

1.2

1.0

0.8

PI-2683-031401

35

30

25

20

15

Power (mW)

10

5

0

0 200 400 600

Scaling Factors:
TNY264 1.0

TNY266 2.0
TNY267 3.5
TNY268 5.5

Drain Voltage (V)

Figure 29. Drain Capacitance Power.

PI-2698-012301

PI-2225-031401

0.6

0.4

(Normalized to 25 °C)

0.2

Under-Voltage Threshold

0

-50 -25 0 25 50 75 100 125

Figure 30. Undervoltage Threshold vs. Temperature.

PART ORDERING INFORMATION

TNY 264 G - TL

Junction Temperature (°C)

TinySwitch Product Family
Series Number
Package Identifier

G Plastic Surface Mount DIP
P Plastic DIP

Package/Lead Options

Blank Standard Configurations

TL Tape & Reel, 1 k pcs minimum, G Package only

18

B
7/01

-E-

.245 (6.22)
.255 (6.48)

Pin 1

-D-

.128 (3.25)
.132 (3.35)

-T­SEATING
PLANE

.100 (2.54) BSC

D S

⊕

.375 (9.53)
.385 (9.78)

.014 (.36)
.022 (.56)

.004 (.10)

T E D S

⊕

.048 (1.22)
.053 (1.35)

.010 (.25) M

.057 (1.45)
.063 (1.60)

(NOTE 6)

0.15 (.38)

MINIMUM

.125 (3.18)
.135 (3.43)

DIP-8B

Notes:

1. Package dimensions conform to JEDEC specification
MS-001-AB (Issue B 7/85) for standard dual-in-line (DIP)
package with .300 inch row spacing.

2. Controlling dimensions are inches. Millimeter sizes are
shown in parentheses.

3. Dimensions shown do not include mold flash or other
protrusions. Mold flash or protrusions shall not exceed
.006 (.15) on any side.

4. Pin locations start with Pin 1, and continue counter-clock­ wise to Pin 8 when viewed from the top. The notch and/or
dimple are aids in locating Pin 1. Pin 6 is omitted.

5. Minimum metal to metal spacing at the package body for
the omitted lead location is .137 inch (3.48 mm).

6. Lead width measured at package body.

7. Lead spacing measured with the leads constrained to be
perpendicular to plane T.

.010 (.25)
.015 (.38)

.300 (7.62) BSC

(NOTE 7)

.300 (7.62)
.390 (9.91)

TNY264/266-268

P08B

PI-2551-101599

-E-

.245 (6.22)
.255 (6.48)

Pin 1

-D-

.128 (3.25)
.132 (3.35)

.032 (.81)
.037 (.94)

D S

.004 (.10)

⊕

.100 (2.54) (BSC)

.375 (9.53)
.385 (9.78)

.048 (1.22)
.053 (1.35)

.372 (9.45)
.388 (9.86)

E S

⊕

.057 (1.45)
.063 (1.60)

(NOTE 5)

.009 (.23)

.010 (.25)

SMD-8B

Heat Sink is 2 oz. Copper

As Big As Possible

Pin 1

Solder Pad Dimensions

.004 (.10)
.012 (.30)

.046

.060

.086

.186

.004 (.10)

.036 (0.91)
.044 (1.12)

.286

.060

.046

.080

Notes:

1. Controlling dimensions are
inches. Millimeter sizes are
shown in parentheses.

2. Dimensions shown do not
include mold flash or other
protrusions. Mold flash or
protrusions shall not exceed
.006 (.15) on any side.

.420

3. Pin locations start with Pin 1,
and continue counter-clock
Pin 8 when viewed from the
top. Pin 6 is omitted.

4. Minimum metal to metal
spacing at the package body
for the omitted lead location
is .137 inch (3.48 mm).

5. Lead width measured at
package body.

6. D and E are referenced
datums on the package
body.

°

°

8

0 -

PI-2546-040501

G08B

7/01

B

19

TNY264/266-268

Revision

A
B

Notes

-

1) Corrected first page spacing and sentence in description describing innovative design.

2) Corrected Frequency Jitter in Figure 4 and Frequency Jitter in Parameter Table.

3) Added last sentence to Over Temperature Protection section.

4) Clarified detecting when there is no external resistor connected to the EN/UV pin.

5) Corrected Figure 6 and its description in the text.

6) Corrected formatting, grammer and style errors in text and figures.

7) Corrected and moved Worst Case EMI & Efficiency Measurement section

8) Added PC Board Cleaning section.

9) Replaced Figure 21 and SMD-8B Package Drawing.

Date
3/01

7/01

For the latest updates, visit our Web site: www.powerint.com
Power Integrations reserves the right to make changes to its products at any time to improve reliability or manufacturability.
Power Integrations does not assume any liability arising from the use of any device or circuit described herein, nor does it
convey any license under its patent rights or the rights of others.

The PI Logo,

TOPSwitch, TinySwitch

and

EcoSmart

are registered trademarks of Power Integrations, Inc.

©Copyright 2001, Power Integrations, Inc.

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Customer Service:
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Power Integrations (Europe) Ltd.
Centennial Court
Easthampstead Road
Bracknell
Berkshire, RG12 1YQ
United Kingdom
Phone: [phone]
Fax: [phone]

e-mail: [e-mail]

JAPAN

Power Integrations, K.K.
Keihin-Tatemono 1st Bldg.
12-20 Shin-Yokohama 2-Chome
Kohoku-ku, Yokohama-shi
Kanagawa 222-0033, Japan
Phone: [phone]
Fax: [phone]

e-mail: [e-mail]

TAIWAN

Power Integrations
International Holdings, Inc.
17F-3, No. 510
Chung Hsiao E. Rd.,
Sec. 5,
Taipei, Taiwan 110, R.O.C.
Phone: [phone]
Fax: [phone]

e-mail: [e-mail]

INDIA (Technical Support)

Innovatech
#1, 8th Main Road
Vasanthnagar
Bangalore, India 560052
Phone: [phone]
Fax: [phone]

e-mail: [e-mail]

CHINA

Power Integrations
International Holdings, Inc.
Rm# 1705, Bao Hua Bldg.
1016 Hua Qiang Bei Lu
Shenzhen, Guangdong 518031
China
Phone: [phone]
Fax: [phone]

e-mail: [e-mail]

APPLICATIONS HOTLINE

World Wide [phone]

APPLICATIONS FAX

World Wide [phone]

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