Datasheet TEA1064AT, TEA1064A Datasheet (Philips)

INTEGRATED CIRCUITS

DATA SH EET

TEA1064A

Low voltage versatile telephone
transmission circuit with dialler
interface and transmit level
dynamic limiting

Product specification
File under Integrated Circuits, IC03A

March 1994

Philips Semiconductors Product specification

Low voltage versatile telephone transmission circuit
with dialler interface and transmit level dynamic limiting

GENERAL DESCRIPTION

The TEA1064A is a bipolar integrated circuit that performs
all the speech and line interface functions required in fully
electronic telephone sets. It performs electronic switching
between dialling and speech and has a powerful DC
supply for peripheral circuits. The IC operates at line
voltages down to 1.8 V DC (with reduced performance) to
facilitate the use of more telephone sets connected in
parallel. The transmit signal on the line is dynamically
limited (speech-controlled) to prevent distortion at high
transmit levels of both the sending signal and the sidetone.

FEA TURES

• Low DC line voltage; operates down to 1.8 V (excluding
polarity guard)

• Voltage regulator with low voltage drop and adjustable
static resistance

• DC line voltage adjustment facility

• Provides a supply for external circuits in two options:

unregulated supply, regulated line voltage;
stabilized supply, line voltage varies with supply

current

• Dynamic limiting (speech-controlled) in transmit
direction prevents distortion of line signal and sidetone

• Symmetrical high-impedance inputs (64 kΩ) for
dynamic, magnetic or piezo-electric microphones

• Asymmetrical high-impedance input (32 kΩ) for electret
microphones

• DTMF signal input

• Confidence tone in the earpiece during DTMF dialling

• Mute input for disabling speech during pulse or DTMF

dialling

• Power-down input for improved performance during
pulse dial or register recall (flash)

• Receiving amplifier for magnetic, dynamic or
piezo-electric earpieces

• Large amplification setting ranges on microphone and
earpiece amplifiers

• Line loss compensation (line current dependent) for
microphone and earpiece amplifiers (not used for DTMF
amplifier)

• Gain control curve adaptable to exchange supply

• Automatic disabling of the DTMF amplifier in

extremely-low voltage conditions

• Microphone MUTE function available with switch

PACKAGE OUTLINES

TEA1064A :20-lead DIL; plastic (SOT146).
TEA1064AT:20-lead mini-pack; plastic (SO20;

SOT163A).

Notes

1. SOT146-1; 1998 Jun 18.

2. SOT163-1; 1998 Jun 18.

(2)

TEA1064A

(1)

March 1994 2

Philips Semiconductors Product specification

Low voltage versatile telephone transmission circuit
with dialler interface and transmit level dynamic limiting

13

9
8

12

14

15

V

CC1

TEA1064A

dB

SUPPLY AND
REFERENCE

−
+

+

−

+

−
+

−

handbook, full pagewidth

IR

MIC+
MIC−

DTMF

MUTE

PD

TEA1064A

LN

116

6

GAR

5

+

−

QR+

4

QR−

19

V

CC2

2

GAS1

3

GAS2

AGC

CIRCUIT

CURRENT

REFERENCE

1711

18 10 7 20

V

EE

REG AGC STAB

LOW

VOLTAGE

CIRCUIT

START

CIRCUIT

DYNAMIC

LIMITER

DLS/MMUTE

SLPE

MGR056

Fig.1 Block diagram.

March 1994 3

Philips Semiconductors Product specification

Low voltage versatile telephone transmission circuit
with dialler interface and transmit level dynamic limiting

QUICK REFERENCE DATA

PARAMETER CONDITIONS SYMBOL MIN. TYP. MAX. UNIT

Operating ambient temperature
range T
Line current operating range:

normal operation l
with reduced performance l

Internal supply current:

power-down input LOW V
power-down input HIGH V

= 2.8 V I

CC1

= 2.8 V I

CC1

Voltage gain range:

microphone amplifier G
receiving amplifier G

Line loss compensation:

gain control range G
exchange supply voltage
range V
exchange feeding bridge
resistance range R

Maximum output voltage swing

on LN (peak-to-peak value) R15 + R16 = 448 Ω

l

=15mA

line

I

= 2 mA V

p

= 4 mA V

I

p

Regulated line voltage application

R15 = 0 Ω;
R16 = 392 Ω

Supply for peripherals l

DC line voltage l

=15mA

line

I

= 1.4 mA V

p

I

= 2.7 mA;

p

R

REG-SLPE

line

without R
R

REG-SLPE

=20kΩ V

=15mA

REG-SLPE

=20kΩ V

amb

line
line

CC1
CC1

v
v

v

exch

exch

LN(p-p)
LN(p-p)

p

p

V

LN
LN

TEA1064A

−25 −+75 °C

11 − 140
2 − 11 mA

− 1.3 1.6 mA

− 60 82 µA

44 − 52 dB
20 − 45 dB

5.7 6.1 6.5 dB

36 − 60 V

400 − 1000 Ω

3.7 3.95 4.2 V

3.0 3.25 3.5 V

2.5 −−V

2.9 −−V

− 3.57 − V

− 4.57 − V

(1)

mA

March 1994 4

Philips Semiconductors Product specification

Low voltage versatile telephone transmission circuit

TEA1064A

with dialler interface and transmit level dynamic limiting

PARAMETER CONDITIONS SYMBOL MIN. TYP. MAX. UNIT

Stabilized supply voltage application

R15 = 392 Ω;
R16 = 56 Ω

Supply for peripherals l

DC line voltage l

Note

1. For TEA1064AT the maximum line current depends on the heat dissipating qualities of the mounted device.

PINNING

handbook, halfpage

DLS/MMUTE

LN
GAS1
GAS2

QR−
QR+

GAR

MIC−
MIC+

STAB

1
2
3
4
5

TEA1064A

6
7
8
9

10

MGR057

Fig.2 Pinning diagram.

= 15 mA

line

I

= 0 to 4 mA V

p

=15mA

line

I

= 2 mA V

p

I

= 4 mA V

p

SLPE

20

V

19

CC2

18

AGC

17

REG
V

16

CC1

PD

15

MUTE

14

IR

13

DTMF

12

V

11

EE

CC2-SLPE

LN
LN

3.05 3.3 3.55 V

4.2 4.4 4.8 V

4.9 5.1 5.5 V

1 LN positive line terminal
2 GAS1 gain adjustment; transmitting amplifier
3 GAS2 gain adjustment; transmitting amplifier
4QR− inverting output, receiving amplifier
5QR+ non-inverting output, receiving

amplifier
6 GAR gain adjustment; receiving amplifier
7 DLS/

MMUTE

decoupling for transmit amplifier

dynamic and microphone MUTE input
8 MIC− inverting microphone input
9 MIC+ non-inverting microphone input

10 STAB current stabilizer

11 V

EE

negative line terminal

12 DTMF dual-tone multi-frequency input
13 IR receiving amplifier input
14 MUTE mute input
15 PD power-down input
16 V

CC1

internal supply decoupling

17 REG voltage regulator decoupling
18 AGC automatic gain control input
19 V

CC2

reference voltage with respect to SLPE

20 SLPE slope adjustment for DC

curve/reference for peripheral circuits.

March 1994 5

Philips Semiconductors Product specification

Low voltage versatile telephone transmission circuit
with dialler interface and transmit level dynamic limiting

FUNCTIONAL DESCRIPTION

, V

Supplies V

CC1

, LN, SLPE, REG and STAB (Fig.3)

CC2

Power for the TEA1064A and its peripheral circuits is
usually obtained from the telephone line. The IC develops
its own supply voltage at V

and regulates its voltage

CC1

drop. The internal supply requires a decoupling capacitor
between V

and VEE. The internal current stabilizer is

CC1

set by a 3.6 kΩ resistor between STAB and VEE.
The DC current flowing into the set is determined by the

exchange supply voltage V
resistance R

, the subscriber line DC resistance R

exch

, the feeding bridge

exch

line

and the DC voltage (including polarity guard) on the
subscriber set (see Fig.3).

The internal voltage regulator generates a
temperature-compensated reference voltage that is
available between V
[V

ref=VCC2-SLPE

and SLPE

CC2

= 3.3 V (typ.)]. This internal voltage
regulator requires decoupling by a capacitor between REG
and VEE(C3).

The reference voltage can be used to:

• regulate directly the line voltage (stabilized
V

LN-SLPE=VCC2-SLPE

• to stabilize the supply voltage for peripherals.

Regulated line voltage

In this application the V
as shown in Fig.3. This configuration gives a stabilized
voltage across pins LN and SLPE which, applied via the
low-pass filter R16, C15, provides a supply to the
peripherals that is independent of the line current and
depends only on the peripheral supply current.

The value of R16 and the level of the DC voltage V
determine the supply capabilities. In the basic application
R16 = 392 Ω and C15 = 220 µF. The worst-case
peripheral supply current as a function of supply voltage is
shown in Fig.4. To increase the supply capabilities, the DC
voltage V

can be increased by using R

LN-SLPE

or by decreasing the value of R16.

(1) The TEA1064A application with regulated line voltage is the

same as is used for TEA1060/TEA1061, TEA1067 and
TEA1068 integrated circuits.

TEA1064A

(1)

)

pin is connected to the LN pin

CC2

VA(REG-SLPE)

LN-SLPE

handbook, full pagewidth

R

line

R

exch

V

exch

The voltage V
line current determine the supply capabilities and the maximum output swing on
the line (no loop damping is necessary).
The line voltage V

LN-SLPE

LN=Vref

is fixed to V

+ ([I

= 3.3± 0.25 V. Resistor R16 together with the

ref

− 1.55 mA]× R9).

line

I

line

TEA1064A

DC
AC

17

REG

C3 R5

I

SLPE

10

STAB20SLPE

LN
1

R9

Fig.3 Application with regulated line voltage (stabilized V

R1

I

CC1

Ip + 0.25 mA

V

CC1

16

0.25 mA

11

V

EE

V

19

CC2

R16C1

I

p

peripheral

C15

LN-SLPE

circuits

MGR058

).

V

p

March 1994 6

Philips Semiconductors Product specification

Low voltage versatile telephone transmission circuit
with dialler interface and transmit level dynamic limiting

The DC line voltage on LN is:

handbook, halfpage

5

I

p

(mA)

4

3

2

1

0

2

l

= 15mA; R16 = 392Ω; R15 = 0 Ω; valid for MUTE = 0 and 1.

line

Line current has very little influence

R

VA (REG-SLPE)

R

VA (REG-SLPE)

without

34

= 20 kΩ

MGR059

V

(V)

p

Fig.4 Minimum supply current for peripherals (Ip)

as a function of the peripheral supply
voltage (Vp).

The maximum AC output swing on the line at low line
currents is influenced by R16 (limited by current) and the
maximum output swing on the line at high line currents is
influenced by the DC voltage V

LN-SLPE

(limited by voltage).
In both these situations, the internal dynamic limiter in the
sending channel prevents distortion when the microphone
input is overdriven. The maximum AC output swing on LN
is shown in Fig.5; practical values for R16 are from 200 to
600 Ω and this influences both the maximum output swing
at low line currents and the supply capabilities.

The SLPE pin is the ground reference for peripheral
circuits, therefore inputs MUTE, PD and DTMF are also
referenced to SLPE.

Active microphones can be supplied between V

CC1

and
VEE. Low-power circuits that provide only MUTE and/or PD
inputs to the TEA1064A also can be powered from V
However V
DTMF signals to the TEA1064A because V

cannot be used for circuits that provide

CC1

CC1

CC1

is referred

to ground.

VLN=V
VLN=V

LN-SLPE

+ ([I

ref

line

in which

V

= 3.3 V ± 0.25 V is the internal reference voltage

ref

between V

and SLPE; its value can be adjusted by

CC2

external resistor R
R9 = external resistor between SLPE and VEE(20 Ω in

basic application).

With R9 = 20 Ω, this results in:

VLN= 3.57 ± 0.25 V at l
VLN= 4.17 ± 0.3 V at l

R

VA(REG-SLPE)

=33kΩ

VLN= 4.57 ± 0.35 V at l
R

VA(REG-SLPE)

=20kΩ

The preferred value for R9 is 20 Ω. Changing R9
influences microphone gain, DTMF gain, the gain control
characteristics, sidetone, and the DC characteristics
(especially the low voltage characteristics).

In normal conditions, I
static behaviour is equivalent to a voltage regulator diode
with an internal resistance of R9. In the audio frequency
range the dynamic impedance is determined mainly by R1.
The equivalent impedance of the circuit in the audio
frequency range is shown in Fig.6.

The internal reference voltage V
by external resistor R
REG and SLPE. The supply voltage V
a function of R

VA(REG-SLPE)

reference voltage influences the output swing of both
sending and receiving amplifiers.

At line currents below 8 mA (typ.), the DC voltage dropped
across the circuit is adjusted to a lower level automatically
(approximately 1.8 V at 2 mA). This gives the possibility of
operating more telephone sets in parallel with DC line
voltages (excluding polarity guard) down to an absolute
minimum of 1.8 V. At line currents below 8 mA (typ.), the
circuit has limited sending and receiving levels.

.

+ (I

SLPE

− I

CC1

VA

SLPE

VA(REG-SLPE)

TEA1064A

× R9)

− 0.25 × 10−3A] × R9)

=15mA

line

=15mA,

line

= 15 mA,

line

>> (I

in Fig.7. Changing the

+ 0.25 mA) and the

CC1

CC2-SLPE

can be increased

connected between

CC2-SLPE

is shown as

If the line current l

exceeds I

line

+ 0.25 mA, the voltage

CC1

converter shunts the excess current to SLPE via LN;
where I

≈ 1.3 mA, the value required by the IC for

CC1

normal operation.

March 1994 7

Philips Semiconductors Product specification

Low voltage versatile telephone transmission circuit
with dialler interface and transmit level dynamic limiting

(mA)

MGR060

handbook, halfpage

L

eq

V

ref

R9
20 Ω

Fig.6 Equivalent impedance between LN and

VEEin the application with stabilized
V

LN-SLPE

R15 = 0 Ω
Leq=C3×R9 × R
Rp=15kΩ

V

LN(p-p)

(V)

6

4

Ip =
0 mA

2

0

10

2 mA
4 mA

20 30

I

line

handbook, halfpage

Fig.5 Maximum AC output swing on the line as a

function of line current with peripheral
supply current as a parameter: R15 = 0 Ω;
R16 = 392 Ω.

TEA1064A

LN

R

p

REG

C3

4.7 µF

:

R1

V

CC1

C1

V

MGR061

p

EE

handbook, full pagewidth

Fig.7 Internal reference voltage V

and 140 mA.

In the stabilized supply application:

VLN=V

CC2-SLPE

+ ([Ip+ 0.25 × 10−3A] × R15) + ([I

In the unregulated supply application (R15 = 0 Ω):

VLN=V

CC2-SLPE

+ ([I

7.8

V

ref

(V)

6.6

5.4

4.2

3.0
08040 120

CC2-SLPE

− 1.55 × 10−3A] × R9)

line

as a function of resistor R

RVA (REG-SLPE) (kΩ)

− 1.55 × 10−3A] × R9)

line

MGR062

VA(REG-SLPE)

with R

VA

infinite

for line currents between 11

March 1994 8

Philips Semiconductors Product specification

Low voltage versatile telephone transmission circuit
with dialler interface and transmit level dynamic limiting

Stabilized peripheral supply voltage

The configuration shown in Fig.8 provides a stabilized
voltage across pins V

and SLPE for peripheral circuits

CC2

(such as dialling and control circuits); the DC voltage
VLNnow varies with the peripheral supply current.

The V

CC2-SLPE

supply must be decoupled by capacitor
C15. For stable loop operation, resistor R16 (≈ 50 Ω) is
connected between V

and SLPE in series with C15.

CC2

The voltage regulator control loop is completed by resistor
R15 between LN and V

CC2

.

For sets with an impedance of 600 Ω, practical values are:
R15 = 200 to 600 Ω; C15 = 220 µF; C3 = 470 nF. The
ratio R15/R16 ≤ 8 is for stable loop operation with
sufficient phase margin, and R15/R16 ≥ 6 is for
satisfactory set impedance in the audio frequency range.

For sets with complex impedance, the value of C3 and the
ratio R15/R16 are different (further information is given in
the TEA1064A Application Report

(1)

).

the values of external components (especially R15). With
R15 = 392 Ω and R16 = 56 Ω (basic application) the
maximum possible AC output swing on the line as a
function of line current is as shown in Fig.9, the curve
parameter is the peripheral supply current (Ip). Different
values for R15 (from 200 to 600 Ω) maintaining
6 < R15/R16 < 8 give different results (these are described
in the TEA1064A Application Report

TEA1064A

(1)

.

The peripheral supply capability depends mainly on the
available line current, the required AC output swing on the
line, the maximum permitted DC voltage on the line and

handbook, full pagewidth

V

R

exch

exch

R

line

I

line

TEA1064A

DC
AC

17

REG

C3 R5

I

SLPE

10

STAB20SLPE

LN
1

R9

(1) Supplied on request.

R1

I

CC1

Ip + 0.25 mA

V

CC1

16

0.25 mA

11
V

EE

19

R15

V

CC2

R16C1

C15

I

p

peripheral

circuits

V

p

Fig.8 Application with stabilized supply voltage for peripheral circuits: R15 = 392 Ω; R16 = 56 Ω.

March 1994 9

MGR063

Philips Semiconductors Product specification

Low voltage versatile telephone transmission circuit
with dialler interface and transmit level dynamic limiting

The DC line voltage on LN is

VLN=V

LN-SLPE

+ (I

SLPE

× R9).

Therefore

VLN=V

+ ([Ip+ 0.25 × 10−3A] × R15) +

ref

([l

− I

line

− 0.25 × 10−3A] × R9)

CC1

in which:

V

is the internal reference voltage between V

ref

SLPE (the value of V
resistor, RVA). V

ref

can be adjusted by an external

ref

= 3.3 V (typ.) without R

VA

Ipis the supply current used by peripheral circuits
R15 is an external resistor between LN and V

in the basic application)
R9 is an external resistor between SLPE and

VEE(20 Ω in the basic application)

MGR064

Ip = 4 mA

2 mA

0 mA

V

LN(p-p)

(V)

8

6

4

handbook, halfpage

CC2

CC2

(392 Ω

and

5.5

handbook, halfpage

V

LN-SLPE

(V)

5.0

4.5

4.0

3.5

3.0
012 4

V
changing the value of R
The total voltage drop V

can be adjusted between approximately 3.3 and 4.3 V by

CC2-SLPE

Fig.10 Curves showing the typical voltage drop

between LN and SLPE as a function of the
supply current for peripherals with R15 as a
parameter: V
connected).

TEA1064A

MGR065

R15 = 511 Ω

392 Ω

301 Ω

3

Ip (mA)

, this results in a parallel-shift of the curves.

VA

≈ V

LN

CC2-SLPE

+ ([I

LN-SLPE

= 3.3 V (RVAnot

− 1.55 mA] × R9).

line

2

0

10

As different values of R15 and R16 are allowed, different curves
would then apply

20 30

I

(mA)

line

Fig.9 Maximum output swing on line as a function

of line current with the peripheral supply
current as a parameter; R15 = 392 Ω;
R16 = 56 Ω.

The DC voltage V

LN-SLPE

as a function of Ipwith R15 as a
parameter is shown in Fig.10. In the audio frequency
range, the dynamic impedance is determined mainly by
R1. The equivalent impedance in the audio range of the
circuit (Fig.8) is shown in Fig.11.

March 1994 10

MGR066

LN

V

handbook, halfpage

=

ReqR

p

LeqC3 R9× Reqwith Rp15 kΩ=×=

L

eq

R9
20 Ω

R15



----------- 1+



R16

R

eq

C3
470 nF

R1
620 Ω

Fig.11 Equivalent impedance between LN and

VEEat f > 300 Hz in the application with
stabilized supply voltage for peripheral
circuits.

EE

Philips Semiconductors Product specification

Low voltage versatile telephone transmission circuit
with dialler interface and transmit level dynamic limiting

Microphone inputs MIC+ and MIC− and gain pins
GAS1 and GAS2

The TEA1064A has symmetrical microphone inputs, its
input impedance is 64 kΩ (2 × 32 kΩ) and its voltage
amplification is typ. 52 dB with R7 = 68 kΩ. Either
dynamic, magnetic or piezo-electric microphones can be
used, or an electret microphone with a built-in FET buffer.
Arrangements for the microphone types are shown in
Fig.12.

handbook, full pagewidth

MIC+

9

(1)

MIC−

8

The gain of the microphone amplifier is proportional to
external resistor R7 connected between GAS1 and GAS2
and with this it can be adjusted between 44 dB and 52 dB
to suit the sensitivity of the transducer.

An external 100 pF capacitor (C6) is required between
GAS1 and SLPE to ensure stability. A larger value of C6
may be chosen to obtain a first-order low-pass filter with a
cut-off frequency corresponding to the time constant
R7 × C6.

V

CC1

MIC−

MIC+

16

8

9

11

V

EE

TEA1064A

MIC+

9

MIC−

8

MGR067

(a) (b)

(c)

Fig.12 Microphone arrangements: a) magnetic or dynamic microphone, the resistor (1) may be connected to

reduce the terminating impedance, or for sensitive types a resistive attenuator can be used to prevent
overloading the microphone inputs; b) electret microphone; c) piezo-electric microphone.

Dynamic limiter (microphone) pin DLS/MMUTE

A low level at the DLS/MMUTE pin inhibits the microphone
inputs MIC+ and MIC− but has no influence on the
receiving and DTMF amplifiers.
Removing the low level at the DLS/MMUTE pin provides
the normal function of the microphone amplifier after a

means that the maximum output swing on the line will be
higher if the DC voltage dropped across the circuit is
increased.

Fig.14 shows the maximum possible output swing on the
line as a function of the DC voltage drop (V
I

− Ipas a parameter.

line

short time determined by the capacitor connected to
DLS/MMUTE pin. The microphone mute function can be
realised by a simple switch as shown in Fig.13.

To prevent distortion of the transmitted signal, the gain of
the sending amplifier is reduced rapidly when peaks of the
signal on the line exceed an internally-determined
threshold. The time in which gain reduction is effected

handbook, halfpage

R17

3.3 kΩ

DLS/MMUTE

7

(attack time) is very short. The circuit stays in the
gain-reduced condition until the peaks of the sending
signal remain below the threshold level. The sending gain

V

EE

11

then returns to normal after a time determined by the
capacitor connected to DLS/MMUTE (release time).

MGR068

LN-SLPE

) with

The internal threshold adapts automatically to the DC
voltage setting of the circuit (voltage V

LN-SLPE

). This

March 1994 11

Fig.13 Microphone-mute function.

Philips Semiconductors Product specification

Low voltage versatile telephone transmission circuit
with dialler interface and transmit level dynamic limiting

SLPE

MGR069

(V)

5.5

LN-SLPE

handbook, full pagewidth

V

LN(p-p)

(V)

10

8

6

4

2

0

3 3.5 4 4.5 5

VLN-V

Fig.14 Maximum output swing on line as a function of the DC voltage drop V

R15 = 392 Ω; R16 = 56 Ω; or R15 = 0 Ω and R16 = 392 + 56 = 448 Ω.

I

line-Ip

(mA)
25
23
21
19
17
15

13
11

with l

TEA1064A

− Ipas a parameter:

line

The internal threshold level is lowered automatically if the
DC current in the transmit output stage is insufficient. This
prevents distortion of the sending signal in applications
using parallel-connected telephones or telephones
operating over long lines, for example.

Dynamic limiting also considerably improves sidetone
performance in over-drive conditions (less distortion;
limited sidetone level).

Receiving amplifier IR, QR+, QR− and GAR

The receiving amplifier has one input IR and two
complementary outputs, QR+ (non-inverting) and QR−
(inverting). These outputs may be used for single-ended or
differential drive, depending on the type and sensitivity of
the earpiece used (see Fig.15). Gain from IR to QR+ is
typically 31 dB with R4 = 100 kΩ, sufficient for
low-impedance magnetic or dynamic earpieces which are
suitable for single-ended drive. By using both outputs
(differential drive) the gain is increased by 6 dB.
Differential drive can be used when the earpiece
impedance exceeds 450 Ω as with high-impedance
dynamic, magnetic or piezo-electric earpieces.

handbook, full pagewidth

5

4

11

QR+

QR−

V

EE

(a) (b) (c) (d)

QR+

5

QR−

4

5

4

QR+

QR−

(1)

5

4

QR+

QR−

(2)

MGR070

Fig.15 Alternative receiver arrangements: a) dynamic earpiece with an impedance less than 450 Ω; b) dynamic

earpiece with an impedance more than 450 Ω; c) magnetic earpiece with an impedance more than 450 Ω,
resistor (1) may be connected to prevent distortion (inductive load); d) piezo-electric earpiece, resistor (2)
is required to increase the phase margin (stability with capacitive load).

March 1994 12

Philips Semiconductors Product specification

Low voltage versatile telephone transmission circuit
with dialler interface and transmit level dynamic limiting

The output voltage of the receiving amplifier is specified for
continuous-wave drive. Fig.16 shows the maximum output
swing of the receiving amplifier as a function of the DC
voltage drop (VLN). The maximum output voltage will be
higher under speech conditions, where the ratio of the
peak to the RMS value is higher.

The gain of the receiving amplifier can be adjusted to suit
the sensitivity of the transducer used. The adjustment
range is between 20 dB and 39 dB with single-ended drive
and between 26 dB and 45 dB with differential drive. The
gain is proportional to the external resistor R4 connected
between GAR and QR+. The overall gain between LN and
QR+ can be found by subtracting the attenuation of the
anti-sidetone network (32 dB) from the amplifier gain.

handbook, halfpage

V

QR(rms)

(V)

Two external capacitors (C4 =100 pF and
C7 = 10 × C4 = 1 nF) ensure stability. A larger value may
be chosen to obtain a first-order low-pass filter. The cut-off
frequency corresponds with the time constant R4 × C4.
The relationship C7 = 10 × C4 must be maintained.

1.5

TEA1064A

MGR071

(1)

(2)

(3)

5

VLN (V)

Curve (1) is for a differential load of 47 nF (series
resistance = 100 Ω); f = 3400 Hz.
Curve (2) is for a differential load of 450 Ω; f = 1 kHz.
Curve (3) is for a single-ended load of 150 Ω; f = 1 kHz.

1.0

0.5

0

34 6

Fig.16 Maximum output swing of the receiving amplifier as a function of DC voltage drop VLNwith the load at the

receiver output as parameter: valid for both supply options; THD = 2%; I

Automatic gain control input AGC

Automatic compensation of line loss is obtained by
connecting a resistor (R6) between AGC and VEE. This
automatic gain control varies the gain of the microphone
amplifier and receiving amplifier in accordance with the DC
line current. The control range is 6.1 dB; this corresponds
to a 5 km line of 0.5 mm diameter copper twisted-pair

The value of R6 must be chosen with reference to the
exchange supply voltage and its feeding bridge resistance
(see Fig.17 and Table 1). Different values of R6 give the
same line current ratios at the start and the end of the
control range. If automatic line-loss compensation is not
required the AGC pin can be left open, the amplifiers then
give their maximum gain.

= 15 mA.

line

cable (DC resistance = 176 Ω/km, average
attenuation = 1.2 dB/km). The DTMF gain is not affected
by this feature.

March 1994 13

Philips Semiconductors Product specification

Low voltage versatile telephone transmission circuit
with dialler interface and transmit level dynamic limiting

handbook, full pagewidth

0

∆A

vd

(dB)

−1

−2

−3

−4

−5

−6

R6 = 118 kΩ

Fig.17 Variation of gain as a function of line current with R6 as a parameter; R9 = 20 Ω.

R6 =

93.1 kΩ66.5 kΩ

∞

80 9060 7040 5020 3010

I

(mA)

line

TEA1064A

MGR072

Table 1 Values of R6 giving optimum line-loss

compensation at various values of exchange
supply voltage (V

bridge resistance (R

) and exchange feeding

exch

); R9 = 20 Ω.

exch

(Ω)

R

exch

400 600 800 1000

R6 (kΩ)

36 84.5 66.5 X X

V

exch

(V)

48 118 93.1 77.8 66.5
60 X X 97.6 84.5

MUTE input (see notes 1. and 2.)
MUTE = HIGH enables the DTMF input and inhibits the

microphone and receiving amplifier inputs.
MUTE = LOW or open-circuit disables the DTMF input and

enables the microphone and receiving amplifier inputs.
Switching MUTE gives negligible clicks at the telephone

outputs and on the line.

Dual-tone multi-frequency input DTMF (see note 1.)
When the DTMF input is enabled, dialling tones may be

sent on to the line. The voltage gain between DTMF-SLPE
and LN-V

is typ. 26 dB less than the gain of the

EE

microphone amplifier and varies with R7 in the same way
as the gain of the microphone amplifier. This means that
the tone level at the DTMF input has to be adjusted after

setting the gain of the microphone amplifier. With
R7=68kΩ the gain is typically 26 dB.

The signalling tones can be heard in the earpiece at a low
level (confidence tone).

Power-down input PD (see notes 1. and 2.)
During pulse dialling or register recall (timed loop break)

the telephone line is interrupted; as a consequence it
provides no supply for the transmission circuit connected
to V

or for the peripherals between V

CC1

and SLPE.

CC2

These supply gaps are bridged by the charges in the
capacitors C1 and C15. The requirements on these
capacitors are eased by applying a HIGH level to the PD
input during the time of the loop break. This reduces the
internal supply current I

from (typ.) 1.3 mA to (typ.)

CC1

60 µA and switches off the voltage regulator to prevent
discharge via LN and V

CC2

.

A HIGH level at PD also internally disconnects the
capacitor at REG so that the voltage stabilizer has no
switch-on delay after line interruptions. This minimizes the
contribution of the IC to the current waveform during pulse
dialling or register recall.

When the power-down facility is not required, the PD pin
can be left open-circuit or connected to SLPE.

Side-tone suppression

Suppression of the transmitted signal in the earpiece is
obtained by the anti-sidetone network comprising R1//Z

line

,

March 1994 14

Philips Semiconductors Product specification

Low voltage versatile telephone transmission circuit
with dialler interface and transmit level dynamic limiting

R2, R3, R8, R9 and Z
compensation is obtained when the following conditions
are fulfilled:

a) R9 × R2 = R1 × (R3 + [R8//Z
b) (Z

/[Z

bal

bal

If fixed values are chosen for R1, R2, R3 and R9, then
condition a) is always fulfilled provided R8//Z

To obtain optimum sidetone suppression, condition b) has
to be fulfilled, resulting in:

Z

= (R8/R1) × Z

bal

where k is a scale factor; k = (R8/R1).
The scale factor k (value of R8) is chosen to meet the

following criteria:

• compatibility with a standard capacitor from the E6 or
E12 range for Z

•Z

//R8  << R3 to fulfil condition a) and thus ensure

bal

correct anti-sidetone bridge operation;

•Z

In practice Z

+ R8  >> R9 to avoid influencing the transmit gain.

bal

varies considerably with the line length and

line

line type. Therefore the value chosen for Z
an average line length giving satisfactory sidetone
suppression with short and long lines. The suppression
also depends on the accuracy of the match between
Z

and the impedance of the average line.

bal

(see Fig.18). Maximum

bal

+ R8]) = (Z

line

;

bal

/[Z

line

=k×Z

line

line

])

bal

+ R1])

<< R3.

bal

should be for

bal

Example

The line impedance for which optimum suppression is to
be obtained can be represented by
210 Ω+(1265 Ω // 140 nF). This represents a 5 km line of

0.5 mm diameter copper twisted-pair cable matched with
600 Ω (176 Ω/km; 38 nF/km).

With k = 0.64 this results in: R8 = 390 Ω;
Z

= 130 Ω+(820 Ω // 220 nF).

bal

The anti-sidetone network for the TEA1060 family shown
in Fig.18 attenuates the signal received from the line by
32 dB before it enters the receiving amplifier. The
attenuation is almost constant over the whole
audio-frequency range.

Alternatively a conventional Wheatstone bridge can be
used as an anti-sidetone circuit (Fig.19). Both bridge types
can be used with either resistive or complex set
impedances. (More information on the balancing of
anti-sidetone bridges can be obtained in our publication

“Versatile speech transmission ICs for electronic
telephone sets”

, order number 9398 341 10011).

Notes

1. The reference used for the MUTE, DTMF and PD
inputs is SLPE.

2. A LOW level for any of these pins is defined by
connection to SLPE, a HIGH level is defined as a
voltage greater than V
V

+ 0.4 V.

CC1

TEA1064A

+ 1.5 V and smaller than

SLPE

March 1994 15

Philips Semiconductors Product specification

Low voltage versatile telephone transmission circuit
with dialler interface and transmit level dynamic limiting

handbook, full pagewidth

Z

line

V

R1

EE

R9

Fig.18 Equivalent circuit of TEA1060 family anti-side-tone bridge.

LN

SLPE

R2

i

m

R3

R8

IR

Z

bal

TEA1064A

R

t

MGR073

handbook, full pagewidth

Fig.19 Equivalent circuit of an anti-sidetone network in the Wheatstone bridge configuration.

LN

Z

line

V

R1

EE

R9

SLPE

Z

bal

i

m

R8

IR

R

t

R

A

MGR074

March 1994 16

Philips Semiconductors Product specification

Low voltage versatile telephone transmission circuit
with dialler interface and transmit level dynamic limiting

RATINGS

Limiting values in accordance with the Absolute Maximum System (IEC 134)

PARAMETER CONDITIONS SYMBOL MIN. MAX. UNIT

Positive line voltage continuous V
Repetitive line voltage during

switch-on line interruption V

Repetitive peak line voltage

one 1 ms pulse per 5 s R9 = 20 Ω;

R10 = 13 Ω

(Fig.24) V
Line current TEA1064A (note 1) R9 = 20 Ω I
Line current TEA1064AT (note 1) R9 = 20 Ω I
Input voltage on pins other than

LN and V

CC2

Total power dissipation (note 2) R9 = 20 Ω

TEA1064A P

TEA1064AT P
Storage temperature range T
Operating ambient temperature range T
Junction temperature T

LN

LN

LN
LN
LN

V

i

tot

tot

stg
amb
j

TEA1064A

− 12 V

− 13.2 V

− 28 V

− 140 mA

− 140 mA

VEE−0.7 V

− 714 mW

− 555 mW

−40 + 125 °C

−25 + 75 °C

−+125 °C

CC1

+ 0.7 V

Notes

1. Mostly dependent on the maximum required T

and on the voltage between LN and SLPE. See Figs 20 and 21 to

amb

determine the current as a function of the required voltage and the temperature.

2. Calculated for the maximum ambient temperature specified T

=75°C and a maximum junction temperature of

amb

125 °C.

THERMAL RESISTANCE

From junction to ambient in free air

TEA1064A R
TEA1064AT mounted on glass epoxy board 41 × 19 × 1.5 mm R

th j-a
th j-a

= 70 K/W
= 90 K/W

March 1994 17

Philips Semiconductors Product specification

Low voltage versatile telephone transmission circuit
with dialler interface and transmit level dynamic limiting

160

handbook, halfpage

I

LN

(mA)

140

120

100

80

60

T

amb

P

tot

(1) 45 °C 1143 mW
(2) 55 °C 1000 mW
(3) 65 °C 857 mW
(4) 75 °C 714 mW

40

212

46810

VLN-V

(1)

(2)

SLPE

TEA1064A

MGR075

(3)

(4)

(V)

T

amb

P

tot

(1) 45 °C 888 mW
(2) 55 °C 777 mW
(3) 65 °C 666 mW
(4) 75 °C 555 mW

Fig.20 TEA1064A safe operating area.

150

handbook, halfpage

I

LN

(mA)

130

110

90

70

50

30

212

46810

VLN-V

SLPE

MSA546

(1)

(2)

(3)

(4)

(V)

Fig.21 TEA1064AT safe operating area.

March 1994 18

Philips Semiconductors Product specification

Low voltage versatile telephone transmission circuit

TEA1064A

with dialler interface and transmit level dynamic limiting

CHARACTERISTICS

= 11 to 140 mA; VEE= 0 V; f = 800 Hz; T

I

line

otherwise specified

PARAMETER CONDITIONS SYMBOL MIN. TYP. MAX. UNIT

, V

Supplies LN, V

CC1

(pins 1, 16, 19)

CC2

Reference DC voltage between

and SLPE I

V

CC2

not connected V

R

VA

Variation with temperature I

Variation with line current referred

to 15 mA I

With R

connected between

VA

REG and SLPE R

DC line voltage:

voltage drop between LN and V

at I

=15mA Ip= 0 mA V

line

at I

= 100 mA Ip= 2 mA V

line

=140mA Ip=2mA V

at I

line

EE

Voltage drop under low current

conditions I

Internal supply current I

current into pin V

CC1

CC1

:

Microphone inputs MIC−, MIC+

(pins 8, 9)

Input impedance:

differential Z
single-ended Z

Common mode rejection ratio CMRR − 82 − dB

=25°C; RL= 600 Ω; tested in the circuit of Fig.22 or 23); unless

amb

=15mA

line

= 0; 4 mA

I

p

3.05 3.3 3.55 V

/∆T −3.0 −1.0 1.0 mV/K

− 60 − mV

3.6 3.8 4.2 V

3.95 4.2 4.65 V

=15mA V

line

= 100 mA ∆V

line

= 33 kΩ V

VA

R

=20kΩ V

VA

CC2-SLPE
CC2-SLPE

CC2-SLPE

CC2-SLPE
CC2-SLPE

MIC−, MIC+
inputs open;
R15 = 392 Ω;
without R

I

p

I

p

p

I

line

I

line

I

line

I

line

V

CC1

PD = LOW I
PD = HIGH I

VA

= 2 mA V
= 4 mA V

=0mA

= 2 mA V
= 4 mA V
= 7 mA V
=11mA V

= 2.8 V

LN
LN
LN
LN
LN

LN
LN
LN
LN

CC1
CC1

i
i

3.4 3.6 4.0 V

4.2 4.4 4.8 V

4.9 5.1 5.5 V

− 6.1 7.0 V

− 7.0 7.8 V

− 1.8 − V

− 2.2 − V

− 3.2 − V

− 3.5 − V

− 1.3 1.6 mA

− 60 82 µA

51 64 77 kΩ

25.5 32.0 38.5 kΩ

March 1994 19

Philips Semiconductors Product specification

Low voltage versatile telephone transmission circuit
with dialler interface and transmit level dynamic limiting

PARAMETER CONDITIONS SYMBOL MIN. TYP. MAX. UNIT

Voltage gain (see Fig.22) I

Variation of G

with frequency,

v

referred to 0.8 kHz f = 300 and 3400 Hz ∆G

Variation of G

with temperature,

v

referred to 25 °C without R6;

DTMF input (pin 12)
Input impedance Z

Voltage gain (see Fig.22) I

Variation of G

with frequency,

v

referred to 0.8 kHz f = 300 and 3400 Hz ∆G

Variation of G

with temperature,

v

referred to 25 °CI

Gain adjustment inputs GAS1, GAS2

(pins 2, 3)
Transmitting amplifier,

gain adjustment range ∆G

Sending amplifier output LN (pin 1)

Dynamic limiter

= 15 mA;

line

R7=68kΩ G

I

= 50 mA;

line

T

= −25 to + 75 °C ∆GvT −±0.2 − dB

amb

= 15 mA;

line

R7=68kΩ G

f = 697 and 1633 Hz ∆G

= 50 mA;

line

T

= −25 to + 75°C ∆GvT −±0.2 0.5 dB

amb

v

f −0.5 ± 0.1 + 0.5 dB

v

i

v

f −0.5 ± 0.1 + 0.5 dB

v

f −0.2 ± 0.05 + 0.2 dB

v

v

TEA1064A

51 52 53 dB

16.8 20.7 24.6 kΩ

25 26 27 dB

−8 −+0dB

Output voltage swing

(peak-to-peak value) I

= 15 mA;

line

R7=68kΩ;
Ip= 0 mA;
V

= 3.6 mV V

i(rms)

Total harmonic distortion V

= 3.6 mV + 10 dB THD − 1.5 2.0 %

i

V

= 3.6 mV + 15 dB THD − 2.8 10.0 %

i

Output voltage swing

(peak-to-peak value) V

= 3.6 mV + 10 dB

i

I

= 2 mA V

p

I

= 4 mA V

p

= 0 mA;

I

p

I

= 7 mA V

line

= 0 mA;

I

p

I

= 4 mA V

line

March 1994 20

LN(p-p)

LN(p-p)
LN(p-p)

LN(p-p)

LN(p-p)

3.6 4.0 4.5 V

3.7 3.95 4.2 V

3.0 3.25 3.5 V

− 2 − V

− 1 − V

Philips Semiconductors Product specification

Low voltage versatile telephone transmission circuit

TEA1064A

with dialler interface and transmit level dynamic limiting

PARAMETER CONDITIONS SYMBOL MIN. TYP. MAX. UNIT

Dynamic behaviour of limiter C16 = 470 nF

attack time, V
2 mV to 40 mV t
release time, V
40 mV to 2 mV t

Noise output voltage (RMS value) l

Receiving amplifier input IR (pin 13)
Input impedance Z

Receiving amplifier outputs QR− QR+

(pins 4, 5)

Output impedance single-ended Z
Voltage gain Fig.23;

single-ended; RT= 300 Ω G
differential; R

Variation with frequency,

referred to 0.8 kHz f = 300 and 3400 Hz ∆Gvf −0.5 −0.2 0 dB

Variation with temperature,

referred to 25 °C without R6;

Output voltage (RMS value) THD = 2%;

single-ended; R

differential; R

differential; C
(100 Ω series resistor); f = 3400 Hz I

jumps from

mic

jumps from

mic

=15mA;

line

R7=68kΩ;
200 Ω between
MIC− and MIC+;
psophometrically
weighted (P53 curve) V

I

= 15 mA;

line

R4 = 100 kΩ

= 600 Ω G

T

I

= 50 mA;

line

T

= −25 to +75 °C ∆GvT −±0.2 − dB

amb

sinewave drive;
R4 = 100 kΩ;
I

=15mA

line

= 150 Ω Ip= 0 mA V

T

I

= 2 mA V

p

= 450 Ω Ip= 0 mA V

T

= 2 mA V

I

p

=47nF;

T

= 0 mA V

p

I

= 2 mA V

p

att

rel

no(rms)

i

o

v
v

o(rms)
o(rms)
o(rms)
o(rms)

o(rms)
o(rms)

− 1.5 5.0 ms

50 150 − ms

−−72 − dBmp

17 21 25 kΩ

− 4 −Ω

30 31 32 dB
36 37 38 dB

− 0.22 − V

− 0.35 − V

− 0.39 − V

− 0.64 − V

− 0.57 − V

− 0.9 − V

March 1994 21

Philips Semiconductors Product specification

Low voltage versatile telephone transmission circuit
with dialler interface and transmit level dynamic limiting

PARAMETER CONDITIONS SYMBOL MIN. TYP. MAX. UNIT

Output voltage (RMS value) Ip= 0 mA;

THD = 10%;
sinewave drive;
R4 = 100 kΩ;
single-ended;
R

= 150 Ω;

T

= 4 mA V

I

line

I

= 7 mA V

line

Noise output voltage (RMS value) I

= 15 mA;

line

= 100 kΩ;

R

4

psophometrically
weighted
(P53 curve);
pin IR open
single-ended;
R

= 300 Ω;V

T

differential;
R

= 600 Ω V

T

Noise output voltage (RMS value) in circuit of Fig.23;

S1 in position 2;
200 Ω between
MIC+ and MIC−;
single-ended;
R

= 300 Ω

T

R

= 68 kΩ V

7

= 24.9 kΩ V

R

7

Gain adjustment input GAR (pin 6)
Receiving amplifier,

gain adjustment range ∆G

MUTE INPUT (pin 14)

o(rms)
o(rms)

no(rms)

no(rms)

no(rms)
no(rms)

v

TEA1064A

− 25 − mV

− 160 − mV

− 45 −µV

− 90 −µV

− 100 −µV

− 65 −µV

−11 −+8dB

Input voltage HIGH V

Input voltage LOW V
Input current I

Change of microphone amplifier

gain at mute-ON MUTE = HIGH −∆G

March 1994 22

IH

IL

mute

1.5 +
V

SLPE

0 −

−

V

CC1

+ 0.4

0.3 +
V

SLPE

V

V

− 11 20 µA

v

− 100 − dB

Philips Semiconductors Product specification

Low voltage versatile telephone transmission circuit
with dialler interface and transmit level dynamic limiting

PARAMETER CONDITIONS SYMBOL MIN. TYP. MAX. UNIT

Voltage gain from input

DTMF-SLPE to QR+ output
with mute-ON MUTE = HIGH;

single-ended load;
R

= 300 Ω G

L

Power-down input PD (pin 15)
Input voltage HIGH V

Input voltage LOW V
Input current I

Automatic gain control input AGC

(pin 18)
Controlling the gain from

IR (pin 13) to QR+,QR−
(pins 4, 5) and the gain
from MIC+, MIC− (pins 8, 9)
to LN (pin 1) R6 = 93.1 kΩ

(between pins
18 and 11)

gain control range with respect to

I

=15mA I

line

=75mA −G

line

Highest line current

for maximum gain I

Lowest line current

for minimum gain I

Change of gain

between I

= 15 and 35 mA −∆G

line

Microphone mute

input DLS/

MMUTE (pin 7)

Input voltage low

Input current at low

input voltage I

Release time after a low

level on pin 7 C16 = 470 nF t

Change of microphone amplifier

gain at low input voltage on
pin 7 −∆G

V

v

IH

IL

PD

v

line

line

v

IL

IL

rel

v

TEA1064A

−−18 − dB

1.5 +
V

SLPE

−

0 −

− 510µA

5.7 6.1 6.5 dB

− 24 − mA

− 61 − mA

0.9 1.4 1.9 dB

V

EE

−

−85 −60 −35 µA

− 30 − ms

− 100 − dB

V

CC1

+ 0.4

0.3 +
V

SLPE

VEE+

0.3

V

V

V

March 1994 23

Philips Semiconductors Product specification

Low voltage versatile telephone transmission circuit
with dialler interface and transmit level dynamic limiting

ndbook, full pagewidth

R16

56 Ω

I

p

C1

C15
220
µF

V

i

100 µF

10
µF

V

i

13

IR

9

MIC+

8

MIC−

12

DTMF

14

MUTE

15

PD

7

DLS/MMUTE

C16
470 nF

19 1

V

V

CC2

CC1

V

EE

R15

392 Ω

R1

620 Ω

16

TEA1064A

REG AGC STAB

181711 10

C3

470

nF

R6

R5

3.6
kΩ

LN

GAR

GAS1

GAS2

SLPE

QR−

QR+

20

R9
20 Ω

4

5

6

2

3

R4

100

kΩ

R7

68

kΩ

100 µF

R

600 Ω

C4
100 pF

C7 1 nF

C6
100 pF

TEA1064A

I

line

V

o

L

11 to

140 mA

MGR076

For measuring the gain from MIC+ and MIC− the MUTE input should be LOW
or open-circuit; for measuring the DTMF input, the MUTE input should be HIGH.
Inputs not being tested should be open-circuit.

Fig.22 Test circuit for defining voltage gain of MIC−, MIC+ and DTMF inputs; voltage gain (Gv) is defined as

20 log Vo / Vi .

March 1994 24

Philips Semiconductors Product specification

Low voltage versatile telephone transmission circuit
with dialler interface and transmit level dynamic limiting

R15

392 Ω

R1

620 Ω

16

V

CC1

TEA1064A

REG AGC STAB

181711

C3

470

R6

nF

LN

QR−

QR+

GAR

GAS1

GAS2

SLPE

10 20

R5

3.6
kΩ

R9
20 Ω

R16

56 Ω

I

p

C1

C15
220
µF

100

µF

R3

3.92 kΩ

130 Ω

820

Ω

220

nF

100 nF

V

i

390

R8

R2

130 kΩ

S1

2
1

Ω

13

10

12

µF

14

15

C16
470 nF

19 1

V

CC2

IR

9

MIC+

8

MIC−

DTMF

MUTE

PD

7

DLS/MMUTE

V

EE

TEA1064A

I

line

10 µF

4

Z

T

5

R4

C4

100

100 pF

kΩ

6

C7 1 nF

2

R7
68
kΩ

3

C6
100 pF

100 µF

V

o

R

L

600 Ω

11 to

140 mA

MGR077

handbook, full pagewidth

Fig.23 Test circuit for defining voltage gain of the receiving amplifier, voltage gain (Gv) is defined as

20 log  Vo/Vi(with S1 in position 1).

APPLICATION INFORMATION

The basic application circuit is shown in Fig.24 and some typical applications are shown in Figs 25, 26 and 27.
In the basic application, the circuit provides two possibilities for supplies to peripheral circuits:

• regulated line voltage VLN(stabilized V

LN-SLPE

) and unregulated supply voltage for peripheral circuits, the supply
voltage is dependent only on the peripheral supply current. This application is the same as that used for
TEA1060/TEA1061, TEA1067 and TEA1068;

• stabilized supply voltage for peripherals (V

CC2-SLPE

), the DC line voltage depends on the current flowing to the

peripheral circuits.

March 1994 25

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March 1994 26

telephone

line

BAS11

(2×)

BZW14

(2×)

R10
13 Ω

R3

3.92 kΩ

R2
130 kΩ

R4

100 kΩ

Z

bal

C7

R8

390 Ω

C5

100 nF

R13

1 nF

C4
100 pF

R14

116

R9

LN

SLPE

C6

100 pF

13

IR

4

QR−

5

QR+

6

GAR

9

MIC+

8

MIC−

20 Ω

pagewidth

R1

620 Ω

TEA1064A

REGGAS2GAS1

173220

R7
68
kΩ

V

CC1

AGC STAB

18 10

C3
470

R6

nF

R15

392 Ω

DLS/MMUTE

V

EE

R5

3.6
kΩ

C1

100 µF

V

CC2

12

DTMF

14

MUTE

15

PD

7

11

C16
470
nF

R16
56 Ω

C15
220 µF

from dial

control circuits

R17

3.3 kΩ

and

Philips Semiconductors Product specification

Low voltage versatile telephone transmission circuit

with dialler interface and transmit level dynamic limiting

+

−

MGR078

Fig.24 Basic application of the TEA1064A with stabilized supply for peripherals, shown here with a piezo-electric earpiece and DTMF dialling.

The diode bridge and R10 limit the current into, and the voltage across, the circuit during line transients. A different protection
arrangement is required for pulse dialling or register recall.

TEA1064A

Philips Semiconductors Product specification

Low voltage versatile telephone transmission circuit
with dialler interface and transmit level dynamic limiting

For the basic application giving regulated line voltage the above circuit is changed as follows:

− R15 must be short-circuited;

− the value of R16 is changed to 392 Ω;

− the value of C3 is changed to 4.7 µF.

handbook, full pagewidth

V
DTMF
M
FL

V

SS

DD

PCD3310

telephone

line

cradle

contact

BST76A

LN V

TEA1064A

V

EE

CC2

DTMF
MUTE

PD

SLPE

TEA1064A

MGR079

Fig.25 Typical DTMF-pulse set application circuit (simplified) showing the TEA1064A with the CMOS bilingual

dialling circuit PCD3310; the broken line indicates optional flash (register recall by timed loop break).

handbook, full pagewidth

telephone

line

cradle

contact

BST76A

LN V

TEA1064A

V

EE

DP/flash

CC2

DTMF
MUTE

PD

SLPE

M
DP

V

V

DD

SS

PCD332x

FAMILY

MGR080

Fig.26 Typical pulse dial set application circuit (simplified) showing the TEA1064A with one of the PCD332X

family of CMOS interrupted current-loop dialling circuits.

March 1994 27

Philips Semiconductors Product specification

Low voltage versatile telephone transmission circuit
with dialler interface and transmit level dynamic limiting

handbook, full pagewidth

telephone

line

cradle

contact

BST76A

LN V

TEA1064A

V

EE

DP/flash

CC2

DTMF

MUTE

PD

SLPE

V

DD

TONE
M
DP

V

SS

2

C-bus

I

PCF8577

LCD MODULE

TEA1064A

PCD3344

16-DIGIT

LCD

MGR081

Fig.27 Typical dual-standard (pulse and DTMF) feature phone application circuit (simplified) showing the

TEA1064A and the PCD3344 CMOS telephone microcontroller with on-chip DTMF generator plus
I2C-bus.

March 1994 28

Philips Semiconductors Product specification

Low voltage versatile telephone transmission circuit
with dialler interface and transmit level dynamic limiting

PACKAGE OUTLINES

DIP20: plastic dual in-line package; 20 leads (300 mil)

D

seating plane

A

L

Z

20

e

b

b

11

1

w M

1

TEA1064A

SOT146-1

M

E

A

2

A

c

(e )

1

M

H

pin 1 index

1

0 5 10 mm

scale

DIMENSIONS (inch dimensions are derived from the original mm dimensions)

A

A

A

UNIT

inches

Note

1. Plastic or metal protrusions of 0.25 mm maximum per side are not included.

max.

mm

OUTLINE
VERSION

SOT146-1

1 2

min.

max.

1.73

1.30

0.068

0.051

IEC JEDEC EIAJ

b

b

1

0.53

0.38

0.021

0.015

0.36

0.23

0.014

0.009

REFERENCES

cD E e M

(1) (1)

26.92

26.54

1.060

1.045

SC603

6.40

6.22

0.25

0.24

E

10

(1)

M

e

L

1

3.60

3.05

0.14

0.12

8.25

7.80

0.32

0.31

EUROPEAN

PROJECTION

H

E

10.0

0.2542.54 7.62

8.3

0.39

0.010.10 0.30

0.33

ISSUE DATE

92-11-17
95-05-24

Z

w

max.

2.04.2 0.51 3.2

0.0780.17 0.020 0.13

March 1994 29

Philips Semiconductors Product specification

Low voltage versatile telephone transmission circuit
with dialler interface and transmit level dynamic limiting

SO20: plastic small outline package; 20 leads; body width 7.5 mm

D

c

y

Z

20

11

TEA1064A

SOT163-1

E

H

E

A

X

v M

A

pin 1 index

1

e

0 5 10 mm

DIMENSIONS (inch dimensions are derived from the original mm dimensions)

UNIT

mm

inches

Note

1. Plastic or metal protrusions of 0.15 mm maximum per side are not included.

A

max.

2.65

0.10

A

1

0.30

0.10

0.012

0.004

A2A

2.45

2.25

0.096

0.089

0.25

0.01

b

0.49

0.36

p

cD

0.32

0.23

0.013

0.009

3

0.019

0.014

10

w M

b

p

scale

(1)E(1) (1)

13.0

12.6

0.51

0.49

eHELLpQ

7.6

1.27

7.4

0.30

0.050

0.29

10.65

10.00

0.419

0.394

Q

A

2

0.055

A

1.4

1

detail X

1.1

1.1

1.0

0.4

0.043

0.043

0.039

0.016

(A )

L

p

L

0.25

0.01

A

3

θ

0.25 0.1

0.01

ywv θ

Z

0.9

0.4

8

0.004

0.035

0.016

0

o
o

OUTLINE
VERSION

SOT163-1

IEC JEDEC EIAJ

075E04 MS-013AC

REFERENCES

March 1994 30

EUROPEAN

PROJECTION

ISSUE DATE

95-01-24
97-05-22

Philips Semiconductors Product specification

Low voltage versatile telephone transmission circuit
with dialler interface and transmit level dynamic limiting

SOLDERING
Introduction

There is no soldering method that is ideal for all IC
packages. Wave soldering is often preferred when
through-hole and surface mounted components are mixed
on one printed-circuit board. However, wave soldering is
not always suitable for surface mounted ICs, or for
printed-circuits with high population densities. In these
situations reflow soldering is often used.

This text gives a very brief insight to a complex technology.
A more in-depth account of soldering ICs can be found in

“Data Handbook IC26; Integrated Circuit Packages”

our
(order code 9398 652 90011).

DIP

S

OLDERING BY DIPPING OR BY WAVE

The maximum permissible temperature of the solder is
260 °C; solder at this temperature must not be in contact
with the joint for more than 5 seconds. The total contact
time of successive solder waves must not exceed
5 seconds.

The device may be mounted up to the seating plane, but
the temperature of the plastic body must not exceed the
specified maximum storage temperature (T
printed-circuit board has been pre-heated, forced cooling
may be necessary immediately after soldering to keep the
temperature within the permissible limit.

R

EPAIRING SOLDERED JOINTS

Apply a low voltage soldering iron (less than 24 V) to the
lead(s) of the package, below the seating plane or not
more than 2 mm above it. If the temperature of the
soldering iron bit is less than 300 °C it may remain in
contact for up to 10 seconds. If the bit temperature is
between 300 and 400 °C, contact may be up to 5 seconds.

SO

REFLOW SOLDERING
Reflow soldering techniques are suitable for all SO

packages.

stg max

). If the

Several techniques exist for reflowing; for example,
thermal conduction by heated belt. Dwell times vary
between 50 and 300 seconds depending on heating
method. Typical reflow temperatures range from
215 to 250 °C.

Preheating is necessary to dry the paste and evaporate
the binding agent. Preheating duration: 45 minutes at
45 °C.

AVE SOLDERING

W
Wave soldering techniques can be used for all SO

packages if the following conditions are observed:

• A double-wave (a turbulent wave with high upward
pressure followed by a smooth laminar wave) soldering
technique should be used.

• The longitudinal axis of the package footprint must be
parallel to the solder flow.

• The package footprint must incorporate solder thieves at
the downstream end.

During placement and before soldering, the package must
be fixed with a droplet of adhesive. The adhesive can be
applied by screen printing, pin transfer or syringe
dispensing. The package can be soldered after the
adhesive is cured.

Maximum permissible solder temperature is 260 °C, and
maximum duration of package immersion in solder is
10 seconds, if cooled to less than 150 °C within
6 seconds. Typical dwell time is 4 seconds at 250 °C.

A mildly-activated flux will eliminate the need for removal
of corrosive residues in most applications.

EPAIRING SOLDERED JOINTS

R
Fix the component by first soldering two diagonally-

opposite end leads. Use only a low voltage soldering iron
(less than 24 V) applied to the flat part of the lead. Contact
time must be limited to 10 seconds at up to 300 °C. When
using a dedicated tool, all other leads can be soldered in
one operation within 2 to 5 seconds between
270 and 320 °C.

TEA1064A

Reflow soldering requires solder paste (a suspension of
fine solder particles, flux and binding agent) to be applied
to the printed-circuit board by screen printing, stencilling or
pressure-syringe dispensing before package placement.

March 1994 31

Philips Semiconductors Product specification

Low voltage versatile telephone transmission circuit

TEA1064A

with dialler interface and transmit level dynamic limiting

DEFINITIONS

Data sheet status

Objective specification This data sheet contains target or goal specifications for product development.
Preliminary specification This data sheet contains preliminary data; supplementary data may be published later.
Product specification This data sheet contains final product specifications.

Limiting values

Limiting values given are in accordance with the Absolute Maximum Rating System (IEC 134). Stress above one or
more of the limiting values may cause permanent damage to the device. These are stress ratings only and operation
of the device at these or at any other conditions above those given in the Characteristics sections of the specification
is not implied. Exposure to limiting values for extended periods may affect device reliability.

Application information

Where application information is given, it is advisory and does not form part of the specification.

LIFE SUPPORT APPLICATIONS

These products are not designed for use in life support appliances, devices, or systems where malfunction of these
products can reasonably be expected to result in personal injury. Philips customers using or selling these products for
use in such applications do so at their own risk and agree to fully indemnify Philips for any damages resulting from such
improper use or sale.

March 1994 32

Philips Semiconductors Product specification

Low voltage versatile telephone transmission circuit
with dialler interface and transmit level dynamic limiting

NOTES

TEA1064A

March 1994 33

Philips Semiconductors Product specification

Low voltage versatile telephone transmission circuit
with dialler interface and transmit level dynamic limiting

NOTES

TEA1064A

March 1994 34

Philips Semiconductors Product specification

Low voltage versatile telephone transmission circuit
with dialler interface and transmit level dynamic limiting

NOTES

TEA1064A

March 1994 35

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© Philips Electronics N.V. 1998 SCA60
All rights are reserved. Reproduction in whole or in part is prohibited without the prior written consent of the copyright owner.

The information presented in this document does not form part of any quotation or contract, is believed to be accurate and reliable and may be changed
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Internet: http://www.semiconductors.philips.com

Printed in The Netherlands 415102/00/02/pp36 Date of release: March 1994 Document order number: 9397 750 nnnnn