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ü
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11
TRANSCEIVERS
Product Description
Ordering Information
Typical Applications
Features
Functional Block Diagram
RF Micro Devices, Inc.
7625 Thorndike Road
Greensboro,NC 27409, USA
Tel (336)664 1233
Fax (336)664 0454
http://www.rfmd.com
Optimum Technology Matching® Applied
Si BJT GaAs MESFETGaAs HBT
Si Bi-CMOS
SiGe HBT
Si CMOS
13 16
8
6
Linear
RSSI
4
2
25 26
Prescaler
÷
64
Phase
Detector &
Charge Pump
29
109 17 181211 23 24
IF2 IN
IF1 OUT
IF2 BP+
IF2 BP-
IF1 BP-
IF1 BP+
IF1 IN+
IF1 IN-
IF2 OUT
DEMOD IN
MIX OUT
MIX IN
LNA OUT
RX IN
RESNTR+
LOOP FLT
RESNTR-
32
PD
DC
BIAS
30 OSC B
31
OSC E
21
RSSI
20 MUTE
22
FM OUT
RF2917
433/868/915MHZ
FM/FSK RECEIVER
• Wireless Meter Reading
• Keyless Entry Systems
• 433/868/915MHz ISM Band Systems
• Remote Data Transfers
• Wireless Security Systems
The RF2917 is a monolithic integrated circuit intended for
use as a low cost FM or FSK receiver. The device is provided in 32-lead plastic packaging and is designed to provide a fully functional FM receiver. The chip is intended
for analog or digital applications in the North American
915 MHz ISM band and European 433MHz and 868MHz
ISM bands. The integrated VCO, ÷64 prescaler, and reference oscillator require only the addition of an external
crystal to provide a complete phase-locked oscillator for
single c hannel applications. The selection of linear FM
output or digital FSK output is done with the mute pin.
• Fully Monolithic Integrated Receiver
• 2.7V to 5.0V Supply Voltage
• Narrowband and Wideband FSK
• 300MHz to 1000MHz Frequency Range
• Power Down Capability
• Analog or Digital Output
RF2917 433/868/915MHz FM/FSK Receiver
RF2917 PCBA-L Fully Assembled Evaluation Board, 433MHz
RF2917 PCBA-M Fully Assembled Evaluation Board, 868MHz
RF2917 PCBA-H Fully Assembled Evaluation Board, 915MHz
11
Rev B2 010118
7° MAX
0° MIN
+
0.15
0.10
0.60
0.127
7.00
+0.20sq.
5.00
+0.10sq.
0.22
+0.05
Dimensions in mm.
0.15
0.05
-A-
1.40
+0.05
0.50
Package Style: LQFP-32_5x5
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RF2917
Rev B2 010118
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TRANSCEIVERS
Absolute Maximum Ratings
Parameter Ratings Unit
Supply Voltage -0.5 to +5.5 V
DC
Control Voltages -0.5 to +5.0 V
DC
Input RF Level +10 dBm
Output Load VSWR 50:1
Operating Ambient Temperature -40 to +85 °C
Storage Temperature -40 to +150 °C
Parameter
Specification
Unit Condition
Min. Typ. Max.
Overall
T=25°C, VCC=3.6V, Freq=915MHz
RF Frequency Range 300 to 1000 MHz
VCO and PLL Section
VCO Frequency Range 300 to 1000 MHz
PLL Lock Time 10 ms The PLL lock time is set externally by the
bandwidth of theloop filter and start up of
the crystal.
PLL Phase Noise -74
-98
dBc/Hz
dBc/Hz
915MHz, 5kHz loop BW, 10kHz offset
915MHz, 5kHz loop BW, 100kHz o ffset
Reference Frequency 0.5 17 MHz
Crystal R
S
50 100 Ω
Charge Pump Current -40 +40 µA
Overall Receive Section
Frequency Range 300 to 1000 MHz
RX Sensitivity -98 -101 dBm IF BW=180kHz, Freq=915MHz , S/N=8dB
LO Leakage -55 dBm
RSSI DC Output Range 0.8 to 1.5 V MUTE = 0; R
L
= 51kΩ
RSSI Sensitivity 13 mV/dB MUTE = 0
RSSI Dynamic Range 60 dB MUTE = 0
LNA
Power Gain 18 dB 433MHz, Matched to 50Ω
16 dB 915MHz, Matched to 50Ω
Noise Figure 3.6 dB 433MHz
3.8 dB 915MHz
Input IP
3
-8 dBm 915MHz
Input P
1dB
-15 dBm 915MHz
RX IN Impedance 82-j86
77-j43
Ω 433MHz (see Plots)
915MHz (see Plots)
Output Impedance Open Collector Ω
Mixer
Single-ended configuration
Conversion Power Gain 15 dB 433MHz, Matched to 50Ω
8 dB 915MHz, Matched to 50Ω
Noise Figure (SSB) 17 dB 433MHz, SSB Measurement
17 dB 915MHz, SSB Measurement
Input IP
3
-20 dBm 433MHz
Input IP
3
-15.5 dBm 915MHz
Input P
1dB
-30 dBm 433MHz
Input P
1dB
-26 dBm 915MHz
First IF Section
IF Frequency Range 0.1 10.7 25 MHz
Voltage Gain 34 dB IF=10.7MHz, Z
L
=330Ω
Noise Figure 13 dB
IF1 Input Impedance 330 Ω
IF1 Output Impedance 330 Ω
Caution! ESD sensitive device.
RF MicroDevices believesthe furnished information iscorrect and accurate
at the time of this printing. However, RF Micro Devices reserves the right to
make changes to its products without notice. RF Micro Devices does not
assume responsibility for the use of the described product(s).
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RF2917
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11
TRANSCEIVERS
Parameter
Specification
Unit Condition
Min. Typ. Max.
Second IF Section
IF Frequency Range 0.1 10.7 25 MHz
VoltageGain 60 dB IF=10.7MHz
Noise Figure 13 dB
IF2 Input Impedance 330 Ω
IF2 Output Impedance 1 kΩ At IF2 OUT- pin 23
Demod Input Impedance 10 kΩ Pin 24
Data Output Impedance 6.3 - j25.7 kΩ
Data Output Bandwidth 500 kHz Z
LOAD
=1 MΩ || 3pF; 3dB dependent on IF
and discriminator BW
Data Output Level 0.3 V
CC
-0.3 V Z
LOAD
=1 MΩ || 3pF; Output voltage is pro-
portional with the instantaneous frequency
deviation.
FM Output DC Level 2.6 V
FM Output AC Level 200 mV
PP
Power Down Control
Logical Controls “ON” 2.0 V Voltage supplied to the input
Logical Controls “OFF” 1.0 V Voltage supplied to the input
Control Input Im pedance 25 kΩ
Tur n On Ti me 10.2 ms From PD=1 to valid data out, current eval
board
Power Supply
Voltage 3.6 V Specifications
2.7 5.0 V Operating limits
2.4 V Temp>0°C
Current Consumption 5 9 12.3 mA RX Mode, MUTE=“1”
1 µA PowerDown Mode
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TRANSCEIVERS
Pin Function Description Interface Schematic
1 VCC1
This pin is used to supply DC bias to the receiver RF electronics. A RF
bypass capacitor should be connected directly to this pin and returned
to ground. A 22pF capacitor is recommended for 915MHz applications.
A 100pF capacitor is recommended for 4 3 3MHz applications.
2RXIN
RF input pin for the receiver electronics. RX IN input impedance is a
low impedance when enabled. RX IN is ahigh impedance when the
receiver is disabled.
3 GND1
Ground connection for RF receiver functions. Ke e p traces physically
short and connect immediately to ground plane for best performance.
4LNAOUT
Output pin for the receiver RF low noise amplifier.This pin is an open
collector output and requires an external pull u p coil to provide bias and
tune the LNA output. A capacitor in series with this output can be used
to match the LNA to 50Ω impedance image filters.
5 GND2
GND2 is c onnection for the 40 dB IF limiting amplifier. Keep traces
physically short and connect immediately to ground pla ne for best performance.
6 MIX IN
RF input to the RF Mixer. An LC matching network between LNA OUT
and MIX I N can be used to connect the LNA output to the RFmixer
input in applications where an image filter is not n eeded or desired.
7 GND3
GND3 is the ground connection for the receiver RF mixer.
8MIXOUT
IF output from the RF mixer. Interfaces directly to 10.7MHz ceramic IF
filters as shown in the application schematic. A pull-up inductor and
series matching capacitor should be used to present a 330Ω termination impedance to the ceramic filter. Alternately, an IF tank can b e used
to tailor the IF frequency and bandwidth to meet the needs of a g iven
application. In addition to the matching components, a 15pF capacitor
should be p laced from this pin to ground.
9IF1IN-
Balanced IF input to the 40dB limiting am plifier strip. A 10nF DC blocking capacitor is required on this input.
10 IF1 IN+
Functionally the same as pin 9 except non-inverting node amplifier
input. In single-ended applications, this input should be bypassed
directly to ground through a 10nF capacitor.
See pin 9.
11 IF1 BP+
DC feedback node for th e 40dB limiting amplifier strip. A 100nF bypass
capacitor from this pin toground is required.
See pin 9.
12 IF2 BP-
See pin 11. See pin 9.
13 IF1 OUT
IF output from the 40dB limiting amplifier. The IF1 OUT output presents
a nominal 330Ω output resistance and interfaces directly to 10.7MHz
ceramicfilters.
14 VREF IF
DC voltage reference for the IF limiting amplifiers (typically 1.1V). A
0.1µF capacitor from this pin toground is required.
15 GND5
Ground connection for 60dB IF limiting amplifier. Keep traces physically
short and connect immediately to ground plane for best performance.
RX IN
LNA OUT
MIX IN
MIX OUT+
V
CC
IF1 IN-IF1 IN+
330 330
60 k
Ω
60 k
Ω
IF1 BP+ IF1 BP-
IF1 OUT
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TRANSCEIVERS
Pin Function Description Interface Schematic
16 IF2 IN
Inverting input to the 60dB limiting amplifier strip. A 10nF DC blocking
capacitor is required on this input. The IF2 IN input presents a nominal
330Ω input resistance and interfaces directly to 10.7MHz ceramic filters.
17 IF2 BP+
DC feedback node for the 60dB limiting amplifier strip. A 100nF bypass
capacitor from this pin to ground is required.
See pin 16.
18 IF2 BP-
See pin 17. See pin 16.
19 VCC3
This pin is used to supply DC bias to the 60dB IF limiting a mplifier. An
IF bypass capacitor should be connected directly to this pin and
returned to ground. A 10 nF capacitor is recommended for 10.7MHz IF
applications.
20 MUTE
This pin is used to select FM, FSK, or mute at the FM OUT pin.
MUTE>Vcc - 0.4V turns the FM OUT signal off. MUTE<0.4V turns the
FM OUT signal on for FSK digital data. When MUTE is leftfloating, the
FM OUT signa l is linear FM.
21 RSSI
A DC voltage proportional to the received signal strength is output from
this pin. The output voltage increases with increasing signal strength.
22 FM OUT
Demodulated output from the discriminator/demodulator. Output levels
on this are CMOS compatible in FSK mode (see pin 20). In linear FM
mode, the demodulated signal level is approximately 240mVpp on a
DC voltage offset. The magnitude of the load impedance is intended to
be 1MΩ or greater.
23 IF2 OUT
IF output from the 60dB limiting amplifier strip. This pin is intended to
be connected topin 24 through a 5pF capacitor (for 10.7MHz IF applications). This capacitor in conjunction with a tank resonant at the IF frequency connected from pin 24 to ground is used to form an FM
discriminator.
24 DEMOD IN
This pin is the input to the FM demodulator. This pin is NOT AC coupled. Therefore, a DC blocking capacitor is required on this pin to avoid
a DC path to ground. A DC blocked LC tank resonant at the IF or
ceramic discriminator should be connected to this pin.
25 RESNTR-
This port is used to supply DC voltag e to the VCO as well as to tune the
center frequency ofthe VCO. Equal value inductors should be connected to this pin and pin 26.
26 RESNTR+
See pin 25. See pin 25.
27 VCC2
This pin is used to supply DC bias to the VCO, prescaler, and PLL. An
IF bypass capacitor should be connected directly to this pin and
returned to ground. A 10nF capacitor is recommended for 10.7MHz IF
applications.
28 GND4
GND4 is the ground shared on chip by the VCO, prescaler, and PLL
electronics.
IF2 IN
330 330
60 k
Ω
60 k
Ω
IF2 BP+ IF2 BP-
MUTE
V
CC
V
CC
RSSI
IF2 OUT
DEMOD IN
10 k
Ω
V
CC
RESNTR-RESNTR+
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TRANSCEIVERS
Pin Function Description Interface Schematic
29 LOOP FLT
Output of the charge pump, and input to the VCO control. An RC network from this pin to ground is used to establish the PLL bandwidth.
30 OSC B
This pin is connected directly to the reference oscillator transistor base.
The intended reference oscillator configuration is a modified Colpitts. A
100pF capacitor should be connected between pin 30 and pin 31.
31 OSC E
This pin is connected directly to the emitter of the reference oscillator
transistor. A 100pF capacitor should be connected from this pinto
ground.
See pin 30.
32 PD
This pin is used to power up or down the RF2917. A logic high (PWR
DWN >2.0V) powers up the receiver and PLL. A logic low (PWR DWN
<1.0V) powers down circuit to standby mode.
ESD
This diode structure is used to provide electrostatic discharge protection to 3kV using the Human body model. The following pins are protected: 1, 3, 5, 7-19, 21-24, 27-31.
LOOP FLT
V
CC
OSC E
OSC B
V
CC
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TRANSCEIVERS
RF2917 Theory of Operation and Application Information
The RF2917 is part of a family of low-power RF transceiver IC’s developed for wireless data communication
devices operating in the European 433/868MHz ISM
bands or the U.S. 915 MHz ISM band. This IC has
been implemented in a 15GHz silicon bipolar process
technology that allows low-power transceiver operation
in a variety of commercial wireless products. The
RF2917 realizes a highly integrated, single-conversion
FM/FSK receiver with the addition of a reference crystal, intermediate frequency (IF) filtering, and a few passive components. The LNA (low noise amplifier) input
of the RF2917 is easily matched to a front-end filter or
antenna by means of a DC blocking capacitor and
reactive components. The receive r local oscillator (LO)
is generated by an internalized VCO, PLL and phase
discriminator in conjunction with the external reference
crystal, loop filter and VCO resonator components.
The receiver IF section is optimized to interface with
low cost 10.7MHz ceramic filters, and its -3dB bandwidth of 25MHz also allows it to be used (with lower
gain) at higherfrequencies with other types of filters.
FM/FSK SYSTEMS
The receiver output functionality is determined by the
tri-state MUTE input. The three output configurations
are linear FM, FSK and mute. An on-chip 1.6MHz RC
filter, which follow s the demodulator output, filters the
harmonics of the IF signal from the output data.
When in the FM mode, the FM OUT signal is the buffered output from the quadrature demodulator. The output signal has a fixed DC offset of V
CC
-1.0V,while the
AC levelis dependent on the FM deviation,with a maximum level of 240mV
P-P
. For optimum operation in
either FM or FSK mode, FM deviation needs to exceed
(with margin) the carrier frequency error anticipated
between the receiver and transmitter.
When in the FSK mode, the FM OUT signal is clipped,
having a rail-to-rail output level. The FM OUT pin is
only capable of driving rail-to-rail output into a very
high impedance and small capacitance, with the
amount of capacitance determining the FM OUT bandwidth. For a 3pF load, the bandwidth is in excess of
500 kHz. The rail-to-railoutput isalso limited by the frequency deviation and bandwidth of the IF filters. With
the 180kHz bandwidth filters on the evaluation boards,
the rail-to-rail output is limited to less than 140kHz.
Choosing the right IF bandwidth and deviation versus
data rate (modulation index) is important in evaluating
the applicability of the RF2917 for a g iven data rate.
AM SYSTEMS
The RF2919 is recommended for use in ASK/OOK
applications, however , the RF2917 may be utilized in
an AM system by using the RSSI (received signal
strength indicator) output to recover the modulation.
The FM outputmode should be selected for AMoperation because of the higher RSSI resolution in FM
mode.
RSSI
The RSSI output signal is supplied from a current
source and therefore requires a resistor to convert it to
a voltage. The RSSI is linear over the same range of
input power for both FM and FSK modes, but the FM
mode has higher RSSI resolution. For a 51kΩ resistive
load, the RSSI will range from 1.0V to 2.6V in FM
mode and from 0.8V to 1.5V in FSK mode (3.6V supply). A small parallel capacitor is suggested to limit the
bandwidth and filter noise.
APPLICATION AND LAYOUT CONSIDERATIONS
The RX IN pin is DC-biased, requiring a DC blocking
capacitor. If the RF filter has DC blocking characteristics,suchasaceramicdielectricfilter,thenaDCblocking capacitor is not necessary. When in power down
mode, the RX IN impedance increases. Therefore, in a
half-duplex application, the RF2917 RX IN may share
the RF filter with a transmitter output having a similar
high impedance power down characteristic. Care must
be taken in this case to account for loading effects of
the transmitter on the receiver, and vice versa, in
matching the filter to both the transmitter and receiver.
TheVCOisaverysensitiveblockinthissystem.RF
signals feeding back into the VCO by either radiation or
coupling of traces may cause the PLL to become
unlocked. The trace(s) for the anode of the tuning varactor should also be kept short. The layout of the resonators and varactor are very important. The capacitor
and varactor should be closest to the RF2917 pins and
the trace length should be as short as possible. The
inductors can be placed further away and any trace
inductance can be compensated by reducing the value
of the inductors. Printed inductors may also be used
with careful design. For best results, the physical layout
should be as symmetrical as possible.
When using loop bandwidths lower than the 5 kHz
shown on the evaluation board, better supply filtering
at the resonators (and lower V
CC
noise as well) will
help reduce the phase noise of the VCO; a series
resistor of 100Ω to 200Ω and a 1µF or larger capacitor
Page 8
11-136
RF2917
Rev B2 010118
11
TRANSCEIVERS
may be used. Phase noise is generally more critical in
narrowband applications where adjacent channel
selectivity is a concern, but it can also contribute to
raising the noise floor of the receiver, thereby degrading sensitivity.
For the interface between the LNA and mixer, the coupling capacitor should be as close to the RF2917 pins
as possible, with the bias inductor being further away.
Once again, the value of the inductor may be changed
to compensate for trace inductance. The output impedance of the LNA is on the order of several kΩ, which
makesmatchingto50Ω difficult.Ifimagefilteringis
desired, a high impedance filter is recommended. If no
filtering is used, the match to the mixer input need not
be a good conjugate match, because of the high gain
of the IF amplifier stages. In fact, a conjugate match
between the LNA and mixer will not significantly
improve sensitivity, but will have an adverse effect on
system IIP3 and increase the likelihood of IF instability.
Because of the high gain of the IF section, care should
be taken in laying out the IF filtering and discriminator
components to minimize the possibility of instability. In
particular, inductive feedback may occur between the
inductor of a discrete (LC) discriminator and any inductor(s) in the IF interstages. Orthogonal placement of
inductors will generally m inimize coupling. Indicators
that an instability may exist include poor sensitivity and
a high RSSI level when no input signal is present.
The quadrature tank of the discriminator may be implemented with ceramic discriminators available from a
variety of sources. Thisdesign works well for wideband
applications, and where the temperature range is limited. The temperature coefficient of a ceramic discriminator may be on theorder of +
50 ppm/°C. An automatic
frequency control loop may be implemented using the
DC level of the FM OUT for feedback to an external
varactor on the reference crystal. An alternative to the
ceramic discriminator is an LC tank. The DEMOD IN
pin has a DC bias and must be DC-blocked. This can
be done either at the pin orat the ground side ofthe LC
tank (this must also be done if a parallel resistor is
used with a ceramic discriminator). The decision
whether to use an LC or a ceramic discriminator
should be based on the frequency deviation in the system, discriminator Q needed, and frequency and temperature tolerances. Tuning of the LC tank is required
to overcome the component tolerances in the tank.
PREDICTING AND MINIMIZING PLL LOCK TIME
The RF2917 implements a conventional on-chip PLL.
The VCO is followed by a prescaler, which divides
down the output frequency for comparison with the reference oscillator frequency. The output of the phase
discriminator is a sequence of pulse width modulated
current pulses in the required direction to steer the
VCO’s control voltage to maintain phase lock, with a
loop filter integrating the current pulses. The lock time
of this PLL is a combination of the loop transient
response time and the slew rate set by the phase discriminator output current, combined with the magnitude of the loop filter capacitance. A good
approximation for totallock time of the RF2917 is:
where D is a factor toaccount for theloop damping, F
C
is the loop cut frequency, C is the sum of all shunt
capacitors in the loop filter, and dV is the required step
voltage change to produce the desired frequency
change during the transient. For loops with low phase
margin (30° to 40°), use D=2, whereas for loops with
better phase margin (50° to 60°), use D=1.
To lock faster, C needs to be minimized.
1. Design the loop filter for the minimum phase margin
possible without causing loop instability problems; this
allowsCtobekeptataminimum.
2. Design the loop filter for the highest loop cut frequency possible without distorting low frequency modulation components; this also allows C to be kept at a
minimum.
LockTime
D
F
C
------ -
35000 CdV⋅⋅+=
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RF2917
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11
TRANSCEIVERS
Pin Out
1
2
3
4
5
6
7
8
24
23
22
21
20
19
18
17
VCC1
RX IN
GND1
LNA OUT
GND2
MIX IN
GND3
MIX OUT
DEMOD IN
IF2 OUT
FM OUT
RSSI
MUTE
VCC3
IF2 BP-
IF2 BP+
32 293031
IF1 IN-
IF1 IN+
IF1 BP+
IF1 BP-
IF1 OUT
VREF IF
GND5
IF2 IN
PD
OSC E
OSC B
LOOP FLT
GND4
VCC2
RESNTR+
RESNTR-
28 27 26 25
9121110 13 14 15 16
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TRANSCEIVERS
915MHz Application Schematic
D1 : SMV1233-011
13 16
22
20
8
6
Linear
RSSI
21
4
2
25 26
Prescaler
÷
64
Phase
Detector &
Charge Pump
29
31
30
109 17 181211 24
32
DC
BIAS
1
3
5
1423
10 nF22 pF 6.8 nH
3pF
D1
6.8 nH
100
Ω
3.9 k
Ω
3.3 nF
2.7 k
Ω
47 nF
PD
22 pF
10
Ω
10 nF
Filter
22 pF
10
Ω
10 nF
12 nH
10 pF
22 pF
10
Ω
10 nF
6.8µH
22 pF
Filter
15 pF
10 nF 10 nF 10 nF 0.1µF
Filter
10 nF 5pF
FM OUT
MUTE
RSSI
10 pF51 k
Ω
47 pF
47 pF
14.15099 MHz
V
CC
V
CC
10 nF
V
CC
V
CC
Page 11
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RF2917
Rev B2 010118
11
TRANSCEIVERS
Evaluation Board Schematic
H (915MHz), M (868MHz), L (433MHz) boards
(Download Bill of Materials from www.rfmd.com.)
13 16
22
20
8
6
Linear
RSSI
21
4
2
26 25
Prescaler
÷64
Phase
Detector &
Charge Pump
29
31
30
10
9
17 181211
32
DC
BIAS
1
3
5
23
C28
47 pF
C27
10 nF
L7*
D1***
L6*
R9
10 Ω
R10
3.9 kΩ
C30
3.3 nF
PD
C3
4.7 µF
R1
10 Ω
C7
47 pF
R2
10 Ω
C8*
L4
6.8 µH
F1
SFECV10.7MS3S-A-TC
f
O
=10.7 MHz
BW=180 kHz
C9
15 pF
C15
10 nF
C16
10 nF
C17
10 nF
C19
10 nF
C20
10 nF
MUTE
RSSI
C21
47 pF
R7
51 kΩ
C33*
C32*
X1*
VCC
C4*
VCC
7
R12
0 Ω
14
C18
10 nF
F2
SFECV10.7MS3S-A-TC
f
O
=10.7 MHz
BW=180 kHz
L1*
C5*
50 Ω µstrip
J1
RF IN
C6
10nF
L2*
C12
47 pF
C11
10 nF
C13
22 pF
L5
10 µH
C14
68 pF
50 Ω µstrip
J2
IF OUT
15
Drawing 2917400C, 401-,
402-
19 VCC
C23
10 pF
C22
10 nF
R6
10 Ω
C29* C31
47 nF
R11
2.7 kΩ
28 27
VCC
C2
47 pF
C1
10 nF
VCC
VCC
R4
10 Ω
*See table for values.
**Components not normally populated.
***D1 : SMV1233-011
24
J3
DATA OUT
C25
4pF
U2 (10.7 MHz)
CDF107B-A0-001
R8
1.5 kΩ
C26
10 nF
C24
100 pF
Ctrim*
3-10 pF
R13*
L (433MHz)
M (868MHz)
H (915MHz)
Board
2
1.5
2
C4 (pF)
27
8.2
6.8
L1 (nH)
33
12
12
L2 (nH)
9
3
3
C29 (pF)
510
-
-
R13 (Ω)
18
6.8
6.8
L6 (nH)
18
6.8
6.8
L7 (nH)
6.612813
13.41015
14.15099
X1 (MHz)
100
100
22
C5 (pF)
100
100
47
C32 (pF)
100
100
47
C33 (pF)
9
1
1
C8 (pF)
P2
1
2
3
P2-1 RSSI
GND
P2-3 MUTE
P1
1
2
3
P1-3 VCC
GND
P1-1 PD
RSW2**
Page 12
11-140
RF2917
Rev B2 010118
11
TRANSCEIVERS
Evaluation Board Layout - M and H
Board Size 2.0” x 2.0”
Board Thickness 0.040”, Board Material FR-4, Multi-Layer
(Same board layout is being used for the -M and -H versions.)
Page 13
11-141
RF2917
Rev B2 010118
11
TRANSCEIVERS
Evaluation Board Layout - L
Board Size 2.0” x 2.0”
Board Thickness 0.048”, Board Material FR-4, Multi-Layer
Page 14
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RF2917
Rev B2 010118
11
TRANSCEIVERS
Current versus Temperature
RX Frequency = 915MHz
6.0
7.0
8.0
9.0
10.0
11.0
12.0
-40.0 -30.0 -20.0 -10.0 0.0 10.0 20.0 30.0 40.0 50.0 60.0 70.0 80.0 90.0
Temperature (°C)
Current (mA)
Vcc=2.70
Vcc=3.60
Sensitivity versus Temperature
RX Frequency = 915MHz
-120.0
-110.0
-100.0
-90.0
-40.0 -30.0 -20.0 -10.0 0.0 10.0 20.0 30.0 40.0 50.0 60.0 70.0 80.0 90.0
Temperature (°C)
Sensitivity (dBm)
Vcc=2.70
Vcc=3.60
RSSI versus Input Power
R
LOAD
= 51k
ΩΩΩΩ
,VCC=3.6V,TA= 25°C
0.0
0.5
1.0
1.5
2.0
2.5
3.0
-130.0 -120.0 -110.0 -100.0 -90.0 -80.0 -70.0 -60.0 -50.0 -40.0 -30.0
InputPower (dBm)
RSSI (Volts)
FSK Mode
FM Mode
0
1.0
1.0-1.0
10.0
1
0
.
0
-
1
0
.
0
5.0
5
.
0
-
5
.
0
2.0
2
.
0
-
2
.
0
3.0
3
.
0
-
3
.
0
4.0
4
.
0
-
4
.
0
0.2
0
.
2
-
0
.
2
0.4
0
.
4
-
0
.
4
0.6
0
.
6
-
0
.
6
0.8
0
.
8
-
0
.
8
LNA Impedance
Swp Max
1GHz
Swp Min
0.3GHz
LNA Input (RX on)
LNA Input (RX off)
LNA Output
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