Datasheet PBL38640-2SHT, PBL38640-2SOS, PBL38640-2SOT, PBL38640-2QNS, PBL38640-2QNT Datasheet (Ericsson)

PBL 386 40/2

Description

The PBL 386 40/2 Subscriber Line Interface Circuit (SLIC) is a 90 V bipolar integrated
circuit for use in Digital Loop Carrier, FITL and other telecommunications equipment.
The PBL 386 40/2 has been optimized for low total line interface cost and a high
degree of flexibility in different applications.

The PBL 386 40/2 emulates resistive loop feed, programmable between 2x50 Ω
and 2x900 Ω, with short loop current limiting adjustable to max 45 mA. In the current
limited region the loop feed is nearly constant current with a slight slope correspond­ing to 2x30 kΩ.

A second, lower battery voltage may be connected to the device to reduce short
loop power dissipation. The SLIC automatically switches between the two battery
supply voltages without need for external components or external control.

The SLIC incorporates loop current, ground key and ring trip detection functions.
The PBL 386 40/2 is compatible with both loop and ground start signaling.

Two- to four-wire and four- to two-wire voice frequency (VF) signal conversion is
accomplished by the SLIC in conjunction with either a conventional CODEC/filter or
with a programmable CODEC/filter, e.g. SLAC, SiCoFi, Combo II. The programmable
two-wire impedance, complex or real, is set by a simple external network.

Longitudinal voltages are suppressed by a feedback loop in the SLIC and the
longitudinal balance specifications meet the DLC requirements.

The PBL 386 40/2 package options are 24-pin SSOP package, 24-pin SOIC and
28-pin PLCC.

Figure 1. Block diagram.

March 2000

PBL 386 40/2

Subscriber Line

Interface Circuit

Key Features

• 24-pin SSOP package

• High and low battery with automatic
switching

• 65 mW on-hook power dissipation in
active state

• On-hook transmission

• Long loop battery feed tracks Vbat for
maximum line voltage

• Only +5 V feed in addition to battery

• Selectable transmit gain (1x or 0.5x)

• No power-up sequence

• Programmable signal headroom

• 43V open loop voltage @ -48V battery
feed

• Constant loop voltage for line leakage
<5 mA (RLeak ~ >10 kΩ @ -48V)

• Full longitudinal current capability
during on-hook state

• Analog over temperature protection
permits transmission while the
protection circuit is active

• Line voltage measurement

• Polarity reversal

• Ground key detector

• Tip open state with ring ground
detector

• -40°C to +85°C ambient temperature
range

24-pin SOIC, 24-pin SSOP, 28-pin PLCC

RRLY

C1

C2

C3
DET

PSG

REF

LP

PLD

PLC

VTX

RSN

PTG

BGND

AGND

VBAT

VBAT2

VCC

HP

RINGX

TIPX

DR

DT

Ring Relay

Driver

Input

Decoder

and

Control

Ring Trip

Comparator

Ground Key

Detector

Line Feed
Controller

and

Longitudinal

Signal

Suppression

Off-hook
Detector

VF Signal

Transmission

Two-wire
Interface

POV

PB

L

386 40/2

1

PBL 386 40/2

PBL 386 40/2

2

Maximum Ratings

Parameter Symbol Min Max Unit

Temperature, Humidity

Storage temperature range T

Stg

-55 +150 °C

Operating temperature range T

Amb

-40 +110 °C

Operating junction temperature range, Note 1 T

J

-40 +140 °C

Power supply, -40°C ≤ T

Amb

≤ +85°C

V

CC

with respect to A/BGND V

CC

-0.4 6.5 V

V

Bat2

with respect to A/BGND V

Bat2

V

Bat

0.4 V

V

Bat

with respect to A/BGND, continuous V

Bat

-75 0.4 V

V

Bat

with respect to A/BGND, 10 ms V

Bat

-80 0.4 V

Power dissipation

Continuous power dissipation at T

Amb

≤ +85 °CP

D

1.5 W

Ground

Voltage between AGND and BGND V

G

-0.3 +0.3 V

Relay Driver

Ring relay supply voltage BGND+14 V

Ring trip comparator

Input voltage V

DT

, V

DR

V

Bat

AGND V

Input current I

DT

, I

DR

-5 5 mA

Digital inputs, outputs (C1, C2, C3, DET)
Input voltage V

ID

-0.4 V

CC

V

Output voltage V

OD

-0.4 V

CC

V

TIPX and RINGX terminals, -40°C < T

Amb

< +85°C, V

Bat

= -50V

Maximum supplied TIPX or RINGX current I

TIPX

, I

RINGX

-100 +100 mA

TIPX or RINGX voltage, continuous (referenced to AGND), Note 2 V

TA

, V

RA

-80 2 V

TIPX or RINGX, pulse < 10 ms, t

Rep

> 10 s, Note 2 VTA, V

RA

V

Bat

-10 5 V

TIPX or RINGX, pulse < 1 µs, t

Rep

> 10 s, Note 2 VTA, V

RA

V

Bat

-25 10 V

TIPX or RINGX, pulse < 250 ns, t

Rep

> 10 s, Notes 2 & 3 VTA, V

RA

V

Bat

-35 15 V

Recommended Operating Condition

Parameter Symbol Min Max Unit

Ambient temperature T

Amb

-40 +85 °C

V

CC

with respect to AGND V

CC

4.75 5.25 V

V

Bat

with respect to AGND V

Bat

-58 -8 V

AGND with respect to BGND V

G

-100 100 mV

Notes

1. The circuit includes thermal protection. Operation at or above 140°C junction temperature may degrade device reliability.

2. With the diodes DVB and D

VB2

included, see figure 12.

3. R

F1

and RF2 ≥ 20 Ω is also required. Pulse is applied to TIP and RING outside RF1 and RF2.

PBL 386 40/2

3

Electrical Characteristics

-40 °C ≤ T

Amb

≤ +85 °C, PTG = open (see pin description), VCC = +5V ±5 %, V

Bat

= -58V to -40V, V

Bat2

=-32V, RLC=32.4 kΩ,

I

L

= 27 mA. RL = 600 Ω, RF1=RF2=0, R

Ref

= 49.9 kΩ, CHP = 47nF, CLP=0.15 µF, RT = 120 kΩ, RSG = 0 kΩ, RRX = 60 kΩ,

R

R

= 52.3 kΩ, ROV =∞ unless otherwise specified. Current definition: current is positive if flowing into a pin.

Ref

Parameter fig Conditions Min Typ Max Unit

Two-wire port

Overhead voltage, V

TRO ,ILdc

> 18mA 2 Active state

1% THD, R

OV

= ∞ 2.7 V

Peak

On-Hook, I

Ldc

< 5mA Note 1 1.1 V

Peak

Input impedance, Z

TR

Note 2 ZT/200

Longitudinal impedance, Z

LOT

, Z

LOR

0 < f < 100 Hz 20 35 Ω/wire

Longitudinal current limit, I

LOT

, I

LOR

active state 28 mA

rms

/wire

Longitudinal to metallic balance, B

LM

IEEE standard 455-1985, Z

TRX

=736Ω

Normal polarity:

0.2 kHz < f < 1.0 kHz, T

amb

0-70°C63 66 dB

1.0 kHz < f < 3.4 kHz, T

amb

0-70°C60 66 dB

0.2 kHz < f < 1.0 kHz, T

amb

-40-85°C60 66 dB

1.0 kHz < f < 3.4 kHz, T

amb

-40-85°C55 66 dB

Reverse polarity:

0.2 kHz < f < 1.0 kHz, T

amb

0-70°C59 66 dB

1.0 kHz < f < 3.4 kHz, T

amb

0-70°C55 66 dB

0.2 kHz < f < 1.0 kHz, T

amb

-40-85°C55 66 dB

1.0 kHz < f < 3.4 kHz, T

amb

-40-85°C55 66 dB

Longitudinal to metallic balance, B

LME

3 Normal polarity:

Longitudinal to four wire balance B

LFE

3 0.2 kHz < f < 1.0 kHz, T

amb

0-70°C63 66 dB

1.0 kHz < f < 3.4 kHz, T

amb

0-70°C60 66 dB

0.2 kHz ≤ f ≤ 1.0 kHz, T

amb

-40-85°C60 66 dB

1.0 kHz < f < 3.4 kHz, T

amb

-40-85°C55 66 dB

Reverse polarity:

0.2 kHz < f < 1.0 kHz, T

amb

0-70°C59 66 dB

1.0 kHz < f < 3.4 kHz, T

amb

0-70°C55 66 dB

0.2 kHz < f < 1.0 kHz, T

amb

-40-85°C55 66 dB

1.0 kHz < f < 3.4 kHz, T

amb

-40-85°C55 66 dB

Metallic to longitudinal balance, B

MLE

4 0.2 kHz < f < 3.4 kHz 40 50 dB

VTR

B

MLE

= 20 · Log ; ERX = 0

V

Lo

Figure 2. Overhead voltage, V

TRO

, two-

wire port

1
<< R

L

, RL= 600 Ω

ωC
R

T

= 120 kΩ, RRX = 60 kΩ

PBL 386 40/2

TIPX

RINGX

RSN

VTX

R

T

R

RX

E

RX

R

L

V

TRO

I

LDC

C

PBL 386 40/2

TIPX

RINGX RSN

VTX

R

T

R

RX

V

TX

R

LT

C

V

TR

R

LR

E

Lo

Figure 3. Longitudinal to metallic (B

LME

)

and Longitudinal to four-wire (B

LFE

)

balance

1

<< 150 Ω, R

LR =RLT

=RL /2=300Ω

ωC

RT = 120 kΩ, RRX = 60 kΩ

B

LFE

= 20 · Log

E

Lo

VTX

B

LME

= 20 · Log

E

Lo

VTR

PBL 386 40/2

4

Parameter fig Conditions Min Typ Max Unit

Four-wire to longitudinal balance, B

FLE

4 0.2 kHz < f < 3.4 kHz 40 50 dB

E

RX

B

FLE

= 20 · Log

V

Lo

Two-wire return loss, r |ZTR + ZL|

r = 20 · Log

|Z

TR

- ZL|

0.2 kHz < f < 1.0 kHz 30 35 dB

1.0 kHz < f < 3.4 kHz, Note 3 20 22 dB

TIPX idle voltage, V

Ti

active, IL < 5 mA - 1.3 V

RINGX idle voltage, V

Ri

active, IL < 5 mA V

Bat

+3.0 V

tip open, I

L

< 5 mA V

Bat

+3.0 V

V

TR

active, IL < 5 mA V

Bat

+4.3 V

Four-wire transmit port (VTX)
Overhead voltage, V

TXO

, IL > 18mA 5 Load impedance > 20 kΩ, 2.7 V

Peak

1% THD, Note 4

On-hook, I

L

< 5mA 1.1 V

Peak

Output offset voltage, ∆V

TX

-100 0 100 mV

Output impedance, z

TX

0.2 kHz < f < 3.4 kHz 15 50 Ω

Four-wire receive port (RSN)
Receive summing node (RSN) DC voltage I

RSN

= -55 µA 1.15 1.25 1.35 V
Receive summing node (RSN) impedance 0.2 kHz < f < 3.4 kHz 8 20 Ω
Receive summing node (RSN) 0.3 kHz < f < 3.4 kHz
current (I

RSN

) to metallic loop current (IL) 200 ratio

gain,α

RSN

Frequency response

Two-wire to four-wire, g

2-4

6 relative to 0 dBm, 1.0 kHz. ERX = 0 V

0.3 kHz < f < 3.4 kHz -0.20 0.10 dB
f = 8.0 kHz, 12 kHz, 16 kHz -1.0 0.1 dB

Figure 4. Metallic to longitudinal and four­wire to longitudinal balance

1
<< 150 Ω, R

LT

=RLR =RL /2 =300Ω

ωC
R

T

= 120 kΩ, RRX = 60 kΩ

Figure 5. Overhead voltage, V

TXO

, four-

wire transmit port

1
<< R

L

, RL = 600 Ω

ωC
R

T

= 120 kΩ, RRX = 60 kΩ

Ref

PBL 386 40/2

TIPX

RINGX RSN

VTX

R

T

R

RX

E

RX

R

LT

C

V

TR

R

LR

V

Lo

PBL 386 40/2

TIPX

RINGX RSN

VTX

R

T

R

RX

R

L

I

LDC

C

E

L

V

TXO

PBL 386 40/2

5

Four-wire to two-wire, g

4-2

6 relative to 0 dBm, 1.0 kHz. EL=0 V

0.3 kHz < f < 3.4 kHz -0.2 0.1 dB
f = 8 kHz, 12 kHz, -1.0 0 dB
16 kHz -2.0 0 dB

Four-wire to four-wire, g

4-4

6 relative to 0 dBm, 1.0 kHz, EL =0 V

0.3 kHz < f < 3.4 kHz -0.2 0.1 dB

Insertion loss

Two-wire to four-wire, G

2-4

6 0 dBm, 1.0 kHz, Note 5

V

TX

G

2-4

= 20 · Log ; ERX = 0 -0.2 0.2 dB

V

TR

PTG = AGND -6.22 -6.02 -5.82 dB

Four-wire to two-wire, G

4-2

6 0 dBm, 1.0 kHz, Note 6

V

TR

G

4-2

= 20 · Log ; EL = 0 -0.2 0.2 dB

E

RX

Gain tracking

Two-wire to four-wire 6 Ref. -10 dBm, 1.0 kHz, Note 7

-40 dBm to + 3 dBm -0.1 0.1 dB

-55 dBm to -40 dBm -0.2 0.2 dB

Four-wire to two-wire 6 Ref. -10 dBm, 1.0 kHz,

-40 dBm to + 3 dBm -0.1 0.1 dB

-55 dBm to -40 dBm -0.2 0.2 dB

Noise

Idle channel noise at two-wire C-message weighting 12 dBrnC
(TIPX-RINGX) or four-wire (VTX) output Psophometrical weighting -78 dBmp

Note 8

Harmonic distortion

Two-wire to four-wire 6 0 dBm -67 -50 dB
Four-wire to two-wire 0.3 kHz < f < 3.4 kHz -67 -50 dB

Battery Feed characteristics

Loop current, I

L

, in the current 13

limited region, reference A, B & C 18mA ≤ IL ≤ 45 mA 0.92 I

L

I

L

1.08 ILmA

Tip open state TIPX current, I

Leak

7 S = closed; R = 7 kΩ, note 10 -100 µA

Tip open state RINGX current, I

LRTo

7R

LRTo

= 0Ω, V

Bat

= -48V I

L

mA

R

LRTo

= 2.5 kΩ, V

Bat

= -48V 17 mA

Tip open state RINGX voltage, V

RTo

7I

LRTo

< 23 mA V

Bat

+ 6 V

Tip voltage (ground start) 7 Active state, Tip lead open (S open), -4 -2.2 V

Ring lead to ground through 150 Ω

Ref

Parameter fig Conditions Min Typ Max Unit

Figure 6.
Frequency response, insertion loss,
gain tracking.

1
<< R

L

, RL = 600 Ω

ωC
R

T

= 120 kΩ, RRX = 60 kΩ

PBL 386 40/2

TIPX

RINGX RSN

VTX

R

T

R

RX

E

RX

R

L

V

TR

I

LDC

C

E

L

V

TX

PBL 386 40/2

6

Tip voltage (ground start) 7 Active state, Tip lead to -48 V -6 -2.4 V

through 7 kΩ (S closed), Ring
lead to ground through 150 Ω

Open circuit state loop current, I

LOC

RL = 0Ω -100 0 100 µA

Loop current detector

Programmable threshold, I

LTh

,

I

LTh

=

500

0.85·I

LThILTh

1.15·I

LTh

mA

active, active reverse

R

LD

RLD in kΩ, I

LTh

≥ 7 mA

Tip open state

I

LTh

=

500 0.85·I

LThILTh

1.15·I

LTh

mA

R

LD

Ground key detector

Ground key detector threshold
(I

LTIPX

and I

LRINGX

current difference to trigger ground key det.) 10 16 22 mA

Line voltage measurement

Pulse width, t

LVM

Note 9 5.5 µs/V

Ring trip comparator

Offset voltage, ∆V

DTDR

Source resistance, RS = 0 Ω -20 0 20 mV

Input bias current, I

B

IB = (IDT + IDR)/2 -200 -20 200 nA

Input common mode range, VDT, V

DR

V

Bat

+1 -1 V

Ring relay driver

Saturation voltage, V

OL

IOL = 50 mA 0.2 0.5 V

Off state leakage current, I

Lk

V

OH

= 12 V 10 µA
Digital inputs (C1, C2, C3)
Input low voltage, V

IL

0 0.5 V

Input high voltage, V

IH

2.5 V

CC

V

Input low current, I

IL

VIL = 0.5 -50 µA

Input high current, I

IH

VIH = 2.5 V 50 µA
Detector output (DET)
Output Low Voltage IOL = 0.5 mA 0.7 V
Internal pull-up resistor 15 kΩ
Power dissipation (V

Bat

= -48V, V

Bat2

= -32 V)

P

1

Open circuit state, C1, C2, C3 = 0, 0, 0 10 15 mW
P

2

Active state, C1, C2, C3 = 0, 1, 0

Longitudinal current = 0 mA, I L=0 mA (on-hook) 65 85 mW
P

3

RL=300 Ω (off-hook) 730 mW
P

4

RL=800 Ω (off-hook) 360 mW
Power supply currents (V

Bat

= -48V)

V

CC

current, I

CC

Open circuit state 1.2 2 mA
V

Bat

current, I

Bat

-0.1 -0.05 mA

V

CC

current, I

CC

Active state 2.8 4 mA
V

Bat

current, I

Bat

On-hook, Long Current = 0 mA -1.5 -1.0 mA

Power supply rejection ratios

V

CC

to 2- or 4-wire port Active State 30 42 dB

V

Bat

to 2- or 4-wire port f = 1 kHz, Vn = 100mV 36 45 dB

V

Bat2

to 2- or 4-wire port 40 60 dB

Temperature guard

Junction threshold temperature, T

JG

145 °C

Thermal resistance

24-pin SSOP, θ

JP24ssop

55 °C/W

24-pin SOIC, θ

JP24soic

43 °C/W

28-pin PLCC, θ

JP28plcc

39 °C/W

Parameter fig Conditions Min Typ Max Unit

Ref

PBL 386 40/2

7

Notes

1. The overhead voltage can be adjusted with the R

OV

resistor for higher levels e.g. min 3.1 V

Peak

and is specified
at the two-wire port with the signal source at the four-wire
receive port.

2. The two-wire impedance is programmable by selection of
external component values according to:

Z

TRX

= ZT/|G

2-4S α RSN

| where:

Z

TRX

= impedance between the TIPX and RINGX

terminals

ZT= programming network between the VTX and RSN

terminals

G

2-4S

= transmit gain, nominally = 1 (or 0.5 see pin PTG)

α

RSN

= receive current gain, nominally = 200 (current

defined as positive flowing into the receive summ­ing node, RSN, and when flowing from ring to tip).

3. Higher return loss values can be achieved by adding a
reactive component to R

T

, the two-wire terminating

impedance programming resistance, e.g. by dividing R

T

into two equal halves and connecting a capacitor from the
common point to ground.

4. The overhead voltage can be adjusted with the R

OV

resistor for higher levels e.g. min 3.1 V

Peak

and is specified
at the four-wire transmit port, VTX, with the signal source
at the two-wire port. Note that the gain from the two-wire
port to the four-wire transmit port is G

2-4S

= 1 (or 0.5 see

pin PTG)

5. Pin PTG = Open sets transmit gain to nom. 0.0dB
Pin PTG = AGND sets transmit gain to nom. -6.02 dB
Secondary protection resistors RF impact the insertion
loss as explained in the text, section Transmission. The
specified insertion loss is for R

F

= 0.

6. The specified insertion loss tolerance does not include
errors caused by external components.

7. The level is specified at the two-wire port.

8. The two-wire idle noise is specified with the port
terminated in 600 Ω (R

L

) and with the four-wire receive

port grounded (E

RX

= 0; see figure 6).
The four-wire idle noise at VTX is specified with the two­wire port terminated in 600 Ω (R

L

). The noise
specification is referenced to a 600 Ω programmed two­wire impedance level at VTX. The four-wire receive port is
grounded (E

RX

= 0).

9. Previous state must be active - loop or ground key
detector.

10. If |V

BExt

| ≥ |V

Bat

+ 2 V|, where V

Bat

is the voltage at V

BAT

pin,

the current I

Leak

is limited to ≈ 5mA.

Figure 7. Tipx voltage.

PBL 386 40/2

TIPX

RINGX

S

R

LRTo

R

V

BExt

PBL 386 40/2

8

Pin Description

Figure 8. Pin configuration, 24-pin SOIC, 24-pin SSOP and 28 pin PLCC package, top view.

Refer to figure 8.

PLCC Symbol Description

1 PTG Prog. Transmit Gain. Left open transmit gain = 0.0 dB, connected to AGND transmit gain = -6.02 dB.
2 RRLY Ring Relay driver output. The relay coil may be connected to maximum +14V.
3 HP Connection for High Pass filter capacitor, CHP. Other end of CHP connects to TIPX.
4NCNo internal Connection
5 RINGX The TIPX and RINGX pins connect to the tip and ring leads of the two-wire interface via overvoltage

protection components and ring relay (and optional test relay).
6 BGND Battery Ground, should be tied together with AGND.
7 TIPX The TIPX and RINGX pins connect to the tip and ring leads of the two-wire interface via overvoltage

protection components and ring relay (and optional test relay).
8 VBAT Battery supply Voltage. Negative with respect to AGND.
9 VBAT2 An optional second (2) Battery Voltage connects to this pin.
10 PSG Programmable Saturation Guard. The resistive part of the DC Feed characteristic is programmed by a

resistor connected from this pin to VBAT.
11 NC No internal Connection
12 LP Connection for Low Pass filter capacitor, C

LP

. Other end of CLP connects to VBAT.

13 DT Input to the ring trip comparator. With DR more positive than DT the detector output, DET, is at logic level

low, indicating off-hook condition. The external ring trip network connects to this input.
14 DR Input to the ring trip comparator. With DR more positive than DT the detector output, DET, is at logic

level low, indicating off-hook condition. The external ring trip network connects to this input.

1

2

3

4

5

6

7

8

9

10
11

24
23
22
21
20
19
18
17
16
15
14

RRLY

PTG

HP

RINGX

BGND

TIPX

VBAT

LP

POV

VTX
AGND

C2

RSN
REF

PLD
VCC

C1

DT

PSG

PLC

VBAT2

DET

12

13

DR

C3

24-pin SOIC

and

24-pin SSOP

5
6
7
8

9
10
11

25
24
23
22
21
20
19

4

3

2

1

28

27

26

12

13

14

15

16

17

18

PTG

RRLY

HP

NC

BGND

TIPX

VBAT

VBAT2

PSG

LP

NC

DT

DR

C3

C2

C1

DET

NC

PLD

POV

PLC

REF

NC

AGND

VTX

RSN

VCC

RINGX

28-pin PLCC

PBL 386 40/2

9

SLIC Operating States

State C3 C2 C1 SLIC operating state Active detector

0000Open circuit ­1001Ringing state Ring trip detector (active low)
2010Active state Loop detector (active low)
3011Active state Line voltage measurement (note 9)
4100Tip open state Loop detector (active low)
5101Active state Ground key detector (active high)
6110Active reverse Loop detector (active low)
7111Active reverse Ground key detector (active high)

Table 1. SLIC operating states.

15 C3

C1, C2 and C3 are digital inputs (internal pull-up) controlling the SLIC operating states.

16 C2

Refer to section "Operating states" for details.

17 C1
18 DET Detector output. Active low when indicating loop detection and ring trip, active high when indicating

ground key detection.
19 NC No internal Connection
20 VCC +5 V power supply.
21 PLD Programmable Loop Detector threshold. The loop detection threshold is programmed by a resistor

connected from this pin to AGND.
22 POV Programmable Overhead Voltage. If pin is left open: The overhead voltage is internally set to min 2.7 V in

off-hook and min 1.1 V in On-hook. If a resistor is connected between this pin and AGND: the overhead

voltage can be set to higher values.
23 PLC Prog. Line Current, the current limit, reference C in figure 13, is programmed by a resistor connected

from this pin to AGND.
24 REF A Reference, 49.9 kΩ, resistor should be connected from this pin to AGND.
25 NC No internal Connection
26 RSN Receive Summing Node. 200 times the AC-current flowing into this pin equals the metallic (transversal)

AC-current flowing from RINGX to TIPX. Programming networks for two-wire impedance and receive

gain connect to the receive summing node. A resistor should be connected from this pin to AGND.
27 AGND Analog Ground, should be tied together with BGND.
28 VTX Transmit vf output. The AC voltage difference between TIPX and RINGX, the AC metallic voltage, is

reproduced as an unbalanced GND referenced signal at VTX with a gain of one (or one half, see pin

PTG). The two-wire impedance programming network connects between VTX and RSN.

}

PBL 386 40/2

10

Transmission

General

A simplified ac model of the transmission
circuits is shown in figure 9. Circuit
analysis yields:

(1)

(2)

V

TR

= EL - IL · Z

L

(3)

where:
V

TX

is a ground referenced version of
the ac metallic voltage between the
TIPX and RINGX terminals.

G

2-4S

is the programmable SLIC two-wire
to four-wire gain (transmit
direction). See note below.

VTRis the ac metallic voltage between

tip and ring.

E

L

is the line open circuit ac metallic
voltage.

I

L

is the ac metallic current.

R

F

is a fuse resistor.

RPis part of the SLIC protection.

Z

L

is the line impedance.

Functional Description
and Applications Infor­mation

VZV

Z

I

TXTRX

RXLRSN

+=

α

ZTdetermines the SLIC TIPX to

RINGX impedance at voice

frequencies.
ZRXcontrols four- to two-wire gain.
V

RX

is the analog ground referenced

receive signal.

α

RSN

is the receive summing node

current to metallic loop current

gain = 200.
Note that the SLICs two-wire to four-wire

gain, G

2-4S

, is user programmable
between two fix values. Refer to the
datasheets for values on G

2-4S

.

Two-Wire Impedance

To calculate Z

TR

, the impedance pre­sented to the two-wire line by the SLIC
including the fuse and protection
resistors RF and RP, let:

V

RX

= 0.

From (1) and (2):

Thus with Z

TR

, α

RSN

, G

2-4S

, RP and R

F

known:

Two-Wire to Four-Wire Gain

From (1) and (2) with VRX = 0:

V

V

G

IR R

TR

TX

S

LFP

=+⋅+

−24

22()

Z

Z

G

RR

TR

T

RSN S

FP

=

⋅

++

−α24

22

ZGZRR

T RSN S TR F P

=⋅ ⋅−−

−α24

22()

G

V
V

Z

Z

G

RR

TX
TR

T RSN

T

RSN S

FP

24

24

22

−

−

==

⋅

++

/ α

α

Four-Wire to Two-Wire Gain

From (1), (2) and (3) with E

L

= 0:

For applications where
ZT/(α

RSN·G2-4S

) + 2RF + 2RP is chosen to

be equal to ZL the expression for G

4-2

simplifies to:

Four-Wire to Four-Wire Gain

From (1), (2) and (3) with E

L

= 0:

Hybrid Function

The hybrid function can easily be
implemented utilizing the uncommitted
amplifier in conventional CODEC/filter
combinations. Please, refer to figure 10.
Via impedance ZB a current proportional
to VRX is injected into the summing node
of the combination CODEC/filter ampli­fier. As can be seen from the expression
for the four-wire to four-wire gain a
voltage proportional to VRX is returned to
VTX. This voltage is converted by RTX to a
current flowing into the same summing
node. These currents can be made to
cancel by letting:

The four-wire to four-wire gain, G

4-4

,
includes the required phase shift and
thus the balance network ZB can be
calculated from:

Figure 9. Simplified ac transmission circuit.

V
R

V

Z

E

TXTXRX

B

L

+==00()

G

Z

ZG

T

RX S4224

1

2

−

−

=− ⋅

G

V
V

Z

Z

Z

Z

GZRR

TR
RX

T

RX

L

T

RSN

SL F P

42

24

22

−

−

==

−⋅

+⋅++

α

()

G

V
V

Z

Z

GZRR

Z

GZRR

TX
RX

T

RX

SL F P

T

RSN

SL F P

44

24

24

22

22

−

−

−

==

−⋅

⋅+ +

+⋅++

()

()

α

ZR

V
V

R

Z

Z

Z

GZRR

GZRR

BTX

RX

TX

TX

RX

T

T

RSN

SL F P

SL F P

=− ⋅ =

⋅⋅

+⋅++

⋅++

−

−

α

24

24

22

22

()

()

PBL 386 40/2

+

-

+

-

VTX

RSN

I

L

/

α

RSN

TIPX

RINGX

+

-

E

L

+

-

TIP

RING

R

F

R

F

Z

TR

Z

T

V

TX

V

RX

Z

RX

I

L

I

L

R

HP

+

-

Z

L

V

TR

R

P

G

2-4S

R

P

PBL 386 40/2

11

Figure 10. Hybrid function.

When choosing RTX, make sure the output
load of the VTX terminal is >20 kΩ.

If calculation of the ZB formula above
yields a balance network containing an
inductor, an alternate method is recom­mended. Contact Ericsson Microelectron­ics for assistance.

The PBL 386 40/2 SLIC may also be
used together with programmable
CODEC/filters. The programmable
CODEC/filter allows for system controller
adjustment of hybrid balance to accom­modate different line impedances without
change of hardware. In addition, the
transmit and receive gain may be ad­justed. Please, refer to the programm­able CODEC/filter data sheets for design
information.

Longitudinal Impedance

A Feed back loop counteracts longitudi­nal voltages at the two-wire port by
injecting longitudinal currents in opposing
phase.

Thus longitudinal disturbances will
appear as longitudinal currents and the
TIPX and RINGX terminals will experi­ence very small longitudinal voltage
excursions, leaving metallic voltages well
within the SLIC common mode range.

The SLIC longitudinal impedance per
wire, Z

LoT

and Z

LoR

, appears as typically
20 Ω to longitudinal disturbances. It
should be noted that longitudinal currents
may exceed the dc loop current without
disturbing the vf transmission.

Capacitors CTC and C

RC

The capacitors designated CTC and C

RC

in figure 12, connected between TIPX
and ground as well as between RINGX
and ground, can be used for RFI filter­ing.. The recommended value for C

TC

and CRC is 2200 pF. Higher capacitance
values may be used, but care must be
taken to prevent degradation of either
longitudinal balance or return loss. C

TC

and CRC contribute to a metallic imped­ance of 1/(π·f·CTC) = 1/(π·f·CRC), a TIPX to
ground impedance of 1/(2·π·f·CTC) and a
RINGX to ground impedance of 1/
(2·π·f·CRC).

AC - DC Separation Capacitor, C

HP

The high pass filter capacitor connected
between terminals HP and TIPX provides
the separation of the ac signal from the
dc part. CHP positions the low end

V

T

Combination
CODEC/Filter

R

TX

R

FB

Z

B

Z

RX

Z

T

VTX

RSN

V

RX

PBL

386 40/2

frequency response break point of the ac
loop in the SLIC. Refer to table 1 for
recommended values of CHP.
Example: A CHP value of 150 nF will
position the low end frequency response
3dB break point of the ac loop at 1.8 Hz
(f

3dB

) according to f

3dB

= 1/(2·π·RHP·CHP)

where RHP = 600 kΩ.

High-Pass Transmit Filter

The capacitor C

TX

in figure 12 connected
between the VTX output and the
CODEC/filter forms, together with R

TX

and/or the input impedance of a pro­grammable CODEC/filter, a high-pass
RC filter. It is recommended to position
the 3 dB break point of this filter between
30 and 80 Hz to get a faster response for
the dc steps that may occur at DTMF
signalling.

Capacitor C

LP

The capacitor CLP, which connects between
the terminals CLP and VBAT, positions
together with the resistive loop feed resis­tor RSG (see section Battery Feed), the high
end frequency break point of the low pass
filter in the dc loop in the SLIC. CLP together
with RSG, CHP and ZT (see section Two-Wire
Impedance) forms the total two wire output

impedance of the SLIC. The choise of
these programmable components have an
influence on the power supply rejection
ratio (PSRR) from VBAT to the two wire
side at sub-audio frequencies. At these
frequencies capacitor C

LP

also influences
the transversal to longitudinal balance in
the SLIC. Table 1 suggests suitable values
on CLP for different Feeding characteristics.
Typical values of the transversal to longitu­dinal balance (T-L bal.) at 200Hz is given in
table 1 for the chosen values on C

LP

.

R

Feed

R

SG

C

LP

T-L bal. C

HP

@200Hz

[Ω][kΩ] [nF] [dB] [nF]

2⋅50 0 150 -46 47
2⋅200 60.4 100 -46 150
2⋅400 147 47 -43 150
2⋅800 301 22 -36 150

Table 1. R

SG

, CLP and CHP values for

different Feeding characteristics.

PBL 386 40/2

12

Battery Feed

The PBL 386 40/2 SLIC emulate resistive
loop Feed, programmable between
2·50Ω and 2·900 Ω, with adjustable
current limitation. In the current limited
region the loop current has a slight slope
corresponding to 2·30 kΩ, see figure 13
reference B.

The open loop voltage measured
between the TIPX and RINGX terminals
is tracking the battery voltage V

Bat

. The
signalling headroom, or overhead voltage
V

TRO

, is programmable with a resistor R

OV

connected between terminal POV on the
SLIC and ground. Please refer to section
“Programmable overhead voltage(POV)”.

The battery voltage overhead, VOH,
depends on the programmed signal
overhead voltage V

TRO

. VOH defines the
TIPX to RINGX voltage at open loop
conditions according to VTR(at IL = 0 mA)
= |V

Bat

| - VOH.

Refer to table 2 for typical values on

VOH and V

OHVirt

. The overhead voltage is
changed when the line current is ap­proaching open loop conditions. To
ensure maximum open loop voltage,
even with a leaking telephone line, this
occurs at a line current of approximately
6 mA. When the overhead voltage has
changed, the line voltage is kept nearly
constant with a steep slope correspon­ding to 2

·25 Ω(reference G in figure 13).

The virtual battery overhead, V

OHVirt

, is
defined as the difference between the
battery voltage and the crossing point of
all possible resistive Feeding slopes, see
figure 13 reference J. The virtual battery
overhead is a theoretical constant
needed to be able to calculate the
Feeding characteristics.

SLIC V

OH(typ)

V

OHVirt(typ)

[V] [V]

PBL 386 40/2 3.0 +V

TRO

4.9 +V

TRO

Table 2. Battery overhead.

The resistive loop Feed (reference D in
figure 13) is programmed by connecting
a resistor, RSG, between terminals PSG
and VBAT according to the equation:

R

Feed

=

RSG + 2·104

+ 2R

F

200
where R

Feed

is in Ω for RSG, and RF in Ω.

−=+ +=

+

−
+

IIII

R

V

RR

RSN RT RRX RR

T

CODEC

RX R

125 125 125,, ,

R

I

R

V

R

R

RSN

T

CODEC

RX

=

−− −

−

125

125

125

,

,

,

The current limit (reference C in figure

13) is adjusted by connecting a resistor,
RLC, between terminal PLC and ground
according to the equation:

R

LC

=

1000

I

LProg

+ 4

where R

LC

is in kΩ for I

LProg

in mA.

A second, lower battery voltage may
be connected to the device at terminal
VBAT2 to reduce short loop power
dissipation. The SLIC automatically
switches between the two battery supply
voltages without need for external
control. The silent battery switching
occurs when the line voltage passes the
value |VB2| - 40·IL - (V

OHVirt

-1.3),

if IL > 6 mA.

For correct functionality it is important
to connect the terminal VBAT2 to the
second power supply via the diode D

VB2

in figure 12.

An optional diode D

BB

connected
between terminal VB and the VB2 power
supply, see figure 12, will make sure that
the SLIC continues to work on the
second battery even if the first battery
voltage disappears.

If a second battery voltage is not used,
VBAT2 is connected to VBAT on the
SLIC and C

VB2

, DBB and D

VB2

are re-

moved.

Metering applications

For designs with metering applications
please contact Ericsson Microelectronics
for assistance.

CODEC Receive Interface

The PBL 386 40/2 SLIC have got a
completely new receive interface at the
four wire side which makes it possible to
reduce the number of capacitors in the
applications and to fit both single and
dual battery Feed CODECs. The RSN
terminal, connecting to the CODEC

receive output via the resistor R

RX

, is dc
biased with +1.25V. This makes it
possible to compensate for currents
floating due to dc voltage differences
between RSN and the CODEC output
without using any capacitors. This is
done by connecting a resistor RR be­tween the RSN terminal and ground.
With current directions defined as in
figure 14, current summation gives:

where V

CODEC

is the reference voltage of
the CODEC at the receive output.
From this equation the resistor RR can be
calculated as

For values on I

RSN

, see table 3.
The resistor RR has no influence on the
ac transmission.

SLIC I

RSN

[µA]

PBL 386 40/2 -55

Table 3. The SLIC internal bias current
with the direction of the current defined
as positive when floating into the terminal
RSN.

Programmable overhead voltage(POV)

With the POV function the overhead

voltage can be increased.

If the POV pin is left open the overhead

voltage is internally set to 3,2 V

Peak

in off-

hook and 1,3 V

Peak

on-hook. If a resistor

R

OV

is connected between the POV pin

0 102030405060

0

1

2

3

4

5

6

7

V

TRO

(V

Peak

)

Rov (KΩ)

off-hook
on-hook

Figure 11. Programmable overhead voltage (POV). RL = 600 Ω or ∞.

PBL 386 40/2

13

Figure 12. Single-channel subscriber line interface with PBL 386 40/2 and combination CODEC/filter.

RESISTORS: (Values according to IEC E96 series)

R

SG

= 0 Ω 1% 1/10 W

R

LD

= 49.9 kΩ 1% 1/10 W

R

OV

= User programmable

R

LC

= 32.4 kΩ 1% 1/10 W

R

REF

= 49.9 kΩ 1% 1/10 W

R

R

= 64.9 kΩ 1% 1/10 W

R

T

= 105 kΩ 1% 1/10 W

R

TX

= 24.9 kΩ 1% 1/10 W

R

B

= 22.1 kΩ 1% 1/10 W

R

RX

= 52.3 kΩ 1% 1/10 W

R

FB

Depending on CODEC / filter

R

1

= 604 kΩ 1% 1/10 W

R

2

= 604 kΩ 1% 1/10 W

R

3

= 249 kΩ 1% 1/10 W

R

4

= 280 kΩ 1% 1/10 W

R

RT

= 330 Ω 5% 2 W

R

P1

, R

P2

= 10 Ω 1% 1/10 W (Note 1)

R

F1

, R

F2

= Line resistor, 40 Ω 1% match

CAPACITORS: (Values according to IEC E96
series)

C

VB

= 100 nF 100 V 10%

C

VB2

= 150 nF 100 V 10%

C

VCC

= 100 nF 10 V 10%

C

TC

= 2.2 nF 100 V 10%

C

RC

= 2.2 nF 100 V 10%

C

HP

= 47 nF 100 V 10%

C

LP

= 150 nF 100 V 10%

C

TX

= 100 nF 10 V 10%

C

GG

= 220 nF 100 V 10%

C

1

= 330 nF 63 V 10%

C

2

= 330 nF 63 V 10%

DIODES:

D

VB

= 1N4448

D

VB2

= 1N4448

D

BB

= 1N4448

D

HP

= 1N4448 (Note 2)

OVP:

Secondary protection (e.g. Power
Innovations TISPPBL2). The ground
terminals of the secondary protection should
be connected to the common ground on the
Printed Board Assembly with a track as
short and wide as possible, preferable a
groundplane.

R

LC

R

RX

R

REF

R

LD

C

VCC

C

TX

PBL 386 40/2

R

TX

0

-

+

0

CODEC/

Filter

R

FB

SYSTEM CONTROL

INTERFACE

R

R

R

T

R

B

­+

VCC

VCC

BGND

TIPX

VBAT

VBAT2

PLC

POV

PLD

VCC

PSG

NC

LP

DT

NC

DET

C1

C2

RRLY

HP

NC

RINGX

AGND

RSN

NC

REF

PTG VTX

DR C3

PBL 386 40/2

R

OV

R

SG

C

LP

C

1

R

4

C

2

R

3

C

HP

VB2

SLIC No. 2 etc.

C

RC

R

P2

R

P1

R

F2

R

F1

TIP

RING

OVP

C

GG

C

TC

VB

+12 V /+5V

K

R

C

VB

D

VB2

C

VB2

D

BB

VB

D

VB

R

RT

E

RG

R

2

R

1

D

HP

and AGND, the overhead voltage can be
set to higher values, typical values can
be seen in figure 11. The R

OV

and

corresponding V

TRO

(signal headroom)
are typical values for THD <1% and the
signal frequency 1000Hz.

Observe that the 4-wire output terminal

V

TX

can not handle more than 3,2 V

Peak.

So if the gain 2-wire to 4-wire is 0dB,
3,2 V

Peak

is maximum also for the 2-wire
side. Signal levels between 3,2 and
6,4 V

Peak

on the 2-wire side can be
handled with the PTG shorted so that the
gain G

2-4S

become -6,02dB. Please note

that the 2-wire impedance, R

R

and the
4-wire to 4-wire gain has to be recalcu­lated if the PTG is shorted.

Please note that the maximum signal
current at the 2-wire side can not be
greater than 9 mA.

How to use POV:

1. Decide what overhead voltage(V

TRO

)
is needed. The POV function is only
needed if the overhead voltage
exceeds 3,2 V

Peak

2. In figure 11 the corresponding ROV for
the decided V

TRO

can be found.

3. If the overhead voltage exceeds
3,2 V

Peak

, the G

2-4S

gain has to be
changed to -6,02dB by connecting
the PTG pin to AGND. Please note
that the two-wire impedance, RR and
the 4-wire to 4-wire gain has to be
recalculated.

Analog Temperature Guard

The widely varying environmental
conditions in which SLICs operate may
lead to the chip temperature limitations
being exceeded. The PBL 386 40/2 SLIC
reduce the dc line current when approxi­mately 145°C and increases it again
automatically when the temperature
drops. Accordingly transmission is not
lost under high ambient temperature
conditions.

The detector output, DET, is forced to
a logic low level when the temperature
guard is active.

NOTES:

1. R

P1

and R

P2

may be omitted if D

VB

is in place.

2. It is required to connect D

HP

between terminal

HP and ground if C

HP

> 47nF

PBL 386 40/2

14

Figure 13. Battery Feed characteristics (without the protection resistors on the line).

A: IL (@ VTR = 0V) = I

LProg

+

|V

Bat

| - V

OHVirt

- R

Feed

· (I

LProg

+ 4·10-3)

60 · 10

3

B: R

FeedB

= 2 · 30 kΩ

C: I

LConst

(typ) = I

LProg

=

10

3

- 4·10

-3

R

LC

VTR = |V

Bat

| - V

OHVirt

- R

Feed

· (I

LProg

+ 4·10-3)

D: R

Feed

=

R

SG

+ 2 · 10

4

200

E: I

L

≈ 6 mA

F: Apparent battery V

Bat

(@ IL = 0) =|V

Bat

| - V

OHVirt

- R

Feed

· 4·10-3)

G: R

FeedG

= 2 · 25 Ω

H: V

TROpen

= |V

Bat

| - V

OH

J: Virtual battery V

Batvirt

(@ IL = 4 mA) = |V

Bat

| - V

OHVirt

Loop Monitoring Functions

The loop current, ground key and ring trip
detectors report their status through a
common output, DET. The detector to be
connected to DET is selected via the
three bit wide control interface C1, C2
and C3. Please refer to section Control
Inputs for a description of the control
interface.

Loop Current Detector

The loop current detector is indicating
that the telephone is off hook and that
current is flowing in the loop by putting
the output DET to a logical low level
when selected.The loop current threshold
value, I

LTh

, at which the loop current
detector changes state is programmable
by selecting the value of resistor RLD. R

LD

connects between pin PLD and ground

and is calculated according to

R

LD

=

500

I

LTh

the current detector is internally filtered
and is not influenced by the ac signal at
the two wire side.

Ground Key Detector

The ground key detector is indicating
when the ground key is pressed (active)
by putting the output pin DET to a logical
high level when selected. The ground
key detector circuit senses the difference
in TIPX and RINGX currents. When the
current at the RINGX side exceeds the
current at the TIPX side with the thres­hold value the detector is triggered. For
threshold current values, please refer to
the datasheet.

Ring Trip Detector

Ring trip detection is accomplished by
connecting an external network to a
comparator in the SLIC with inputs DT
and DR. The ringing source can be
balanced or unbalanced superimposed
on V

B

or GND. The unbalanced ringing
source may be applied to either the ring
lead or the tip lead with return via the
other wire. A ring relay driven by the
SLIC ring relay driver connects the
ringing source to tip and ring.

The ring trip function is based on a
polarity change at the comparator input
when the line goes off-hook. In the on­hook state no dc current flows through
the loop and the voltage at comparator
input DT is more positive than the
voltage at input DR. When the line goes
off-hook, while the ring relay is ener­gized, dc current flows and the compara­tor input voltage reverses polarity.

Figure 12 gives an example of a ring

C

D

B

A

E

G

FF

J

H

CB

D

A

VTR [V]

I

L

[mA]

DC characteristics

PBL 386 40/2

15

Figure 14. CODEC receive interface.

PBL386 40/2

CODEC

+

_

VTX

RSN

R

RX

R

T

R

R

I

RRX

I

RSN

I

RT

I

RR

U

REFcodec

+1.25 V

I

DC-GND

trip detection network. This network is
applicable, when the ring voltage super­imposed on VB and is injected on the ring
lead of the two-wire port. The dc voltage
across sense resistor R

RT

is monitored by
the ring trip comparator input DT and DR
via the network R

1

, R2, R3, R4, C1 and C2.
With the line on-hook (no dc current) DT
is more positive than DR and the DET
output will report logic level high, i.e. the
detector is not tripped. When the line
goes off-hook, while ringing, a dc current
will flow through the loop including sense
resistor RRT and will cause input DT to
become more negative than input DR.
This changes output DET to logic level
low, i.e. tripped detector condition. The
system controller (or line card processor)
responds by de-energizing the ring relay,
i.e. ring trip.

Complete filtering of the 20 Hz ac
component at terminal DT and DR is not
necessary. A toggling DET output can be
examined by a software routine to deter­mine the duty cycle. When the DET
output is at logic level low for more than
half the time, off-hook condition is
indicated.

Relay driver

The PBL 386 40/2 SLIC incorporates a
ring relay driver designed as open
collector (npn) with a current sinking
capability of 50 mA. The drive transistor
emitter is connected to BGND. The relay
driver has an internal zener diode clamp
for inductive kick-back voltages.
Care must be taken when using the relay
driver together with relays that have high
impedance.

Control Inputs

The PBL 386 40/2 SLIC have three
digital control inputs, C1, C2 and C3.

A decoder in the SLIC interprets the
control input condition and sets up the
commanded operating state.
C1 to C3 are internal pull-up inputs.

Open Circuit State

In the Open Circuit State the TIPX and
RINGX line drive amplifiers as well as
other circuit blocks are powered down.
This causes the SLIC to present a high
impedance to the line. Power dissipation
is at a minimum and no detectors are
active.

Ringing State

The ring relay driver and the ring trip
detector are activated and the ring trip
detector is indicating off hook with a logic
low level at the detector output.
The SLIC is in the active normal state.

Active States

TIPX is the terminal closest to ground
and sources loop current while RINGX is
the more negative terminal and sinks
loop current. Vf signal transmission is
normal. The loop current or the ground
key detector is activated. The loop
current detector is indicating off hook
with a logic low level and the ground key
detector is indicating active ground key
with a logic high level present at the
detector output.

In PBL 386 40/2 a line voltage meas­urement feature is available in the active
state, which may be used for line length
estimations or for line test purposes. The
line voltage is presented on the detector
output as a pulse at logic high level with
a pulsewidth of 5.5 µs/V. To start the line
voltage measurement this mode has to
be entered from the Active State with the
loop or ground key detector active. The
pulse presented at the DET output
proportional to the line voltage starts
when entering the line voltage measuring
mode.

Tip Open State

Tip Open State is used for ground start
signalling.

In this state the SLICs present a high
impedance to the line on the TIPX pin
and the programmed dc characteristic,
with the longitudinal current compensa­tion (see section Longitudinal Imped­ance) not active, to the line on the
RINGX pin.
The loop current detector is active.

Active Polarity Reversal State

TIPX and RINGX polarity is reversed
from the Active State: RINGX is the
terminal closest to ground and sources
loop current while TIPX is the more
negative terminal and sinks current. Vf
signal transmission is normal. The loop
current or the ground key detector is
activated. The loop current detector is
indicating off hook with a logic low level
and the ground key detector is indicating
active ground key with a logic high level
present at the detector output.

Overvoltage Protection

The PBL 386 40/2 SLIC must be pro­tected against overvoltages on the
telephone line caused by lightning, ac
power contact and induction. Refer to
Maximum Ratings, TIPX and RINGX
terminals, for maximum allowable
continuous and transient ratings that
may be applied to the SLIC.

Secondary Protection

The circuit shown in figure 12 utilizes
series resistors together with a program­mable overvoltage protector
(e.g. PowerInnovations TISPPBL2),
serving as a secondary protection.

The TISP PBL2 is a dual forward­conducting buffered p-gate overvoltage
protector. The protector gate references
the protection (clamping) voltage to
negative supply voltage (i e the battery
voltage, V

B

). As the protection voltage
will track the negative supply voltage the
overvoltage stress on the SLIC is
minimized.

Positive overvoltages are clamped to
ground by a diode. Negative overvolt­ages are initially clamped close to the
SLIC negative supply rail voltage and the

PBL 386 40/2

16

Ordering Information

Package Temp. Range Part No.

24 pin SSOP Tape & Reel -40° - +85° C PBL 386 40/2SHT
24 pin SOIC Tube -40° - +85° C PBL 386 40/2SOS
24 pin SOIC Tape & Reel -40° - +85° C PBL 386 40/2SOT
28 pin PLCC Tube -40° - +85° C PBL 386 40/2QNS

28 pin PLCC Tape & Reel -40° - +85° C PBL 386 40/2QNT

Specifications subject to change without
notice.
1522-PBL 386 40/2 Uen Rev. B
© Ericsson Microelectronics AB 2000

Ericsson Microelectronics AB

SE-164 81 Kista-Stockholm, Sweden
Telephone: [phone]

Information given in this data sheet is believed to be
accurate and reliable. However no responsibility is
assumed for the consequences of its use nor for any
infringement of patents or other rights of third parties
which may result from its use. No license is granted
by implication or otherwise under any patent or patent
rights of Ericsson Microelectronics AB. These
products are sold only according to Ericsson
Microelectronics AB' general conditions of sale,
unless otherwise confirmed in writing.

This product is an original Ericsson
product protected by US, Europe and
other patents.

protector will crowbar into a low voltage
on-state condition, by firing an internal
thyristor.

A gate decoupling capacitor, C

GG

, is
needed to carry enough charge to supply
a high enough current to quickly turn on
the thyristor in the protector. C

GG

shall
be placed close to the overvoltage
protection device. Without the capacitor
even the low inductance in the track to
the V

Bat

supply will limit the current and
delay the activation of the thyristor
clamp.

The fuse resistors R

F

serve the dual
purposes of being non-destructive
energy dissipators, when transients are
clamped and of being fuses, when the
line is exposed to a power cross.

If a PTC is chosen for R

F

, note that it is
important to always use the PTC´s in
series with resistors not sensitive to
temperature, as the PTC will act as a
capacitance for fast transients and
therefore will not protect the TISP.

No special power-up sequence is
necessary except that ground has to be
present before all power supply voltages.

Printed Circuit Board Layout

Care in PCB layout is essential for
proper function. The components
connecting to the RSN input should be
placed in close proximity to that pin, so
that no interference is injected into the
RSN pin. Ground plane surrounding the
RSN pin is advisable.

The two ground pins AGND and BGND
should be connected together on the
PCB at the device location.

The capacitors for the battery should
be connected with short wide leads of the
same length.

Power-up Sequence