Datasheet OP27GPZ, OP27EPZ Specification

Low Noise, Precision

–

FEATURES

Low noise: 80 nV p-p (0.1 Hz to 10 Hz), 3 nV/√Hz
Low drift: 0.2 μV/°C
High speed: 2.8 V/μs slew rate, 8 MHz gain bandwidth
Low V
Excellent CMRR: 126 dB at VCM of ±11 V
High open-loop gain: 1.8 million
Fits OP07, 5534A sockets
Available in die form

GENERAL DESCRIPTION

The OP27 precision operational amplifier combines the low
offset and drift of the
Offsets down to 25 μV and maximum drift of 0.6 μV/°C make
the OP27 ideal for precision instrumentation applications.
Exceptionally low noise, e
noise corner frequency of 2.7 Hz, and high gain (1.8 million),
allow accurate high-gain amplification of low-level signals.
A gain-bandwidth product of 8 MHz and a 2.8 V/μs slew rate
provide excellent dynamic accuracy in high speed, data­acquisition systems.

A low input bias current of ±10 nA is achieved by use of a bias
current cancellation circuit. Over the military temperature
range, this circuit typically holds I
and 15 nA, respectively.

The output stage has good load driving capability. A guaranteed
swing of ±10 V into 600 Ω and low output distortion make the
OP27 an excellent choice for professional audio applications.

: 10 μV

OS

OP07 with both high speed and low noise.

= 3.5 nV/√Hz, at 10 Hz, a low 1/f

n

and IOS to ±20 nA

B

(Continued on Page 3)

Operational Amplifier

OP27

PIN CONFIGURATIONS

BAL

BAL 1

IN 2

+IN 3

OP27

4V– (CASE)

NC = NO CONNECT

Figure 1. 8-Lead TO-99 (J-Suffix)

OS

TRIM

–IN

+IN

1

OP27

2

3

4

NC = NO CONNECT

V

Figure 2. 8-Lead CERDIP – Glass Hermetic Seal (Z-Suffix),

8-Lead PDIP (P-Suffix),

8-Lead SO (S-Suffix)

V+

OUT

NC

00317-001

8

V

TRIM

OS

7

V+

6

OUT

5

NCV–

00317-002

FUNCTIONAL BLOCK DIAGRAM

V+

C2

Q21

Q23

Q27 Q28

R23 R24

R5

Q24

Q22

C1

R9

R12

C3 C4

Q20 Q19

Q26

Q46

OUTPUT

Q45

V–

One Technology Way, P.O. Box 9106, Norwood, MA 02062-9106, U.S.A.
Tel: [phone] www.analog.com
Fax: [phone] ©2006 Analog Devices, Inc. All rights reserved.

00317-003

.

Q2B

R4

1

R2

Q2AQ1A Q1B

Q11 Q12

NONINVERTING

INPUT (+)

INVERTING

INPUT (–)

1

R1 AND R2 ARE PERMANENTLY
ADJUSTED AT WAFER TEST FOR
MINIMUM OFFSET VOLTAGE

R3

Q6

Q3

18

VOS ADJ.

1

R1

Figure 3.

Rev. F

Information furnished by Analog Devices is believed to be accurate and reliable. However, no
responsibility is assumed by Anal og Devices for its use, nor for any infringements of patents or ot her
rights of third parties that may result from its use. Specifications subject to change without notice. No
license is granted by implication or otherwise under any patent or patent rights of Analog Devices.
Trademarks and registered trademarks are the property of their respective owners.

OP27

TABLE OF CONTENTS

Features.............................................................................................. 1

Typical Performance Characteristics..............................................8

General Description......................................................................... 1

Pin Configurations........................................................................... 1

Functional Block Diagram ..............................................................1

Revision History ...............................................................................2

Specifications..................................................................................... 4

Electrical Characteristics............................................................. 4

Typical Electrical Characteristics ...............................................6

Absolute Maximum Ratings............................................................ 7

Thermal Resistance...................................................................... 7

ESD Caution.................................................................................. 7

REVISION HISTORY

5/06—Rev. E to Rev. F

Removed References to 745 ..............................................Universal

Updated 741 to AD741......................................................Universal

Changes to Ordering Guide.......................................................... 20

12/05—Rev. D to Rev. E

Edits to Figure 2................................................................................ 1

9/05—Rev. C to Rev. D

Updated Format..................................................................Universal

Changes to Table 1............................................................................ 4

Removed Die Characteristics Figure ............................................ 5

Removed Wafer Test Limits Table .................................................. 5

Changes to Table 5............................................................................ 7

Changes to Comments on Noise Section ....................................15

Changes to Ordering Guide.......................................................... 24

Application Information................................................................ 14

Offset Voltage Adjustment........................................................ 14

Noise Measurements.................................................................. 14

Unity-Gain Buffer Applications ............................................... 14

Comments On Noise................................................................. 15

Audio Applications .................................................................... 16

References.................................................................................... 18

Outline Dimensions....................................................................... 19

Ordering Guide............................................................................... 20

9/01—Rev. 0 to Rev. A

Edits to Ordering Information ........................................................1

Edits to Pin Connections..................................................................1

Edits to Absolute Maximum Ratings ..............................................2

Edits to Package Type .......................................................................2

Edits to Electrical Characteristics .............................................. 2, 3

Edits to Wafer Test Limits ................................................................4

Deleted Typical Electrical Characteristics......................................4

Edits to Burn-In Circuit Figure.......................................................7

Edits to Application Information ....................................................8

1/03—Rev. B to Rev. C

Edits to Pin Connections................................................................. 1

Edits to General Description........................................................... 1

Edits to Die Characteristics............................................................. 5

Edits to Absolute Maximum Ratings ............................................. 7

Updated Outline Dimensions....................................................... 16

Edits to Figure 8.............................................................................. 14

Edits to Outline Dimensions......................................................... 16

Rev. F | Page 2 of 20

OP27

GENERAL DESCRIPTION

(Continued from Page 1)

PSRR and CMRR exceed 120 dB. These characteristics, coupled
with long-term drift of 0.2 μV/month, allow the circuit designer
to achieve performance levels previously attained only by
discrete designs.

Low cost, high volume production of OP27 is achieved by
using an on-chip Zener zap-trimming network. This reliable
and stable offset trimming scheme has proven its effectiveness
over many years of production history.

The OP27 provides excellent performance in low noise,
high accuracy amplification of low level signals. Applications
include stable integrators, precision summing amplifiers,
precision voltage threshold detectors, comparators, and
professional audio circuits such as tape heads and micro­phone preamplifiers.

The OP27 is a direct replacement for
amplifiers;
the nulling potentiometer of the

AD741 types can be directly replaced by removing

OP06, OP07, and OP45

AD741.

Rev. F | Page 3 of 20

OP27

SPECIFICATIONS

ELECTRICAL CHARACTERISTICS

VS = ±15 V, TA = 25°C, unless otherwise noted.

Table 1.

OP27A/E OP27/G
Parameter Symbol Conditions Min Typ Max Min Typ Max Unit

INPUT OFFSET VOLTAGE
LONG-TE RM VOS STABILITY2,
INPUT OFFSET CURRENT IOS 7 35 12 75 nA
INPUT BIAS CURRENT IB ±10 ±40 ±15 ±80 nA
INPUT NOISE VOLTAGE
INPUT NOISE en fO = 10 Hz 3.5 5.5 3.8 8.0 nV/√Hz

Voltage Density
f
INPUT NOISE in fO = 10 Hz 1.7 4.0 1.7 pA/√Hz

Current Density

INPUT RESISTANCE

Differential Mode

Common Mode R
INPUT VOLTAGE RANGE IVR ±11.0 ±12.3
COMMON-MODE REJECTION RATIO CMRR VCM = ±11 V 114 126
POWER SUPPLY REJECTION RATIO PSRR VS = ±4 V to ±18 V
LARGE SIGNAL VOLTAGE GAIN AVO RL ≥ 2 k Ω, VO = ±10 V 1000 1800

OUTPUT VOLTAGE SWING VO RL ≥ 2 k Ω ±12.0 ±13.8

SLEW RATE

6

GAIN BANDWIDTH PRODUCT
OPEN-LOOP OUTPUT RESISTANCE RO VO = 0, IO = 0 70 70 Ω
POWER CONSUMPTION Pd VO 90 140 100 170 mW
OFFSET ADJUSTMENT RANGE RP = 10 kΩ ±4.0

1

Input offset voltage measurements are performed approximately 0.5 seconds after application of power. A/E grades guaranteed fully warmed up.

2

Long-term input offset voltage stability refers to the average trend line of VOS vs. time over extended periods after the first 30 days of operation. Excluding the initial

hour of operation, changes in V

3

Sample tested.

4

See voltage noise test circuit (Figure 31).

5

Guaranteed by input bias current.

6

Guaranteed by design.

1

3

3, 4

3

3

5

6

during the first 30 days are typically 2.5 μV. Refer to the Typical Performance Characteristics section.

OS

VOS 10 25 30 100 μV
VOS/Time 0.2 1.0 0.4 2.0 μV/MO

e

0.1 Hz to 10 Hz 0.08 0.18 0.09 0.25 μV p-p

n p-p

f

RIN 1.3 6

INCM

SR RL ≥ 2 kΩ 1.7 2.8
GBW 5.0 8.0

= 30 Hz 3.1 4.5 3.3 5.6 nV/√Hz

O

= 1000 Hz 3.0 3.8 3.2 4.5 nV/√Hz

O

= 30 Hz

f

O

fO = 1000 Hz

≥ 600 Ω, VO = ±10 V 800 1500

R

L

≥ 600 Ω ±10.0 ±11.5

R

L

1.0 2.3

0.4 0.6

3

0.7 4

±11.0 ±12.3
100 120

1.0

pA/√Hz

0.4 0.6 pA/√Hz

MΩ

2

GΩ
V
dB

1 10 2 20 μV/V

700 1500
600 1500
±11.5 ±13.5
±10.0 ±11.5

1.7 2.8

5.0 8.0

±4.0

V/mV
V/mV
V
V
V/μs
MHz

mV

Rev. F | Page 4 of 20

OP27

VS = ±15 V, −55°C ≤ TA ≤ 125°C, unless otherwise noted.

Table 2.

OP27A
Parameter Symbol Conditions Min Typ Max Unit

INPUT OFFSET VOLTAGE
AVERAGE INPUT OFFSET DRIFT TCV

INPUT OFFSET CURRENT IOS 15 50 nA
INPUT BIAS CURRENT IB ±20 ±60 nA
INPUT VOLTAGE RANGE IVR ±10.3 ±11.5 V
COMMON-MODE REJECTION RATIO CMRR VCM = ±10 V 108 122
POWER SUPPLY REJECTION RATIO PSRR VS = ±4.5 V to ±18 V 2 16 μV/V
LARGE SIGNAL VOLTAGE GAIN AVO RL ≥ 2 kΩ, VO = ±10 V 600 1200
OUTPUT VOLTAGE SWING VO RL ≥ 2 kΩ ±11.5 ±13.5

1

Input offset voltage measurements are performed by automated test equipment approximately 0.5 seconds after application of power. A/E grades guaranteed fully

warmed up.

2

The TCVOS performance is within the specifications unnulled or when nulled with RP = 8 kΩ to 20 kΩ. TCVOS is 100% tested for A/E grades, sample tested for G grades.

3

Guaranteed by design.

VS = ±15 V, −25°C ≤ TA ≤ 85°C for OP27J, OP27Z, 0°C ≤ TA ≤ 70°C for OP27EP, and –40°C ≤ TA ≤ 85°C for OP27GP, OP27GS, unless
otherwise noted.

Table 3.

OP27E OP27G
Parameter Symbol Conditions Min Typ Max Min Typ Max Unit

INPUT ONSET VOLTAGE VOS
AVERAGE INPUT OFFSET DRIFT TCV

INPUT OFFSET CURRENT IOS
INPUT BIAS CURRENT IB
INPUT VOLTAGE RANGE IVR ±10.5 ±11.8
COMMON-MODE REJECTION RATIO CMRR VCM = ±10 V 110 124
POWER SUPPLY REJECTION RATIO PSRR VS = ±4.5 V to ±18 V 2 15 2 32 μV/V
LARGE SIGNAL VOLTAGE GAIN AVO RL ≥ 2 kΩ, VO = ±10 V 750 1500
OUTPUT VOLTAGE SWING VO RL ≥ 2 kΩ ±11.7 ±13.6

1

The TCVOS performance is within the specifications unnulled or when nulled with RP = 8 kΩ to 20 kΩ. TCVOS is 100% tested for A/E grades, sample tested for C/G grades.

2

Guaranteed by design.

1

TCV

VOS 30 60 μV

OS

OSn

1

2

TCV

2

OS

3

OSn

0.2 0.6 μV/°C

20 50

0.2 0.6

0.2 0.6
10 50
±14 ±60

±10.5 ±11.8
96 118

450 1000
±11.0 ±13.3

55 220 μV
0 4 1.8 μV/°C
0 4 1.8 μV/°C
20 135 nA
±25 ±150 nA

dB

V/mV
V

V
dB

V/mV
V

Rev. F | Page 5 of 20

OP27

TYPICAL ELECTRICAL CHARACTERISTICS

VS = ±15 V, TA = 25°C unless otherwise noted.

Table 4.

Parameter Symbol Conditions OP27N Typical Unit

AVERAGE INPUT OFFSET VOLTAGE DRIFT
TCV
AVERAGE INPUT OFFSET CURRENT DRIFT TCIOS 80 pA/°C
AVERAGE INPUT BIAS CURRENT DRIFT TCIB 100 pA/°C
INPUT NOISE VOLTAGE DENSITY en fO = 10 Hz 3.5 nV/√Hz
e
e

INPUT NOISE CURRENT DENSITY in fO = 10 Hz 1.7 pA/√Hz
i
i
INPUT NOISE VOLTAGE SLEW RATE e

GAIN BANDWIDTH PRODUCT GBW 8 MHz

1

Input offset voltage measurements are performed by automated test equipment approximately 0.5 seconds after application of power.

1

TCVOS or Nulled or unnulled 0.2 μV/°C

RP = 8 kΩ to 20 kΩ

OSn

fO = 30 Hz 3.1 nV/√Hz

n

fO = 1000 Hz 3.0 nV/√Hz

n

fO = 30 Hz 1.0 pA/√Hz

n

fO = 1000 Hz 0.4 pA/√Hz

n

0.1 Hz to 10 Hz 0.08 μV p-p

np-p

SR R

≥ 2 kΩ 2.8 V/μs

L

Rev. F | Page 6 of 20

OP27

ABSOLUTE MAXIMUM RATINGS

Table 5.

Parameter Rating

Supply Voltage ±22 V
Input Voltage

1

±22 V

Output Short-Circuit Duration Indefinite
Differential Input Voltage
Differential Input Current

2

2

±0.7 V
±25 mA

Storage Temperature Range −65°C to +150°C
Operating Temperature Range

OP27A (J, Z) −55°C to +125°C
OP27E, ( Z) −25°C to +85°C
OP27E, (P) 0°C to 70°C
OP27G (P, S, J, Z) −40°C to +85°C

Lead Temperature Range (Soldering, 60 sec) 300°C
Junction Temperature −65°C to +150°C

1

For supply voltages less than ±22 V, the absolute maximum input voltage is

equal to the supply voltage.

2

The inputs of the OP27 are protected by back-to-back diodes. Current

limiting resistors are not used in order to achieve low noise. If differential
input voltage exceeds ±0.7 V, the input current should be limited to 25 mA.

Stresses above those listed under Absolute Maximum Ratings
may cause permanent damage to the device. This is a stress
rating only; functional operation of the device at these or any
other conditions above those indicated in the operational
section of this specification is not implied. Exposure to absolute
maximum rating conditions for extended periods may affect
device reliability.

THERMAL RESISTANCE

θJA is specified for the worst-case conditions, that is, θ
specified for device in socket for TO, CERDIP, and PDIP
packages; θ

is specified for device soldered to printed circuit

JA

board for SO package.

Absolute maximum ratings apply to both DICE and packaged
parts, unless otherwise noted.

Table 6.

Package Type θJA θ

JC

TO-99 (J) 150 18 °C/W
8-Lead Hermetic DlP (Z) 148 16 °C/W
8-Lead Plastic DIP (P) 103 43 °C/W
8-Lead SO (S) 158 43 °C/W

is

JA

Unit

ESD CAUTION

ESD (electrostatic discharge) sensitive device. Electrostatic charges as high as 4000 V readily accumulate on
the human body and test equipment and can discharge without detection. Although this product features
proprietary ESD protection circuitry, permanent damage may occur on devices subjected to high energy
electrostatic discharges. Therefore, proper ESD precautions are recommended to avoid performance
degradation or loss of functionality.

Rev. F | Page 7 of 20

OP27

TYPICAL PERFORMANCE CHARACTERISTICS

100

90

10

TA = 25°C
V

= ±15V

S

80

70

60

GAIN (dB)

50

TEST TIME OF 10sec FURTHER
LIMITS LOW FREQUENCY

40

(<0.1Hz) GAIN

30

0.01 0.1 1 10 100

FREQUENCY (Hz)

Figure 4. 0.1 Hz to 10 Hz p-p Noise Tester Frequency Response

10

9
8

7

6

5

4

3

I/F CORNER = 2.7Hz

2

VOLTAGE NOISE (nV/√Hz)

1

1 10 100 1k

FREQUENCY (Hz)

TA = 25°C

= ±15V

V

S

Figure 5. Voltage Noise Density vs. Frequency

00317-004

00317-005

1

0.1

RMS VOLTAGE NOISE (μV)

0.01
100 1k 10k 100k

BANDWIDTH (Hz)

00317-007

Figure 7. Input Wideband Voltage Noise vs. Bandwidth (0.1 Hz to Frequency

Indicated)

100

TA = 25°C
V

= ±15V

S

10

AT 10Hz

TOTAL NOISE (nV/√Hz)

AT 1kHz

RESISTOR NOISE ONLY

1

100 1k 10k

SOURCE RESISTANCE (Ω)

R1

R2

R

– 2R1

S

00317-008

Figure 8. Total Noise vs. Sourced Resistance

100

741

10

I/F CORNER = 2.7Hz

VOLTAGE NOISE (nV/√Hz)

INSTRUMENTATION

1

1 10 100 1k

I/F CORNER

OP27 I/F CORNER

RANGE TO DC

FREQUENCY (Hz)

LOW NOISE
AUDIO OP AMP

AUDIO RANGE

TO 20kHz

Figure 6. A Comparison of Op Amp Voltage Noise Spectra

00317-006

Rev. F | Page 8 of 20

5

4

AT 10Hz

3

AT 1kHz

VOLTAGE NOISE (nV/√Hz)

2

1

–50 0–25 100755025 125

TEMPERATURE (°C)

Figure 9. Voltage Noise Density vs. Temperature

VS = ±15V

00317-009

OP27

5

TA = 25°C

4

3

VOLTAGE NOISE (nV/√Hz)

2

1

04

10 20 30

TOTAL SUPPLY VOLTAGE, V+ – V–, (V)

AT 10Hz

AT 1kHz

0

00317-010

Figure 10. Voltage Noise Density vs. Supply Voltage

60

50

40

30

20

10

0

–10

–20

–30

OFFSET VOLTAGE (μV)

–40

TRIMMING WITH

–50

10kΩ POT DOES
NOT CHANGE

–60

TCV

OS

–70

–75 175

–50 –25 0 25 50 75 100 125 150

TEMPERATURE (°C)

OP27C

OP27A

OP27A

OP27A

OP27C

00317-013

Figure 13. Offset Voltage Drift of Five Representative Units vs. Temperature

10.0

Hz)

√

1.0

CURRENT NOISE (pA/

I/F CORNER = 140Hz

0.1
10 10k

100 1k

FREQUENCY (Hz)

00317-011

Figure 11. Current Noise Density vs. Frequency

5.0

4.0

TA = +125°C

3.0

TA = –55°C

SUPPLY CURRENT (mA)

2.0

TA = +25°C

1.0
54

15 25 35

TOTAL SUPPLY VOLTAGE (V)

5

00317-012

Figure 12. Supply Current vs. Supply Voltage

6

4

2

0

–2

–4

–6

6

4

2

0

CHANGE IN OFFSET VOLTAGE (μV)

–2

–4

–6

07

123456

Figure 14. Long-Term Offset Voltage Drift of Six Representative Units

TA= 25°C

= 15V

V

S

10

5

CHANGE IN INPUT OFFSET VOLTAGE (μV)

1

0

Figure 15. Warm-Up Offset Voltage Drift

TIME (Months)

OP27 C/G

OP27 F

OP27 A/E

1234

TIME AFTER POWER ON (Min)

5

00317-014

00317-015

Rev. F | Page 9 of 20

OP27

30

25

20

15

10

OPEN-LOOP GAIN (dB)

VS =±15V

= 70°C

TA =

°

C

25

5

0

–20 100

T

A

THERMAL
SHOCK
RESPONSE
BAND

DEVICE IMMERSED
IN 70

°

C OIL BATH

0 20406080

TIME (Sec)

Figure 16. Offset Voltage Change Due to Thermal Shock

00317-016

130

110

90

70

50

VOLTAGE GAIN (dB)

30

10

–10

10 1001 1k 10k 100k 1M 10M

FREQUENCY (Hz)

100M

00317-019

Figure 19. Open-Loop Gain vs. Frequency

50

40

30

20

INPUT BIAS CURRENT (nA)

10

0

–50 –25 0 25 50 75 100 125

TEMPERATURE (

OP27C

OP27A

Figure 17. Input Bias Current vs. Temperature

50

40

30

20

INPUT OFFSET CURRENT (nA)

10

0

–50 –25–75 0 25 50 75 100

TEMPERATURE (

OP27C

OP27A

Figure 18. Input Offset Current vs. Temperature

125

10

9

8

7

6

GAIN BANDWIDTH PRODUCT (MHz)

00317-020

VS=±15V

150

°

C)

00317-017

70

60

50

SLEW RATE (V/μS) PHASE MARGIN (Degrees)

ΦM

GBW

4

3

2

–50 –25–75 0 25 50 75 100

SLEW

TEMPERATURE (°C)

VS= ±15V

Figure 20. Slew Rate, Gain Bandwidth Product, Phase Margin vs.

Temperature

= ±15V

100M

80

100

120

140

160

180

200

220

PHASE SHIFT (Degrees)

00317-021

VS=±15V

125

°

C)

00317-018

25

20

GAIN

15

PHASE

10

5

GAIN (dB)

0

–5

–10

1M

MARGIN

= 70°

10M

FREQUENCY (Hz)

TA = 25°C
V

S

Figure 21. Gain, Phase Shift vs. Frequency

Rev. F | Page 10 of 20

OP27

–

2.5

TA= 25°C

2.0

RL= 2kΩ

1.5

RL= 1kΩ

1.0

OPEN-LOOP GAIN (V/μV)

0.5

% OVERSHOOT

100

VS= ±15V
V

= 100mV

IN

A

= +1

80

60

40

20

V

0

05

10 20 30 40

TOTAL SUPPLY VOLTAGE (V)

0

00317-022

Figure 22. Open-Loop Voltage Gain vs. Supply Voltage

28

24

20

16

12

8

MAXIMUM OUTPUT SWING

4

0

1k 10M

10k 100k 1M

FREQUENCY (Hz)

TA= 25°C
V

= ±15V

S

00317-023

Figure 23. Maximum Output Swing vs. Frequency

18

16

14

12

10

8

6

4

MAXIMUM OUTPUT (V)

2

0

–2

100

POSITIVE
SWING

LOAD RESISTANCE (

NEGATIVE
SWING

1k

TA= 25°C
V

=±15V

S

Ω

)

10k

00317-024

Figure 24. Maximum Output Voltage vs. Load Resistance

0

0 2500

Figure 25. Small-Signal Overshoot vs. Capacitive Load

50mV

0V

50mV

Figure 26. Small-Signal Transient Response

+5V

0V

–5V

Figure 27. Large Signal Transient Response

500 1000 1500 2000

CAPACITIVE LOAD (pF)

20mV 500ns

A

VCL

C

= 15pF

L

V

= ±15V

S

T

= 25°C

A

2V 2μs

A

VCL

V

= ±15V

S

T

= 25°C

A

= +1

= +1

00317-025

00317-026

00317-027

Rev. F | Page 11 of 20

OP27

SHORT-CIRCUIT CURRENT (mA)

60

50

40

30

20

TA= 25°C
V

= 15V

S

ISC(+)

ISC(–)

10

0.1μF

100k

Ω

Ω

OP27
D.U.T.

VOLTAGE

GAIN

= 50,000

4.7μF

Ω

2k

22μF

4.3k

OP12

100k

Ω

SCOPE× 1

= 1M

Ω

R

Ω

IN

10

05

140

120

100

CMRR (dB)

80

60

100 1M

16

12

8

4

0

–4

–8

COMMON-MODE RANGE (V)

–12

–16

0

1234

TIME FROM OUTPUT SHORTED TO GROUND (Min)

Figure 28. Short-Circuit Current vs. Time

VS= ±15V
T

= 25°C

A

V

CM

1k 10k 100k

FREQUENCY (Hz)

Figure 29. CMRR vs. Frequency

TA = –55°C

TA = +25°C

TA = +125°C

TA = –55°C

TA = +25°C

TA = +125°C

±5 ±10 ±15

SUPPLY VOLTAGE (V)

= ±10V

±20

00317-028

00317-029

00317-030

Figure 31. Voltage Noise Test Circuit (0.1 Hz to 10 Hz)

2.4
TA = 25°C
V

= ±15V2.2

S

2.0

1.8

1.6

1.4

1.2

1.0

0.8

OPEN-LOOP VOLTAGE GAIN (V/μV)

0.6

0.4

100 1k 10k 100k

Figure 32. Open-Loop Voltage Gain vs. Load Resistance

120

80

40

0

–40

VOLTAGE NOISE (nV)

–90

–120

Figure 30. Common-Mode Input Range vs. Supply Voltage

2.2μF

0.1μF

24.3k

Ω

LOAD RESISTANCE (Ω)

1 SEC/DIV

0.1Hz TO 10Hz p-p NOISE

Figure 33. Low Frequency Noise

110k

Ω

00317-031

00317-032

00317-033

Rev. F | Page 12 of 20

OP27

160

140

120

100

80

60

40

20

POWER SUPPLY REJECTION RATIO (dB)

TA = 25°C

NEGATIVE
SWING

POSITIVE
SWING

0

1 100M

10 100 1k 10k 100k 1M 10M

FREQUENCY (Hz)

Figure 34. PSRR vs. Frequency

00317-034

Rev. F | Page 13 of 20

OP27

APPLICATION INFORMATION

OP27 series units can be inserted directly into OP07 sockets
with or without removal of external compensation or nulling
components. Additionally, the OP27 can be fitted to unnulled

AD741-type sockets; however, if conventional AD741 nulling

circuitry is in use, it should be modified or removed to ensure
correct OP27 operation. OP27 offset voltage can be nulled to
0 (or another desired setting) using a potentiometer (see
Figure 35

).

The OP27 provides stable operation with load capacitances of
up to 2000 pF and ±10 V swings; larger capacitances should be
decoupled with a 50 Ω resistor inside the feedback loop. The
OP27 is unity-gain stable.

Thermoelectric voltages generated by dissimilar metals at the
input terminal contacts can degrade the drift performance.
Best operation is obtained when both input contacts are
maintained at the same temperature.

R

10kΩ

P

1

2

3

OP27

V–

8

7

4

–-

+

Figure 35. Offset Nulling Circuit

V+

6

OUTPUT

00317-035

OFFSET VOLTAGE ADJUSTMENT

The input offset voltage of the OP27 is trimmed at wafer level.
However, if further adjustment of V
potentiometer can be used. TCV
Other potentiometer values from 1 kΩ to 1 MΩ can be used
with a slight degradation (0.1 μV/°C to 0.2 μV/°C) of TCV
Trimming to a value other than zero creates a drift of approxi­mately (V

0.33 μV/°C if V

/300) μV/°C. For example, the change in TCVOS is

OS

is adjusted to 100 μV. The offset voltage

OS

adjustment range with a 10 kΩ potentiometer is ±4 mV. If smaller
adjustment range is required, the nulling sensitivity can be
reduced by using a smaller potentiometer in conjunction with
fixed resistors. For example,
a 280 μV adjustment range.

1

Figure 36. Offset Voltage Adjustment

is necessary, a 10 kΩ trim

OS

is not degraded (see Figure 35).

OS

Figure 36 shows a network that has

84.7kΩ4.7kΩ 1kΩ POTT

V+

00317-036

.

OS

Rev. F | Page 14 of 20

NOISE MEASUREMENTS

To measure the 80 nV p-p noise specification of the OP27 in
the 0.1 Hz to 10 Hz range, the following precautions must be
observed:

• The device must be warmed up for at least five minutes.

As shown in the warm-up drift curve, the offset voltage
typically changes 4 μV due to increasing chip temperature
after power-up. In the 10-second measurement interval,
these temperature-induced effects can exceed tens-of­nanovolts.

• For similar reasons, the device has to be well-shielded

from air currents. Shielding minimizes thermocouple effects.

• Sudden motion in the vicinity of the device can also

feedthrough to increase the observed noise.

• The test time to measure 0.1 Hz to 10 Hz noise should not

exceed 10 seconds. As shown in the noise-tester frequency
response curve, the 0.1 Hz corner is defined by only one
zero. The test time of 10 seconds acts as an additional zero
to eliminate noise contributions from the frequency band
below 0.1 Hz.

• A noise voltage density test is recommended when

measuring noise on a large number of units. A 10 Hz noise
voltage density measurement correlates well with a 0.1 Hz to
10 Hz p-p noise reading, since both results are determined
by the white noise and the location of the 1/f corner
frequency.

UNITY-GAIN BUFFER APPLICATIONS

When Rf ≤ 100 Ω and the input is driven with a fast, large
signal pulse (>1 V), the output waveform looks as shown in the
pulsed operation diagram (see

During the fast feedthrough-like portion of the output, the
input protection diodes effectively short the output to the input,
and a current, limited only by the output short-circuit protect­ion, is drawn by the signal generator. With R
output is capable of handling the current requirements (I
at 10 V); the amplifier stays in its active mode and a smooth
transition occurs.

When R

> 2 kΩ, a pole is created with Rf and the amplifier’s

f

input capacitance (8 pF) that creates additional phase shift and
reduces phase margin. A small capacitor (20 pF to 50 pF) in
parallel with R

eliminates this problem.

f

R

f

–

OP27

+

Figure 37. Pulsed Operation

Figure 37).

≥ 500 Ω, the

f

≤ 20 mA

L

2.8V/μs

00317-037

OP27

COMMENTS ON NOISE

The OP27 is a very low noise, monolithic op amp. The out­standing input voltage noise characteristics of the OP27
are achieved mainly by operating the input stage at a high
quiescent current. The input bias and offset currents, which
would normally increase, are held to reasonable values by the
input bias current cancellation circuit. The OP27A/E has I
and I

of only ±40 nA and 35 nA at 25°C respectively. This

OS

is particularly important when the input has a high source
resistance. In addition, many audio amplifier designers prefer
to use direct coupling. The high I

, VOS, and TCVOS of previous

B

designs have made direct coupling difficult, if not impossible,
to use.

Voltage noise is inversely proportional to the square root of bias
current, but current noise is proportional to the square root of
bias current. The noise advantage of the OP27 disappears when
high source resistors are used.
compare the observed total noise of the

Figure 38, Figure 39, Figure 40

OP27 with the noise

performance of other devices in different circuit applications.

⎡

NoiseTotal

⎢

⎢

=

⎢
⎢

⎣

2

)(

+

NoiseVoltage

RNoiseCurrent

2

)(

NoiseResistor

2/1

⎤
⎥

2

)(

+×

⎥

S

⎥
⎥

⎦

Figure 38 shows noise vs. source resistance at 1000 Hz. The
same plot applies to wideband noise. To use this plot, multiply
the vertical scale by the square root of the bandwidth.

100

50

OP08/108

Hz)

√

TOTAL NOISE (nV/

OP07

10

5

5534

OP27/37

REGISTER

1

50 10k

NOISE ONLY

100 50k

500 1k 5k

RS—SOURCE RESISTANCE (Ω)

1 RS UNMATCHED
e.g.R

=RS1 = 10kΩ,RS2 = 0

S

2 R

MATCHED

S

e.g.R

= 10kΩ,RS1 =RS2 = 5k

S

R

R

S1

S2

Figure 38. Noise vs. Source Resistance (Including Resistor Noise) at 1000 Hz

At RS < 1 kΩ, the low voltage noise of the OP27 is maintained.

< 1 kΩ, total noise increases but is dominated by the

With R

S

resistor noise rather than current or voltage noise. lt is only
beyond R

of 20 kΩ that current noise starts to dominate. The

S

argument can be made that current noise is not important for
applications with low-to-moderate source resistances. The
crossover between the OP27 and OP07 noise occurs in the 15 kΩ
to 40 kΩ region.

B

1

2

Ω

00317-038

Figure 39 shows the 0.1 Hz to 10 Hz p-p noise. Here the picture
is less favorable; resistor noise is negligible and current noise
becomes important because it is inversely proportional to the
square root of frequency. The crossover with the

OP07 occurs

in the 3 kΩ to 5 kΩ range depending on whether balanced or
unbalanced source resistors are used (at 3 kΩ the I
error also can be 3× the V

1k

OP08/108

500

5534

OP07

100

OP27/37

p-p NOISE (nV)

50

REGISTER

10

50 10k

Figure 39. Peak-to-Peak Noise (0.1 Hz to 10 Hz) as Source Resistance

NOISE ONLY

100 50k

spec).

OS

1

2

1 RS UNMATCHED
e.g.R

=RS1 = 10kΩ,RS2 = 0

S

2 R

MATCHED

S

e.g.R

= 10kΩ,RS1 =RS2 = 5k

S

R

R

500 1k 5k

RS—SOURCE RESISTANCE (Ω)

(Includes Resistor Noise)

S1

S2

and IOS

B

Ω

00317-039

For low frequency applications, the OP07 is better than the

OP37 when RS > 3 kΩ. The only exception is when gain

OP27/
error is important.

Figure 40 illustrates the 10 Hz noise. As expected, the results are
between the previous two figures.

100

50

OP08/108

Hz)

√

OP07

10

5534

5

TOTAL NOISE (nV/

OP27/37

REGISTER

1

50 10k

NOISE ONLY

100 50k

500 1k 5k

RS—SOURCE RESISTANCE (Ω)

1 RS UNMATCHED

=RS1 = 10kΩ,RS2 = 0

e.g.R

S

MATCHED

2 R

S

= 10kΩ,RS1 =RS2 = 5k

e.g.R

S

Figure 40. 10 Hz Noise vs. Source Resistance (Includes Resistor Noise)

Audio Applications

1

2

R

S1

R

S2

Ω

00317-040

Rev. F | Page 15 of 20

OP27

C

For reference, typical source resistances of some signal sources
are listed in

Table 7.

Table 7.

Source

Device

Strain Gauge <500 Ω

Impedance

Comments

Typically used in low frequency
applications.

Magnetic
Tape Head

<1500 Ω

Low is very important to reduce
self-magnetization problems
when direct coupling is used.
OP27 IB can be neglected.

Magnetic
Phonograph
Cartridges

<1500 Ω

Similar need for low IB in direct
coupled applications. OP27 does
not introduce any self­magnetization problems.

Linear
Variable
Differential

<1500 Ω

Used in rugged servo-feedback
applications. Bandwidth of
interest is 400 Hz to 5 kHz.

Transform er

Table 8. Open-Loop Gain

Frequency OP07 OP27 OP37

@ 3 Hz 100 dB 124 dB 125 dB
@ 10 Hz 100 dB 120 dB 125 dB
@ 30 Hz 90 dB 110 dB 124 dB

AUDIO APPLICATIONS

Figure 41 is an example of a phono pre-amplifier circuit using the
OP27 for A1; R1-R2-C1-C2 form a very accurate RIAA network
with standard component values. The popular method to
accomplish RIAA phono equalization is to employ frequency
dependent feedback around a high quality gain block. Properly
chosen, an RC network can provide the three necessary time
constants of 3180 μs, 318 μs, and 75 μs.

For initial equalization accuracy and stability, precision metal
film resistors and film capacitors of polystyrene or polypro­pylene are recommended because they have low voltage
coefficients, dissipation factors, and dielectric absorption.
(high-k ceramic capacitors should be avoided here, though
low-k ceramics, such as NPO types that have excellent
dissipation factors and somewhat lower dielectric absorption,
can be considered for small values.)

MOVING MAGNET

ARTRIDGE I NPUT

R

A

47.5kΩ

3

C
150pF

A1

A

OP27

2

Figure 41. Phono Preamplifier Circuit

6

C3

0.47µF

R1

97.6kΩ

R2

7.87kΩ

R3
100Ω

G = 1kHz GAIN

= 0.101 ( 1 + )

= 98.677 (39.9dB) AS SHOWN

C4 (2)
220µF

++

LF ROLLOFF

C1

0.03µF

C2

0.01µF

OUT IN

R4

75kΩ

R1
R3

R5

100kΩ

OUTPUT

The OP27 brings a 3.2 nV/√Hz voltage noise and 0.45 pA/√Hz
current noise to this circuit. To minimize noise from other
sources, R3 is set to a value of 100 Ω, generating a voltage noise
of 1.3 nV/√Hz. The noise increases the 3.2 nV/√Hz of the
amplifier by only 0.7 dB. With a 1 kΩ source, the circuit noise
measures 63 dB below a 1 mV reference level, unweighted, in a
20 kHz noise bandwidth.

Gain (G) of the circuit at 1 kHz can be calculated by the
expression:

R1

G 1101.0

⎛
⎜
⎝

⎞

+=

⎟

R3

⎠

For the values shown, the gain is just under 100 (or 40 dB).
Lower gains can be accommodated by increasing R3, but gains
higher than 40 dB show more equalization errors because of the
8 MHz gain bandwidth of the OP27.

This circuit is capable of very low distortion over its entire
range, generally below 0.01% at levels up to 7 V rms. At 3 V
output levels, it produces less than 0.03% total harmonic
distortion at frequencies up to 20 kHz.

Capacitor C3 and Resistor R4 form a simple −6 dB per octave
rumble filter, with a corner at 22 Hz. As an option, the switch
selected Shunt Capacitor C4, a nonpolarized electrolytic,
bypasses the low frequency roll-off. Placing the rumble filter’s
high-pass action after the preamplifier has the desirable result
of discriminating against the RIAA-amplified low frequency
noise components and pickup produced low frequency
disturbances.

00317-041

A preamplifier for NAB tape playback is similar to an RIAA
phono preamplifier, though more gain is typically demanded,
along with equalization requiring a heavy low frequency boost.
The circuit in
shown by

Rev. F | Page 16 of 20

Figure 41 can be readily modified for tape use, as

Figure 42.

OP27

Noise performance of this circuit is limited more by the Input
Resistors R1 and R2 than by the op amp, as R1 and R2 each
generate a 4 nV/√Hz noise, while the op amp generates a

3.2 nV/√Hz noise. The rms sum of these predominant noise
sources is about 6 nV/√Hz, equivalent to 0.9 μV in a 20 kHz
noise bandwidth, or nearly 61 dB below a 1 mV input signal.
Measurements confirm this predicted performance.

R1

1kΩ

R3

316kΩ

C1

5mF

R6

100Ω

TAP E

HEAD

+

OP27

C

R

A

A

10Ω

–

R2

5kΩ

R1

33kΩ

0.01µF

0.47µF

T1 = 3180µs
T2 = 50µs

Figure 42. Tape Head Preamplifier

15kΩ

00317-042

While the tape equalization requirement has a flat high
frequency gain above 3 kHz (T2 = 50 μs), the amplifier need
not be stabilized for unity gain. The decompensated

OP37

provides a greater bandwidth and slew rate. For many applica­tions, the idealized time constants shown can require trimming
of R1 and R2 to optimize frequency response for nonideal tape
head performance and other factors (see the

References

section).

The network values of the configuration yield a 50 dB gain at
1 kHz, and the dc gain is greater than 70 dB. Thus, the worst­case output offset is just over 500 mV. A single 0.47 μF output
capacitor can block this level without affecting the dynamic
range.

The tape head can be coupled directly to the amplifier input,
because the worst-case bias current of 80 nA with a 400 mH,
100 μ inch head (such as the PRB2H7K) is not troublesome.

Amplifier bias-current transients that can magnetize a head
present one potential tape head problem. The OP27 and

OP37

are free of bias current transients upon power-up or power­down. It is always advantageous to control the speed of power
supply rise and fall to eliminate transients.

In addition, the dc resistance of the head should be carefully
controlled and preferably below 1 kΩ. For this configuration,
the bias current induced offset voltage can be greater than the
100 pV maximum offset if the head resistance is not sufficiently
controlled.

A simple, but effective, fixed gain transformerless microphone
preamp (

Figure 43) amplifies differential signals from low
impedance microphones by 50 dB and has an input impedance
of 2 kΩ. Because of the high working gain of the circuit, an

OP37 helps to preserve bandwidth, which is 110 kHz. As the
OP37 is a decompensated device (minimum stable gain of 5), a

dummy resistor, R

, may be necessary if the microphone is to be

p

unplugged. Otherwise, the 100% feedback from the open input
can cause the amplifier to oscillate.

Common-mode input noise rejection will depend upon the
match of the bridge-resistor ratios. Either close tolerance (0.1%)
types should be used, or R4 should be trimmed for best CMRR.
All resistors should be metal film types for best stability and low
noise.

LOW IMPEDANCE

MICROP HONE INP UT

(Z = 50Ω TO 200Ω)

R4

R3

=

R2

R1

R2

1kΩ

R

P

30kΩ

–

OP27/
OP37

+

R4

316kΩ

R7
10kΩ

OUTPUT

Figure 43. Fixed Gain Transformerless Microphone Preamplifier

For applications demanding appreciably lower noise, a high
quality microphone transformer coupled preamplifier (

) incorporates the internally compensated OP27. T1 is a JE-

44

Figure

115K-E 150 Ω/15 kΩ transformer that provides an optimum
source resistance for the OP27 device. The circuit has an overall
gain of 40 dB, the product of the transformer’s voltage setup and
the op amp’s voltage gain.

C2

1800pF

150Ω

SOURCE

R1

121Ω

1

T1

R3

100Ω

R2

1100Ω

2

A1

OP27

3

6

1

T1 – JENSEN JE – 115K – E

JENSEN TRANSFORMERS

OUTPUT

00317-044

Figure 44. High Quality Microphone Transformer Coupled Preamplifier

Gain can be trimmed to other levels, if desired, by adjusting R2
or R1. Because of the low offset voltage of the OP27, the output
offset of this circuit is very low, 1.7 mV or less, for a 40 dB gain.
The typical output blocking capacitor can be eliminated in such
cases, but it is desirable for higher gains to eliminate switching
transients.

+18V

8

2

3

Figure 45. Burn-In Circuit

OP27

–18V

7

6

4

00317-045

00317-043

Rev. F | Page 17 of 20

OP27

Capacitor C2 and Resistor R2 form a 2 μs time constant in this
circuit, as recommended for optimum transient response by the
transformer manufacturer. With C2 in use, A1 must have unity­gain stability. For situations where the 2 μs time constant is not
necessary, C2 can be deleted, allowing the faster
employed.

A 150 Ω resistor and R1 and R2 gain resistors connected to a
noiseless amplifier generate 220 nV of noise in a 20 kHz
bandwidth, or 73 dB below a 1 mV reference level. Any practical
amplifier can only approach this noise level; it can never exceed
it. With the OP27 and T1 specified, the additional noise
degradation is close to 3.6 dB (or −69.5 referenced to 1 mV).

OP37 to be

REFERENCES

1. Lipshitz, S. R, “On RIAA Equalization Networks,” JAES,

Vol. 27, June 1979, p. 458–481.

2.

Jung, W. G., IC Op Amp Cookbook, 2nd. Ed., H. W. Sams

and Company, 1980.

Jung, W. G., Audio IC Op Amp Applications, 2nd. Ed., H. W.

3.
Sams and Company, 1978.

Jung, W. G., and Marsh, R. M., “Picking Capacitors,” Audio,

4.
February and March, 1980.

5.

Otala, M., “Feedback-Generated Phase Nonlinearity in

Audio Amplifiers,” London AES Convention, March 1980,
preprint 1976.

6.

Stout, D. F., and Kaufman, M., Handbook of Operational

Amplifier Circuit Design, New York, McGraw-Hill, 1976.

Rev. F | Page 18 of 20

OP27

OUTLINE DIMENSIONS

0.400 (10.16)

0.365 (9.27)

0.355 (9.02)

8

5

0.280 (7.11)

4

0.250 (6.35)

0.240 (6.10)

0.015
(0.38)
MIN

SEATING
PLANE

0.005 (0.13)
MIN

(N-8)

P-Suffix

0.060 (1.52)

0.015 (0.38)
GAUGE

PLANE

MAX

0.325 (8.26)

0.310 (7.87)

0.300 (7.62)

0.430 (10.92)
MAX

0.195 (4.95)

0.130 (3.30)

0.115 (2.92)

0.014 (0.36)

0.010 (0.25)

0.008 (0.20)

5.00 (0.1968)

4.80 (0.1890)

4.00 (0.1574)

3.80 (0.1497)

0.25 (0.0098)

0.10 (0.0040)

COPLANARITY

0.10

85

1.27 (0.0500)

SEATING

PLANE

BSC

6.20 (0.2440)

5.80 (0.2284)

41

1.75 (0.0688)

1.35 (0.0532)

0.51 (0.0201)

0.31 (0.0122)

0.25 (0.0098)

0.17 (0.0067)

0.50 (0.0196)

0.25 (0.0099)

8°

1.27 (0.0500)

0°

0.40 (0.0157)

COMPLIANT TO JEDEC STANDARDS MS-012-AA

CONTROLLING DIMENSIONS ARE IN MILLIMETERS; INCH DIMENSIONS
(IN PARENTHESES) ARE ROUNDED-OFF MILLIMETER EQUIVALENTS FOR
REFERENCE ONLY AND ARE NOT APPROPRIATE FOR USE IN DESIGN.

Figure 48. 8-Lead Standard Small Outline Package [SOIC]

Narrow Body

(R-8)

S-Suffix

Dimensions shown in millimeters and (inches)

× 45°

1

PIN 1

0.100 (2.54)

0.210

(5.33)

MAX

0.150 (3.81)

0.130 (3.30)

0.115 (2.92)

0.022 (0.56)

0.018 (0.46)

0.014 (0.36)

CONTROLLING DIMENSIONS ARE IN INCHES; MILLIMETER DIMENSIONS
(IN PARENTHESES) ARE ROUNDED-OFF INCH EQUIVALENTS FOR
REFERENCE ONLY AND ARE NOT APPROPRIATE FOR USE IN DESIGN.
CORNER LEADS MAY BE CONFIGURED AS WHOLE OR HALF LEADS.

BSC

0.070 (1.78)

0.060 (1.52)

0.045 (1.14)

COMPLIANT TO JEDEC STANDARDS MS-001-BA

Figure 46. 8-Lead Plastic Dual-in-Line Package [PDIP]

Dimensions shown in inches and (millimeters)

0.005 (0.13)

0.055 (1.40)

MIN

14

MAX

58

0.310 (7.87)

0.220 (5.59)

0.100 (2.54) BSC

0.405 (10.29) MAX

0.200 (5.08)
MAX

0.200 (5.08)

0.125 (3.18)

0.023 (0.58)

0.014 (0.36)

CONTROLLING DIMENSIONS ARE IN INCHES; MILLIMETER DIMENSIONS
(IN PARENTHESES) ARE ROUNDED-OFF INCH EQUIVALENTS FOR
REFERENCE ONLY AND ARE NOT APPROPRIATE FOR USE IN DESIGN.

0.070 (1.78)

0.030 (0.76)

0.060 (1.52)

0.015 (0.38)

0.150 (3.81)
MIN

SEATING
PLANE

0.320 (8.13)

0.290 (7.37)

15°

0°

0.015 (0.38)

0.008 (0.20)

Figure 47. 8-Lead Ceramic DIP – Glass Hermetic Seal [CERDIP]

(Q-8)

Z-Suffix

Dimensions shown in inches and (millimeters)

REFERENCE PL ANE

0.5000 (12.70)

0.1850 (4.70)

0.1650 (4.19)

0.3700 (9.40)

0.3350 (8.51)

0.3350 (8.51)

0.3050 (7.75)

0.0400 (1.02) MAX

0.0400 (1.02)

0.0100 (0.25)

CONTROL LING DIM ENSIONS ARE IN INCHES; MILLI METER DIM ENSIONS
(IN PARENT HESES) ARE ROUNDED-OFF INCH EQUIVALENTS FOR
REFERENCE ON LY AND ARE NOT APPROPRI ATE FOR USE IN DE SIGN.

MIN

0.2500 (6.35) MIN

0.0500 (1.27) M AX

0.0190 (0.48)

0.0160 (0.41)

0.0210 (0.53)

0.0160 (0.41)

BASE & SEATING PLANE

COMPLI ANT TO JEDEC STANDARDS MO -002-AK

0.2000
(5.08)

BSC

0.1000
(2.54)

BSC

0.1000 (2.54)
BSC

5

4

3

2

1

0.0340 (0.86)

0.0280 (0.71)

45° BSC

0.1600 (4.06)

0.1400 (3.56)

6

7

8

0.0450 (1.14)

0.0270 (0.69)

022306-A

Figure 49. 8-Lead Metal Can [TO-99]

(H-08)

J-Suffix

Dimensions shown in inches and (millimeters)

Rev. F | Page 19 of 20

OP27

ORDERING GUIDE

Model Temperature Range Package Description Package Option

OP27AJ/883C –55° to +125°C 8-Lead Metal Can (TO-99) J-Suffix (H-08)
OP27GJ –40° to +85°C 8-Lead Metal Can (TO-99) J-Suffix (H-08)
OP27AZ –55° to +125°C 8-Lead CERDIP Z-Suffix (Q-8)
OP27AZ/883C –55° to +125°C 8-Lead CERDIP Z-Suffix (Q-8)
OP27EZ –25° to +85°C 8-Lead CERDIP Z-Suffix (Q-8)
OP27GZ –40° to +85°C 8-Lead CERDIP Z-Suffix (Q-8)
OP27EP 0° to +70°C 8-Lead PDIP P-Suffix (N-8)
OP27EPZ
OP27GP –40° to +85°C 8-Lead PDIP P-Suffix (N-8)
OP27GPZ
OP27GS –40° to +85°C 8-Lead SOIC S-Suffix (R-8)
OP27GS-REEL –40° to +85°C 8-Lead SOIC S-Suffix (R-8)
OP27GS-REEL7 –40° to +85°C 8-Lead SOIC S-Suffix (R-8)
OP27GSZ
OP27GSZ-REEL
OP27GSZ-REEL7
OP27NBC Die

1

Z = Pb-free part.

1

1

1

1

1

0° to +70°C 8-Lead PDIP P-Suffix (N-8)

–40° to +85°C 8-Lead PDIP P-Suffix (N-8)

–40° to +85°C 8-Lead SOIC S-Suffix (R-8)
–40° to +85°C 8-Lead SOIC S-Suffix (R-8)
–40° to +85°C 8-Lead SOIC S-Suffix (R-8)

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