Datasheet MC 44603 AP Datasheet

Page 1

MC44603A

Enhanced Mixed Frequency Mode GreenLinet PWM Controller:

Fixed Frequency, Variable Frequency, Standby Mode

The MC44603A is an enhanced high performance controller that is specifically designed for off−line and dc−to−dc converter applications. This device has the unique ability of automatically changing operating modes if the converter output is overloaded, unloaded, or shorted, offering the designer additional protection for increased system reliability. The MC44603A has several distinguishing features when compared to conventional SMPS controllers. These features consist of a foldback facility for overload protection, a standby mode when the converter output is slightly loaded, a demagnetization detection for reduced switching stresses on transistor and diodes, and a high current totem pole output ideally suited for driving a power MOSFET. It can also be used for driving a bipolar transistor in low power converters (< 150 W). It is optimized to operate in discontinuous mode but can also operate in continuous mode. Its advanced design allows use in current mode or voltage mode control applications.

Features

• Pb−Free Packages are Available*

Current or Voltage Mode Controller

• Operation up to 250 kHz Output Switching Frequency

• Inherent Feed Forward Compensation

• Latching PWM for Cycle−by−Cycle Current Limiting

• Oscillator with Precise Frequency Control

High Flexibility

• Externally Programmable Reference Current

• Secondary or Primary Sensing7

• Synchronization Facility

• High Current Totem Pole Output

• Undervoltage Lockout with Hysteresis

Safety/Protection Features

• Overvoltage Protection Against Open Current and Open Voltage Loop

• Protection Against Short Circuit on Oscillator Pin

• Fully Programmable Foldback

• Soft−Start Feature

• Accurate Maximum Duty Cycle Setting

• Demagnetization (Zero Current Detection) Protection

• Internally Trimmed Reference

• Enhanced Output Drive

GreenLine Controller: Low Power Consumption in Standby Mode

• Low Startup and Operating Current

• Fully Programmable Standby Mode

• Controlled Frequency Reduction in Standby Mode

• Low dV/dT for Low EMI Radiations

*For additional information on our Pb−Free strategy and soldering details, please download the ON Semiconductor Soldering and Mounting

Techniques Reference Manual, SOLDERRM/D.

Foldback Input

Protection (OVP)

Current Sense Input

Demag Detection

See detailed ordering and shipping information in the package dimensions section on page 21 of this data sheet.

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PDIP−16

P SUFFIX

CASE 648

SOIC−16

DW SUFFIX CASE 751G

A = Assembly Location WL = Wafer Lot YY = Year WW = Work Week G = Pb−Free Package

PIN CONNECTIONS

1 16

Output

GND

Overvoltage

(Top View)

ORDERING INFORMATION

MARKING

DIAGRAMS

MC44603AP

AWLYYWWG

MC44603ADW

AWLYYWWG

ref

Frequency

Standby Voltage Feedback Input

Error Amp Output

Power Standby

Soft−Start/D Voltage Mode

Sync Input

max

November, 2005 − Rev. 4

1 Publication Order Number:

MC44603A/D

Page 2

MC44603A

MAXIMUM RATINGS

Rating Symbol Value Unit

Total Power Supply and Zener Current (ICC + IZ) 30 mA Supply Voltage with Respect to Ground (Pin 4) V

Output Current (Note 1) mA

Source I Sink I

O(Source)

O(Sink)

Output Energy (Capacitive Load per Cycle) W 5.0 R

, CT, Soft−Start, R

F Stby

Foldback Input, Current Sense Input,

, R

ref

Inputs V

P Stby

E/A Output, Voltage Feedback Input, Overvoltage Protection, Synchronization Input

Synchronization Input

High State Voltage V Low State Reverse Current V

IH IL

Demagnetization Detection Input Current mA

Source I Sink I

Error Amplifier Output Sink Current I

demag−ib (Source)

demag−ib (Sink)

E/A (Sink)

Power Dissipation and Thermal Characteristics

P Suffix, Dual−In−Line, Case 648

Maximum Power Dissipation at TA = 85°C P Thermal Resistance, Junction−to−Air



DW Suffix, Surface Mount, Case 751G

Maximum Power Dissipation at TA = 85°C P

Thermal Resistance, Junction−to−Air Operating Junction Temperature T Operating Ambient Temperature T



JA J

Maximum ratings are those values beyond which device damage can occur. Maximum ratings applied to the device are individual stress limit values (not normal operating conditions) and are not valid simultaneously. If these limits are exceeded, device functional operation is not implied, damage may occur and reliability may be affected.

1. ESD data available upon request.

18 V

−750 750

−0.3 to 5.5 V

−0.3 to V

+ 0.3

VCC + 0.3 V

−20 mA

−4.0 10 20 mA

0.6 W

100 °C/W

0.45 W

145 °C/W 150 °C

−25 to +85 °C

J

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Page 3

MC44603A

ELECTRICAL CHARACTERISTICS (V

and VC = 12 V, (Note 2), R

= 10 k, CT = 820 pF, for typical values TA =

ref

25°C, for min/max values TA = −25° to +85°C (Note 3), unless otherwise noted.)

Characteristic Symbol Min Typ Max Unit

OUTPUT SECTION

Output Voltage (Note 4) V

Low State (I

High State (I

Output Voltage During Initialization Phase

VCC = 0 to 1.0 V, I VCC = 1.0 to 5.0 V, I

VCC = 5.0 to 13 V, I Output Voltage Rising Edge Slew−Rate (CL = 1.0 nF, TJ = 25°C) dVo/dT − 300 − Output Voltage Falling Edge Slew−Rate (CL = 1.0 nF, TJ = 25°C) dVo/dT − −300 −

= 100 mA)

Sink

= 500 mA)

Sink

Source Source

= 200 mA) = 500 mA)

= 10 A

Sink

= 100 A

Sink

= 1.0 mA

Sink

−

1.0

1.4

1.5

2.0

0.1

1.2

2.0

2.7

−

1.0

1.0 V/s

V/s

ERROR AMPLIFIER SECTION

Voltage Feedback Input (V Input Bias Current (VFB = 2.5 V) I Open Loop Voltage Gain (V

= 2.5 V) V

E/A out

= 2.0 to 4.0 V) A

E/A out

FB−ib

VOL

2.42 2.5 2.58 V

−2.0 −0.6 − 65 70 − dB

Unity Gain Bandwidth BW MHz

TJ = 25°C − 4.0 − TJ = −25° to +85°C − − 5.5

Voltage Feedback Input Line Regulation (VCC = 10 to 15 V) V

FBline−reg

−10 − 10 mV

Output Current mA

Sink (V

= 1.5 V, VFB = 2.7 V)

E/A out

Sink

2.0 12 −

TA = −25° to +85°C

Source (V

= 5.0 V, VFB = 2.3 V)

E/A out

Source

−2.0 − −0.2

TA = −25° to +85°C

Output Voltage Swing V

High State (I Low State (I

E/A out (source)

E/A out (sink)

= 0.5 mA, VFB = 2.3 V) V

= 0.33 mA, VFB = 2.7 V) V

OH OL

5.5 6.5 7.5

− 1.0 1.1

REFERENCE SECTION

Reference Output Voltage (VCC = 10 to 15 V) V Reference Current Range (I Reference Voltage Over I

ref

Range

ref

= V

, R = 5.0 k to 25 k)

ref/Rref

V

ref

2.4 2.5 2.6 V

−500 − −100

−40 − 40 mV

OSCILLATOR AND SYNCHRONIZATION SECTION

Frequency f

OSC

TA = 0° to +70°C 44.5 48 51.5

TA = −25° to +85°C 44 − 52 Frequency Change with Voltage (VCC = 10 to 15 V) Frequency Change with Temperature (TA = −25° to +85°C)

f

/V

OSC

f

/T

OSC

− 0.05 − %/V

− 0.05 − %/°C

2. Adjust VCC above the startup threshold before setting to 12 V.

3. Low duty cycle pulse techniques are used during test to maintain junction temperature as close to ambient as possible.

4. VC must be greater than 5.0 V.

5. Standby is disabled for V

6. If not used, Synchronization input must be connected to Ground.

7. Synchronization Pulse Width must be shorter than t

8. This function can be inhibited by connecting Pin 8 to GND. This allows a continuous current mode operation.

< 25 mV typical.

R P Stby

OSC

= 1/f

OSC

9. This function can be inhibited by connecting Pin 5 to VCC.

10.The MC44603A can be shut down by connecting the Soft−Start pin (Pin 11) to Ground.

A

kHz

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Page 4

MC44603A

ELECTRICAL CHARACTERISTICS (continued) (V

and VC = 12 V, (Note 2), R

= 10 k, CT = 820 pF, for typical values TA =

ref

25°C, for min/max values TA = −25° to +85°C (Note 3), unless otherwise noted.)

Characteristic UnitMaxTypMinSymbol

OSCILLATOR AND SYNCHRONIZATION SECTION

Oscillator Voltage Swing (Peak−to−Peak) V Ratio Charge Current/Reference Current I

OSC(pp)

charge/Iref

1.65 1.8 1.95 V

TA = 0° to +70°C (VCT = 2.0 V) 0.375 0.4 0.425

TA = −25° to +85°C 0.37 − 0.43 Fixed Maximum Duty Cycle = I Ratio Standby Discharge Current versus I

TA = 0° to +70°C I

discharge

/(I

discharge

R F Stby

+ I

) D 78 80 82 %

charge

(Note 5) I

disch−Stby

R F Stby

/ −

0.46 0.53 0.6

TA = −25° to +85°C (Note 8) 0.43 − 0.63 V

R F Stby

= 100 A)

Frequency in Standby Mode (R

(Pin 15) = 25 k)

F Stby

Current Range I Synchronization Input Threshold Voltage (Note 6) V

Synchronization Input Current I Minimum Synchronization Pulse Width (Note 7) t

R F Stby

Stby

R F Stby

inthH

inthL

Sync−in

Sync

2.4 2.5 2.6 V 18 21 24 kHz

−200 − −50

3.2

0.45

3.7

0.7

4.3

0.9

−5.0 − 0

− − 0.5

UNDERVOLTAGE LOCKOUT SECTION

Startup Threshold V Output Disable Voltage After Threshold Turn−On (UVLO 1) V

stup−th

disable1

13.6 14.5 15.4 V

TA = 0° to +70°C 8.6 9.0 9.4 TA = −25° to +85°C 8.3 − 9.6

Reference Disable Voltage After Threshold Turn−On (UVLO 2) V

disable2

7.0 7.5 8.0 V

DEMAGNETIZATION DETECTION SECTION (Note 8)

Demagnetization Detect Input

Demagnetization Comparator Threshold (V

Decreasing) V

Pin 9

demag−th

50 65 80 mV

Propagation Delay (Input to Output, Low to High) − − 0.25 −

Input Bias Current (V Negative Clamp Level (I Positive Clamp Level (I

= 65 mV) I

demag

= −2.0 mA) C

demag

= 2.0 mA) C

demag

demag−lb

L(neg)

L(pos)

−0.5 − −

− −0.38 − V

− 0.72 − V

SOFT−START SECTION (Note 10)

Ratio Charge Current/I

ref

ss(ch)/Iref

TA = 0° to +70°C 0.37 0.4 0.43

TA = −25° to +85°C 0.36 − 0.44 Discharge Current (V Clamp Level V

= 1.0 V) I

soft−start

discharge

ss(CL)

1.5 5.0 − mA

2.2 2.4 2.6 V

2. Adjust VCC above the startup threshold before setting to 12 V.

3. Low duty cycle pulse techniques are used during test to maintain junction temperature as close to ambient as possible.

4. VC must be greater than 5.0 V.

5. Standby is disabled for V

6. If not used, Synchronization input must be connected to Ground.

7. Synchronization Pulse Width must be shorter than t

8. This function can be inhibited by connecting Pin 8 to GND. This allows a continuous current mode operation.

< 25 mV typical.

R P Stby

OSC

= 1/f

OSC

9. This function can be inhibited by connecting Pin 5 to VCC.

10.The MC44603A can be shut down by connecting the Soft−Start pin (Pin 11) to Ground.

−

A

A s

s A

−

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Page 5

MC44603A

ELECTRICAL CHARACTERISTICS (continued) (V

and VC = 12 V, (Note 2), R

= 10 k, CT = 820 pF, for typical values TA =

ref

25°C, for min/max values TA = −25° to +85°C (Note 3), unless otherwise noted.)

Characteristic UnitMaxTypMinSymbol

SOFT−START SECTION (Note 10)

Duty Cycle (R

Duty Cycle (V

= 12 k)

soft−start

soft−start (Pin 11)

= 0.1 V)

soft−start 12k

soft−start

−

OVERVOLTAGE SECTION

Protection Threshold Level on V Propagation Delay (V Protection Level on V

> 2.58 V to V

OVP

Low) 1.0 − 3.0

out

OVP−th

CC prot

2.42 2.5 2.58 V

TA = 0° to +70°C 16.1 17 17.9

TA = −25° to +85°C 15.9 − 18.1 Input Resistance −

TA = 0° to +70°C 1.5 2.0 3.0

TA = −25° to +85°C 1.4 − 3.4

FOLDBACK SECTION (Note 9)

Current Sense Voltage Threshold (V Foldback Input Bias Current (V

foldback (Pin 5)

= 0.9 V) V

= 0 V) I

CS−th

foldback−lb

0.86 0.89 0.9 V

−6.0 −2.0 −

STANDBY SECTION

Ratio I

R P Stby/Iref

TA = 0° to +70°C 0.37 0.4 0.43

TA = −25° to +85°C 0.36 − 0.44 Ratio Hysteresis (Vh Required to Return to Normal Operation from

Vh/V

R P Stby

Standby Operation)

TA = 0° to +70°C 1.42 1.5 1.58

TA = −25° to +85°C 1.4 − 1.6 Current Sense Voltage Threshold (V

R P Stby (Pin 12)

= 1.0 V) V

CS−Stby

0.28 0.31 0.34 V

CURRENT SENSE SECTION

Maximum Current Sense Input Threshold

feedback (Pin 14)

= 2.3 V and V

foldback (Pin 6)

= 1.2 V) Input Bias Current I Propagation Delay (Current Sense Input to Output at VTH of

CS−ib

CS−th

0.96 1.0 1.04 V

−10 −2.0 −

− − 120 200 ns

MOS transistor = 3.0 V)

TOTAL DEVICE

Power Supply Current I

Startup (VCC = 13 V with VCC Increasing) − 0.3 0.45 Operating TA = −25° to +85°C (Note 2) 13 17 20

Power Supply Zener Voltage (ICC = 25 mA) V

18.5 − − V

Thermal Shutdown − − 155 − °C

2. Adjust VCC above the startup threshold before setting to 12 V.

3. Low duty cycle pulse techniques are used during test to maintain junction temperature as close to ambient as possible.

4. VC must be greater than 5.0 V.

5. Standby is disabled for V

6. If not used, Synchronization input must be connected to Ground.

7. Synchronization Pulse Width must be shorter than t

8. This function can be inhibited by connecting Pin 8 to GND. This allows a continuous current mode operation.

< 25 mV typical.

R P Stby

OSC

= 1/f

OSC

9. This function can be inhibited by connecting Pin 5 to VCC.

10.The MC44603A can be shut down by connecting the Soft−Start pin (Pin 11) to Ground.

s

k

A

−

A

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Page 6

MC44603A

Demag

Detect

Sync Input

Pwr Stby

Feed−

back

Compensation

Foldback

Input

Negative

0.4 I

Active

Clamp

ref

65 mV

ref

3.7 V

0.7 V

F Stby

15 16

F Stby

Demag Out

Synchro

OSC prot

Reference

refIref

Block

ref

UVLO2

18.0 V

aux

14.5 V/7.5 V To Power

F Stby

Transformer

1.0 V

0.8 I

ref

Discharge/2

refVref

1.0 V

Discharge

0.25 IF

Stby

Current Mirror X2

OSC

Thermal

Shutdown

ref

0.2 I

ref

0.4 I

ref

2.0 s Delay

ref

5.0 s

V Out

OVP

ref

11.6 k

Delay

2.0 k

1.6 V

2.5 V

UVLO1

2.4 V

5.0 mA +

9.0 V

1.6 V

0.4 I

ref

3.6 V

0.4 I

refVref

ref

0.6 I

ref

1.0 mA

2.5 V

Error Amplifier

Output

GND

OVP

Current Sense Input

= Sink only

= Positive True Logic

SS/D

/VM

max

This device contains 243 active transistors.

Figure 1. Representative Block Diagram

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Page 7

MC44603A

, TIMING RESISTANCE (k )Ω

100

ref

CT = 2200 pF

10 k

CT = 100 pF

VCC = 16 V TA = 25°C

CT = 500 pF

CT = 1000 pF

, Oscillator Frequency (Hz)

OSC

Figure 2. Timing Resistor versus

Oscillator Frequency

10000

100010

, TIMING CAPACITOR (pF)

3003.0

0.43

0.42

0.41

0.40

= 2.0 k

F Stby

= 5.0 k

F Stby

= 27 k

F Stby

= 100 k

F Stby

10 k

OSC

100 k100 k 1.0 M1.0 M

, Oscillator Frequency (Hz)

Figure 3. Standby Mode Timing Capacitor

versus Oscillator Frequency

VCC = 16 V TA = 25°C R

= 10 k

ref

, OSCILLATOR FREQUENCY (kHz)

OSC

VCC = 12 V R

= 10 k

ref

CT = 820 pF

−50 −25 0 25 50 75 100

TA, AMBIENT TEMPERATURE (°C)

Figure 4. Oscillator Frequency

versus Temperature

600

400

200

Current

VCC = 12 V CL = 2200 pF TA = 25°C

−200

−400

, OUTPUT CURRENT (mA)

−600 O

Voltage

−800

−1000

Figure 6. Output Waveform Figure 7. Output Cross Conduction

0.39

= RATIO CHARGE CURRENT/I

REFERENCE CURRENT

ref

0.38

charge

0.37

, OUTPUT DRIVE VOLTAGE (V)

−10

, OUTPUT DRIVE VOLTAGE (V)

−10

VCC = 12 V R

= 10 k

ref

CT = 820 pF

−50 −25 0 25 50 75 100

TA, AMBIENT TEMPERATURE (°C)

Figure 5. Ratio Charge Current/Reference

Current versus Temperature

VCC = 12 V CL = 2200 pF TA = 25°C

Current

Voltage

1.0 s/Div1.0 s/Div

−1

−

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Page 8

MC44603A

500

475

450

425

400

375

350

, DISCHARGE CURRENT (μA)

325

disch

300

−50 −25 0 25 50 75 100

VCC = 12 V R

= 10 k

ref

CT = 820 pF

Figure 8. Oscillator Discharge Current

versus Temperature

Sink Saturation (Load to VCC)

1.6

1.2

2.5

2.0

1.5

1.0

, SOURCE OUTPUT SATURATION VOLTAGE (V)

0 100 200 300 400 500

, OUTPUT SOURCE CURRENT (mA)TA, AMBIENT TEMPERATURE (°C)

source

Figure 9. Source Output Saturation Voltage

versus Load Current

802.0

VCC = 12 V G = 10 Vin = 30 mV VO = 2.0 to 4.0 V RL = 100 k TA = 25°C

VCC = 12 V R

= 10 k

ref

CT = 820 pF TA = 25°C

140

0.8

TA = 25°C

0.4

, SINK OUTPUT SATURATION VOLTAGE (V)

0 100

200 300 400 500

, SINK OUTPUT CURRENT (mA)

sink

VCC = 12 V 80 s Pulsed Load 120 Hz Rate

Figure 10. Sink Output Saturation Voltage

versus Sink Current

2.60

VCC = 12 V

2.55

2.50

2.45

, VOLTAGE FEEDBACK INPUT (V)

2.40

−50 −25 0 25 50 75 100

TA, AMBIENT TEMPERATURE (°C)

G = 10 VO = 2.0 to 4.0 V RL = 100 k

Figure 12. Voltage Feedback Input

versus Temperature

GAIN (dB)

−20 01234

1010 10 10

f, FREQUENCY (kHz)

Figure 11. Error Amplifier Gain and Phase

versus Frequency

, DEMAG COMPARATOR THRESHOLD (mV)

−50 −25 0 25 50 75 100

demag−th

TA, AMBIENT TEMPERATURE (°C)

VCC = 12 V

Figure 13. Demag Comparator Threshold

versus Temperature

PHASE (DEGREES)

−40

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Page 9

3.2

MC44603A

100

Printed circuit board heatsink example

5.0

3.1

3.0

, CURRENT SENSE GAIN

2.9

VCS

VCC = 12 V R

= 10 k

ref

CT = 820 pF

2.8

−50 −25 0 25 50 75 100

TA, AMBIENT TEMPERATURE (°C)

Figure 14. Current Sense Gain

versus Temperature

140

120

100

PROPAGATION DELAY (ns)

VCC = 12 V R

= 10 k

ref

CT = 820 pF



2.0 oz

Copper

Graphs represent symmetrical layout

for TA = 70°C

, THERMAL RESISTANCE JUNCTION−TO−AIR ( C/W)

D(max)

10 20 30 40 50

L, LENGTH OF COPPER (mm)

Figure 15. Thermal Resistance and Maximum

Power Dissipation versus P.C.B. Copper Length

0.35

0.30

0.25

0.20

0.15

0.10

STARTUP CURRENT (mA)

0.05

3.0 mm

= 10 k

ref

CT = 820 pF

4.0

3.0

2.0

1.0

, MAXIMUM POWER DISSIPATION (W)

−50 −25 0 25 50 75 100

TA, AMBIENT TEMPERATURE (°C)

Figure 16. Propagation Delay Current Sense

Input to Output versus Temperature

8.0

TA = 25°C

6.0 R

= 10 k

, SUPPLY CURRENT (mA)

4.0

2.0

ref

CT = 820 pF VFB = 0 V VCS = 0 V

2.0 4.0 6.0 8.0 10 12 14 16

VCC, SUPPLY VOLTAGE (V)

Figure 18. Supply Current versus

Supply Voltage

4.00 2.0 6.0

8.0 10 12 14

VCC, SUPPLY VOLTAGE (V)

Figure 17. Startup Current versus V

21.5

21.0

20.5

20.0

, ZENER VOLTAGE (V)

19.5

ICC = 25 mA

19.0

−50 −25 0 25 50 75 100

TA, AMBIENT TEMPERATURE (°C)

Figure 19. Power Supply Zener Voltage

versus Temperature

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Page 10

MC44603A

OVP

)

out

15.5

15.0

14.5

VCC Increasing VCC Decreasing

14.0

, STARTUP THRESHOLD VOLTAGE (V)

stup−th

13.5

−50 −25 0 25 50 75 100

TA, AMBIENT TEMPERATURE (°C)

Figure 20. Startup Threshold Voltage

versus Temperature

7.8

7.6

, UVLO2 (V)

7.4 VCC Decreasing

7.2

disable2

7.0

6.8

−50 −25 0 25 50 75 100

TA, AMBIENT TEMPERATURE (°C)

Figure 22. Disable Voltage After Threshold

Turn−On (UVLO2) versus Temperature

9.50

9.25

, UVLO1 (V)

9.00

disable1

8.55

8.50

−50 −25 0 25 50 75 100

TA, AMBIENT TEMPERATURE (°C)

Figure 21. Disable Voltage After Threshold

Turn−On (UVLO1) versus Temperature

2.608.0

2.55

2.50

2.45

2.40

2.35

, PROTECTION THRESHOLD LEVEL (V

2.30

OVP−th

−50 −25 0 25 50 75 100

TA, AMBIENT TEMPERATURE (°C)

VCC = 12 V

Figure 23. Protection Threshold Level on

versus Temperature

= 10 k

ref

CT = 820 pF Pin 6 Open

, PROTECTION LEVEL (V)

16.5

CC prot

−50 −25 0 25 50 75 100

TA, AMBIENT TEMPERATURE (°C)

Figure 24. Protection Level on V

versus Temperature

3.0

μPROPAGATION DELAY ( s)

2.517.5

2.0

1.5

1.0

−50 −25 0 25 50 75 100

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TA, AMBIENT TEMPERATURE (°C)

Figure 25. Propagation Delay (V

to V

Low) versus Temperature

VCC = 12 V R

= 10 k

ref

CT = 820 pF

> 2.58 V

OVP

Page 11

μIA)

270

265

260

255

250

245

R P Stdby (Pin 12)

Voltage Increasing

240

, STANDBY REFERENCE CURRENT (

235

230

R P Stby

−50 −25 0 25 50 75 100

TA, AMBIENT TEMPERATURE (°C)

MC44603A

0.33

0.32

0.31

STANDBY MODE (V)

, CURRENT SENSE THRESHOLD

CS−stby

0.30

VCC = 12 V R

= 10 k

ref

CT = 820 pF Pin 12 Clamped at 1.0 V

−50 −25 0 25 50 75 100

TA, AMBIENT TEMPERATURE (°C)

Figure 26. Standby Reference Current

versus Temperature

Figure 27. Current Sense Voltage Threshold

Standby Mode versus Temperature

PIN FUNCTION DESCRIPTION

Pin Name Description

1 V 2 V

3 Output Peak currents up to 750 mA can be sourced or sunk, suitable for driving either MOSFET or Bipolar

4 GND The ground pin is a single return, typically connected back to the power source; it is used as control and

5 Foldback Input The foldback function provides overload protection. Feeding the foldback input with a portion of the V

6 Overvoltage

Protection

7 Current Sense

Input

8 Demagnetization

Detection

9 Synchronization

Input

10 C

11 Soft−Start/D

Voltage−Mode

12 R

P Standby

13 E/A Out The error amplifier output is made available for loop compensation. 14 Voltage

Feedback 15 R 16 R

F Standby

ref

This pin is the positive supply of the IC. The operating voltage range after startup is 9.0 to 14.5 V. The output high state (VOH) is set by the voltage applied to this pin. With a separate connection to the power

source, it can reduce the effects of switching noise on the control circuitry.

transistors. This output pin must be shunted by a Schottky diode, 1N5819 or equivalent.

power ground.

voltage (1.0 V max) establishes on the system control loop a foldback characteristic allowing a smoother startup and sharper overload protection. Above 1.0 V the foldback input is inactive.

When the overvoltage protection pin receives a voltage greater than 17 V, the device is disabled and requires a complete restart sequence. The overvoltage level is programmable.

A voltage proportional to the current flowing into the power switch is connected to this input. The PWM latch uses this information to terminate the conduction of the output buffer when working in a current mode of operation. A maximum level of 1.0 V allows either current or voltage mode operation.

A voltage delivered by an auxiliary transformer winding provides to the demagnetization pin an indication of the magnetization state of the flyback transformer. A zero voltage detection corresponds to complete core saturation. The demagnetization detection ensures a discontinuous mode of operation. This function can be inhibited by connecting Pin 8 to GND.

The synchronization input pin can be activated with either a negative pulse going from a level between 0.7 V and 3.7 V to GND or a positive pulse going from a level between 0.7 V and 3.7 V up to a level higher than

3.7 V. The oscillator runs free when Pin 9 is connected to GND. The normal mode oscillator frequency is programmed by the capacitor CT choice together with the R

resistance value. CT, connected between Pin 10 and GND, generates the oscillator sawtooth.

A capacitor, resistor or a voltage source connected to this pin limits the switching duty−cycle. This pin can

max

be used as a voltage mode control input. By connecting Pin 11 to Ground, the MC44603A can be shutdown. A voltage level applied to the R

turn into the reduced frequency mode of operation (i.e. standby mode). An internal hysteresis comparator

pin determines the output power level at which the oscillator will

P Standby

allows to return in the normal mode at a higher output power level.

This is the inverting input of the Error Amplifier. It can be connected to the switching power supply output through an optical (or other) feedback loop.

The reduced frequency or standby frequency programming is made by the R R

sets the internal reference current. The internal reference current ranges from 100 A to 500 A. This

ref

requires that 5.0 k ≤ R

≤ 25 k.

ref

resistance choice.

F Standby

ref

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Page 12

MC44603A

CC prot

stup−th

disable1

disable2

UVLO1

Pin 11

(Soft−Start)

OVP Out

Output

No−Take Over Loop Failure

Startup Restart

>2.0 s

Normal Mode

ref

17 mA

0.3 mA

Figure 28. Starting Behavior and Overvoltage Management

Demag In

Output

(Pin 3)

Demag Out

Demag In

Demagnetization

Management

Demag Out

Oscillator

Figure 29. Demagnetization

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Buffer Output

Page 13

stup−th

disable1

disable2

UVLO1

Pin 11

(Soft−Start)

Output (Pin 3)

MC44603A

ref

Demag Out

OSC prot

0.3 mA

1.0 V

Stby

OSC

17 mA

Figure 30. Switching Off Behavior

Demag Out

3.6 V

1.6 V

Synchronization

Input

Oscillator

Stby

Figure 31. Oscillator

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OSC prot

OSC

Page 14

max

VCT low

Output (Pin 3)

MC44603A

ref

+ 1.6 V

CSS

3.6 V

1.6 V

OSC

Soft−Start

Figure 32. Soft−Start & D

Internal Clamp

External Clamp

OPERATING DESCRIPTION

Error Amplifier

A fully compensated Error Amplifier with access to the inverting input and output is provided. It features a typical DC voltage gain of 70 dB. The noninverting input is internally biased at 2.5 V and is not pinned out. The converter output voltage is typically divided down and monitored by the inverting input. The maximum input bias current with the inverting input at 2.5 V is −2.0 A. This can cause an output voltage error that is equal to the product of the input bias current and the equivalent input divider source resistance.

The Error Amp output (Pin 13) is provided for external loop compensation. The output voltage is offset by two diode drops (≈ 1.4 V) and divided by three before it connects to the inverting input of the Current Sense Comparator. This guarantees that no drive pulses appear at the Output (Pin 3) when Pin 13 is at its lowest state (VOL). The Error Amp minimum feedback resistance is limited by the amplifier’s minimum source current (0.2 mA) and the required output voltage (VOH) to reach the current sense comparator’s 1.0 V clamp level:

f(min)

3.0 (1.0V) ) 1.4 V

[

0.2 mA

+ 22 k

Compensation

Voltage

Feedback

Input

Foldback

Input

2.5 V

Amplifier

From Power Supply Output

Error

1.0 mA

Current Sense

Comparator

1.0 V

GND 4

Figure 33. Error Amplifier Compensation

Current Sense Comparator and PWM Latch

The MC44603A can operate as a current mode controller or as a voltage mode controller. In current mode operation, the MC44603A uses the current sense comparator. The output switch conduction is initiated by the oscillator and terminated when the peak inductor current reaches the

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Page 15

MC44603A

threshold level established by the Error Amplifier output (Pin 13). Thus, the error signal controls the peak inductor current on a cycle−by−cycle basis. The Current Sense Comparator PWM Latch ensures that only a single pulse appears at the Source Output during the appropriate oscillator cycle.

The inductor current is converted to a voltage by inserting the ground referenced sense resistor RS in series with the power switch Q1.

This voltage is monitored by the Current Sense Input (Pin 7) and compared to a level derived from the Error Amp output. The peak inductor current under normal operating conditions is controlled by the voltage at Pin 13 where:

(Pin 13) – 1.4V

[

The Current Sense Comparator threshold is internally clamped to 1.0 V. Therefore, the maximum peak switch current is:

1.0 V

[

Substrate

1N5819

Current Sense

Demag Out

Thermal

Protection

Current Sense

Comparator

pk(max)

OSC prot

UVLO

RSQ R

PWM Latch

Figure 34. Output Totem Pole

connected to the c harging current source ( 0.4 I

) and so,

ref

the discharge current source has to be higher than the charge current to be able to decrease t he CT voltage (refer to Figure 36).

This condition is performed, its value being (2.0 I

normal working and (0.4 I

ref

0.4 I

1.0 V

1.6 V

3.6 V

Regul

Figure 35. Oscillator

ref

Charge

0.4 I

ref

Discharge

+ 0.5 I

ref

VOS prot

OSC Low

CT < 1.6 V

Discharge

OSC High

OSC Regul

0: Discharge Phase 1: Charge Phase

Disch

in standby mode).

F Stby

OSC prot

OSC

1.6 V

Regul

OSC Regul

Synchro

Demag

Out

Discharge

ref

) in

OSC

Series gate resistor, R2, will dampen any high frequency oscillations caused by the MOSFET input capacitance and any series wiring inductance in the gate−source circuit. Diode D is required if the negative current into the output drive pin exceeds 15 mA.

Oscillator

The oscillator is a very accurate sawtooth generator that can work either in free mode or in synchronization mode. In this second mode, the oscillator stops in the low state and waits for a demagnetization or a synchronization pulse to start a new charging cycle.

• The Sawtooth Generation:

In the steady state, the oscillator voltage varies between about 1.6 V and 3.6 V.

The s awtooth is o btained b y charging a nd d ischarging a n external capacitor CT (Pin 10), using two distinct current sources = I

charge

and I

discharge

. In fact, CT is permanently

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Figure 36. Simplified Block Oscillator

Two comparators are used to generate the sawtooth. They compare the CT voltage to the oscillator valley (1.6 V) and peak reference (3.6 V) values. A latch (L

) memorizes

disch

the oscillator state.

In addition to the charge and discharge cycles, a third state can exist. This phase can be produced when, at the end of the discharge phase, the oscillator has to wait for a synchronization or demagnetization pulse before restarting. During this delay, the CT voltage must remain equal to the oscillator valley value (]1.6 V). So, a third regulated current source I to CT in order to perfectly compensate the (0.4 I

controlled by C

Regul

OSC Regul

, is connected

ref

source that permanently supplies CT.

The maximum duty cycle is 80%. Indeed, the on−time is allowed only during the oscillator capacitor charge.

) current

Page 16

MC44603A

Consequently:

= CT x V/I

charge

discharge

= CT x V/I

charge

discharge

where:

is the oscillator charge time

charge

V is the oscillator peak−to−peak value I

is the oscillator charge current

charge

and

discharge

So, as fS = 1 /(T

is the oscillator discharge time

is the oscillator discharge current

charge

+ T

discharge

) when the Regul arrangement is not activated, the operating frequency can be obtained from the graph in Figure 2.

NOTE: The output is disabled by the signal V

OSC prot

when

VCT is lower than 1.0 V (refer to Figure 31).

Synchronization and Demagnetization Blocks

To enable the output, the L output must be low. Reset is activated by the L during the discharge phase. T o restart, the L

latch complementary

OSC

disch

has to be set

OSC

output

(refer to Figure 35). To perform this, the demagnetization signal and the synchronization must be low.

• Synchronization:

The synchronization block consists of two comparators that compare the synchronization signal (external) to 0.7 and

3.7 V (typical values). The comparators’ outputs are connected to the input of an AND gate so that the final output of the block should be:

− high when 0.7 < SYNC < 3.7 V

− low in the other cases.

As a low level is necessary to enable the output, synchronized low level pulses have to be generated on the output of the synchronization block. If synchronization is not required, the Pin 9 must be connected to the ground.

3.7 V

That is why, the MC44603A demagnetization detection consists of a comparator that can compare the auxiliary winding voltage to a reference that is typically equal to 65 mV.

Zero Current

Pin 8

On−Time Off−Time Dead−Time

Figure 38. Demagnetization Detection

Detection

0.75 V

65 mV

−0.33 V

A diode D has been incorporated to clamp the positive applied voltages while an active clamping system limits the negative voltages to typically −0.33 V. This negative clamp level is sufficient to avoid the substrate diode switching on.

In addition to the comparator, a latch system has been incorporated in order to keep the demagnetization block output level low as soon as a voltage lower than 65 mV is detected and as long as a new restart is produced (high level on the output) (refer to Figure 39). This process prevents ringing on the signal at Pin 8 from disrupting the demagnetization detection. This results in a very accurate demagnetization detection.

The demagnetization block output is also directly connected to the output, disabling it during the demagnetization phase (refer to Figure 34).

NOTE: The demagnetization detection can be inhibited by connecting Pin 8 to the ground.

Oscillator

Output Buffer

0.7 V

Figure 37. Synchronization

Sync

• Demagnetization:

In flyback applications, a good means to detect magnetic saturation of the transformer core, or demagnetization, consists in using the auxiliary winding voltage. This voltage is:

− negative during the on−time,

− positive during the off−time,

− equal to zero for the dead−time with generally some

− ringing (refer to Figure 38).

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Oscillator Output

RSQ Demag

Negative Active

Clamping System

C Dem

65 mV

Standby

Buffer

Demag Out

Figure 39. Demagnetization Block

• Power Losses in a Classical Flyback Structure

Page 17

MC44603A

Clamping Network

Snubber

AC Line

ICL

startup

MC44603A

Figure 40. Power Losses in a Classical

Flyback Structure

In a classical flyback (as depicted in Figure 40), the standby losses mainly consist of the energy waste due to:

− the startup resistor R

startup

→ P

startup

− the consumption of the IC and the power

− switch control → P

− the inrush current limitation resistor R

ICL

− the switching losses in the power switch → P

− the snubber and clamping network → P

is nearly constant and is equal to:

startup

(Vin–VCC)2ńR

only depends on the current drawn from the mains.

ICL

startup

→ P

control

ICL SW SN−CLN

Losses can be considered constant. This waste of energy decreases when the standby losses are reduced.

increases when the oscillator frequency is

control

increased (each switching requires some energy to turn on the power switch).

PSW and P

SN−CLN

are proportional to the switching

frequency.

Consequently, standby losses can be minimized by

decreasing the switching frequency as much as possible.

The MC44603A was designed to operate at a standby

frequency lower than the normal working one.

• Standby Power Calculations with MC44603A

During a switching period, the energy drawn by the transformer during the on−time to be transferred to the output during the off−time, is equal to:

E +

xLxI

where:

− L is the transformer primary inductor,

− lpk is the inductor peak current.

Input power is labelled Pin:

Pin+ 0.5xLxI

where fS is the normal working switching frequency.

Also,

where RS is the resistor used to measure the power switch current.

Thus, the input power is proportional to V

(VCS being

the internal current sense comparator input).

That is why the standby detection is performed by creating

threshold. An internal current source (0.4 x I

a V

ref

) sets

the threshold level by connecting a resistor to Pin 12.

As depicted in Figure 41, the standby comparator noninverting input voltage is typically equal to (3.0 x VCS + VF) while the inverter input value is (V

P Stby

AmpOut

0.4 I

refVref

ref

0.6 I

ref

Stby

Figure 41. Standby

refVref

0.8 I

ref

Discharge/2IDischarge

C. S. Comparator

0.25 I

F Stby

+ VF).

R P Stby

ref

0.2 I

Current Mirror X2

Oscillator

Discharge

Current

ref

The VCS threshold level is typically equal to [(V labelled P

)/3] and if t he corresponding powe r threshol d i s

R P Stby

thL

+ 0.5 x L x

RPStby

3.0 R

And as:

PStby

RPStby

+ R

RPStby

10.6 x RSxR

PStby

ref

x0.4xI

x0.4x

ref

Lxf

ref

thL

Thus, when the power drawn by the converter decreases, VCS decreases and when VCS becomes lower than [V x (V

)/3], the s t andby m ode i s a ctivated. T his r esult s i n

R P Stby

CS−th

an oscillator discharge current reduction in order to increase the oscillator period and to diminish the switching frequency. As it is represented in Figure 41, the (0.8 x I

ref

current source is disconnected and is replaced by a lower value one (0.25 x I

Where: I

F Stby

= V

F Stby

ref/RF Stby

)

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Page 18

MC44603A

max

In order to prevent undesired mode switching when power is close to the threshold value, a hysteresis that is proportional to V VCS threshold level that is equal to [2.5 x (V

is incorporated creating a second

R P Stby

)/3]. When the standby comparator output is high, a second current source (0.6 x I

) is connected to Pin 12.

ref

Finally, the standby mode function can be shown

graphically in Figure 42.

Normal

Working

thH

thL

[(V

)/3] 2.5 x [(V

R P Stby

Standby

R P Stby

)/3]

Stby

Figure 42. Dynamic Mode Change

This curve shows that there are two power threshold

levels:

− the low one:

fixed by V

thL

R P Stby

− the high one:

thH

+ (2.5)2xP

+ 6.25 x P

thL

Stby

Maximum Duty Cycle and Soft−Start Control

Maximum duty cycle can be limited to values less than

80% by utilizing the D

and soft−start control. As

max

depicted in Figure 43, the Pin 11 voltage is compared to the oscillator sawtooth.

ref

0.4 I

ref

Dmax

2.4 VD

Output

Control

max

Output

Drive

Voltage

max

Pin 11

(Pin 10)

Figure 44. Maximum Duty Cycle Control

Using the internal current source (0.4 I

), the Pin 11

ref

voltage can easily be set by connecting a resistor to this pin.

If a capacitor is connected to Pin 11, the voltage increases from 0 to its maximum value progressively (refer to Figure 45), thereby, implementing a soft−start. The soft−start capacitor is discharged internally when the V

(Pin 1) voltage drops below 9.0 V.

Pin 11

R Connected to Pin 11 I = 0.4 I

ref

C C // R

 = RC

Figure 45. Different Possible Uses of Pin 11

If no external component is connected to Pin 11, an internal zener diode clamps the Pin 11 voltage to a value V that is higher than the oscillator peak value, disabling soft−start and maximum duty cycle limitation.

Foldback

As depicted in Figures 33 and 49, the foldback input (Pin 5) can be used to reduce the maximum VCS value, providing foldback protection. The foldback arrangement is a programmable peak current limitation.

If the output load is increased, the required converter peak current becomes higher and VCS increases until it reaches its maximum value (normally, VCS

= 1.0 V).

max

Then, if the output load keeps on increasing, the system is unable to supply enough energy to maintain the output voltages in regulation. Consequently, the decreasing output can be applied to Pin 5, in order to limit the maximum peak current. In this way, the well known foldback characteristic can be obtained (refer to Figure 46).

Soft−Start Capacitor

Figure 43. D

OSC

and Soft−Start

Oscillator

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Page 19

MC44603A

Nominal

disable2

out

New Startup

Sequence Initiated

pk max

Overload

out

Figure 46. Foldback Characteristic

NOTE: Foldback is disabled by connecting Pin 5 to VCC.

Overvoltage Protection

The overvoltage arrangement consists of a comparator

that compares the Pin 6 voltage to V

(2.5 V) (refer to

ref

Figure 47).

If no external component is connected to Pin 6, the

comparator noninverting input voltage is nearly equal to:

2.0 k

11.6 k ) 2.0 k

The comparator output is high when:

2.0 k

11.6 k ) 2.0 k

xVCCw 2.5 V

à VCCw 17 V

A delay latch (2.0 s) is incorporated in order to sense

overvoltages that last at least 2.0 s.

If this condition is achieved, V

OVP out

, the delay latch output, becomes high. As this level is brought back to the input through an OR gate, V the IC output) until V

is disabled.

ref

remains high (disabling

OVP out

Consequently, when an overvoltage longer than 2.0 s is detected, the output is disabled until VCC is removed and then re−applied.

The VCC is connected after V

has reached steady state

ref

in order to limit the circuit startup consumption.

The overvoltage section is enabled 5.0 s after the regulator has started to allow the reference V

to stabilize.

ref

By connecting an external resistor to Pin 6, the threshold VCC level can be changed.

ref

Undervoltage Lockout Section

F Stby

ref enable

startup

disable2

7.5 V

UVLO1

disable1

9.0 V

Figure 48. V

Startup

14.5 V

UVLO1

(to Soft−Start)

Management

Reference Block:

Voltage and Current

Sources Generator

ref

Pin 15 Pin 16

, I

, ...)

ref

As depicted in Figure 48, an undervoltage lockout has been incorporated to guarantee that the IC is fully functional before allowing system operation.

This block particularly, produces V I

that is determined by the resistor R

ref

(Pin 16 voltage) and

ref

connected between

ref

Pin 16 and the ground:

ref ref

where V

+ 2.5 V (typically)

ref

Another resistor is connected to the Reference Block: R

that is used to fix the standby frequency.

F Stby

In addition to this, VCC is compared to a second threshold level that is nearly equal to 9.0 V (V

disable1

). UVLO1 is generated to reset the maximum duty cycle and soft−start block disabling the output stage as soon as VCC becomes lower than V

. In this way, the circuit is reset and made

disable1

ready for the next startup, before the reference block is disabled (refer to Figure 30). Finally, the upper limit for the minimum normal operating voltage is 9.4 V (maximum value of V ((V

stup−th) min

) and so the minimum hysteresis is 4.2 V.

disable1

= 13.6 V).

The large hysteresis and the low startup current of the MC44603A make it ideally suited for off−line converter applications where efficient bootstrap startup techniques are required.

External Resistor

Out

2.5 V

Enable

2.5 V (V

ref

Delay

)

OVP

11.6 k

2.0 k

OVLO

5.0 s

the Output is Disabled)

Figure 47. Overvoltage Protection

In Out

Delay

2.0 s

(If V

OVP out

= 1.0,

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Page 20

R15

5.6 k

R15 22 k

R17 22 k

R25

1.0 k

185 VAC

270 VAC

RFI

Filter

C8 2.2 nF

C9 1.0 nF

C10 1.0 F

R18 27 k

1.0/5.0 W

C11

1.0 nF

Sync

C12

6.8 nF

D1 ... D4

1N4007

R19 10 k

1.0 nF/1000 V

68 k/2.0 W

MC44603AP

C4 ... C7

100 pF

C1 220 F

220 F

R12

C16

27 k

C15

1.0 nF

R7 180 k

R8 15 k

*D15 1N5819

R10 10

R11 39

C13 100 nF

R9 1.0 k

R12 22

MC44603A

R20

22 k

5.0 W

1N4934

1.0 H

1N4148

C14

4.7 nF

MTP6N60E

R26

1.0 k

C17 47 nF

M856

1.2 k

R6 150

R14

0.2

aux

MR856

C18

2.2 nF

D12

R13

1.0 k

1.0 nF/1.0 kV

4.7 M

MOC8101

TL431

C32 220 pF

MR856

100 F

C29 220 pF

MR852

C26 220 pF

D10

MR852

C23 220 pF

D11

MR852

1000 F

R21 10 k

33 nF

C30

1000 F

C21

C20

22.5 H

100 F

C27

C25

R24

270

C19

100 nF

C33

150 V/0.6 A

C31

0.1 F

30 V/2.0 A

C28

0.1 F

14 V/2.0 A

C24

0.1 F

7.0 V/2.0 A

C22

0.1 F

R23

147.5 k

D14 1N4733

R22

2.5 k

* Diode D15 is required if the negative current into the output pin exceeds 15 mA.

Figure 49. 250 W Input Power Off−Line Flyback Converter with MOSFET Switch

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Page 21

MC44603A

250 W Input Power Fly−Back Converter 185 V − 270 V Mains Range MC44603AP & MTP6N60E

Tests Conditions Results

Line Regulation

150 V

130 V 114 V

7.0 V

Load Regulation

150 V

Cross Regulation

150 V Efficiency Vin = 220 VAC, Pin = 250 W 81% Standby Mode

P input Switching Frequency

Output Short Circuit P Startup Pin = 250 W VAC = 160 V

Vin = 185 VAC to 270 VAC F

= 50 Hz

mains

= 0.6 A

out

= 2.0 A

out

= 2.0 A

out

= 2.0 A

out

Vin = 220 VAC I

= 0.3 A to 0.6 A 50 mV

out

Vin = 220 VAC I

(150 V) = 0.6 A

out

(30 V) = 0 A to 2.0 A

out

(14 V) = 2.0 A

out

(7.0 V) = 2.0 A

out

Vin = 220 VAC, P

= 270 W Safe on all outputs

out (max)

= 0 W 3.3 W

out

10 mV 10 mV 10 mV 20 mV

< 1.0 mV

20 kHz fully stable

DEVICE ORDERING INFORMATION

Device Operating Temperature Range Package Shipping

MC44603AP MC44603APG PDIP−16

PDIP−16 25 Units / Rail

25 Units / Rail

(Pb−Free) MC44603ADW SOIC−16 47 Units / Rail MC44603ADWG SOIC−16

TA = −25°C to +85°C

47 Units / Rail

(Pb−Free) MC44603ADWR2 SOIC−16 1000 / Tape & Reel MC44603ADWR2G SOIC−16

1000 / Tape & Reel

(Pb−Free)

†For information on tape and reel specifications, including part orientation and tape sizes, please refer to our Tape and Reel Packaging

Specifications Brochure, BRD8011/D.

†

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Page 22

MC44603A

PACKAGE DIMENSIONS

PDIP−16

CASE 648−08

ISSUE T

−A−

916

16 PL

0.25 (0.010) T

16 9

H8X

0.25

B16X

0.25 B

14X

GreenLine is a trademark of Motorola, Inc.

NOTES:

1. DIMENSIONING AND TOLERANCING PER ANSI Y14.5M, 1982.

2. CONTROLLING DIMENSION: INCH.

3. DIMENSION L TO CENTER OF LEADS WHEN

SEATING

−T−

PLANE

FORMED PARALLEL.

4. DIMENSION B DOES NOT INCLUDE MOLD FLASH.

5. ROUNDED CORNERS OPTIONAL.

DIM MIN MAX MIN MAX

A 0.740 0.770 18.80 19.55 B 0.250 0.270 6.35 6.85 C 0.145 0.175 3.69 4.44 D 0.015 0.021 0.39 0.53 F 0.040 0.70 1.02 1.77

G 0.100 BSC 2.54 BSC

H 0.050 BSC 1.27 BSC J 0.008 0.015 0.21 0.38 K 0.110 0.130 2.80 3.30 L 0.295 0.305 7.50 7.74

M 0 10 0 10

S 0.020 0.040 0.51 1.01

MILLIMETERSINCHES

____

SOIC−16WB

CASE 751G−03

ISSUE C

h X 45

SEATING PLANE

NOTES:

1. DIMENSIONS ARE IN MILLIMETERS.

2. INTERPRET DIMENSIONS AND TOLERANCES PER ASME Y14.5M, 1994.

3. DIMENSIONS D AND E DO NOT INLCUDE MOLD PROTRUSION.

4. MAXIMUM MOLD PROTRUSION 0.15 PER SIDE.

5. DIMENSION B DOES NOT INCLUDE DAMBAR PROTRUSION. ALLOWABLE DAMBAR PROTRUSION SHALL BE 0.13 TOTAL IN EXCESS OF THE B DIMENSION AT MAXIMUM MATERIAL CONDITION.

MILLIMETERS

DIM MIN MAX

A 2.35 2.65

A1 0.10 0.25

B 0.35 0.49 C 0.23 0.32 D 10.15 10.45

E 7.40 7.60 e 1.27 BSC

H 10.05 10.55

h 0.25 0.75 L 0.50 0.90 q 0 7

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MC44603A/D