Page 1
SEMICONDUCTOR
TECHNICAL DATA
POWER FACTOR
CONTROLLERS
PIN CONNECTIONS
Order this document by MC34261/D
D SUFFIX
PLASTIC PACKAGE
CASE 751
(SO–8)
8
1
8
1
P SUFFIX
PLASTIC PACKAGE
CASE 626
Voltage Feedback
Input
1
2
3
4
8
7
6
5
(Top View)
Compensation
Multiplier Input
Current Sense
Input
V
CC
Drive Output
Gnd
Zero Current
Detect Input
Device
Operating
Temperature Range
Package
ORDERING INFORMATION
MC34261D
MC34261P
TA = 0° to +70°C
SO–8
Plastic DIP
MC33261D
MC33261P
SO–8
Plastic DIP
TA = –40° to +85°C
1
MOTOROLA ANALOG IC DEVICE DATA
The MC34261/MC33261 are active power factor controllers specifically
designed for use as a preconverter in electronic ballast and in off–line power
converter applications. These integrated circuits feature an internal startup
timer, a one quadrant multiplier for near unity power factor, zero current
detector to ensure critical conduction operation, high gain error amplifier,
trimmed internal bandgap reference, current sensing comparator, and a
totem pole output ideally suited for driving a power MOSFET.
Also included are protective features consisting of input undervoltage
lockout with hysteresis, cycle–by–cycle current limiting, and a latch for single
pulse metering. These devices are available in dual–in–line and surface
mount plastic packages.
• Internal Startup Timer
• One Quadrant Multiplier
• Zero Current Detector
• Trimmed 2% Internal Bandgap Reference
• Totem Pole Output
• Undervoltage Lockout with Hysteresis
• Low Startup and Operating Current
• Pinout Equivalent to the SG3561
• Functional Equivalent to the TDA4817
Simplified Block Diagram
Voltage
Feedback
Input
Multiplier,
Latch,
PWM,
Timer,
&
Logic
V
ref
Error Amp
Multiplier
Undervoltage
Lockout
2.5V
Reference
Zero Current Detector
5
8
6
7
4
3
2
1
Drive Output
Gnd
Zero Current
Detect Input
Multiplier
Input
Compensation
V
CC
Current Sense
Input
Motorola, Inc. 1996 Rev 1
Page 2
MC34261 MC33261
2
MOTOROLA ANALOG IC DEVICE DATA
MAXIMUM RATINGS
Rating Symbol Value Unit
Total Power Supply and Zener Current (ICC + IZ) 30 mA
Output Current, Source or Sink (Note 1) I
O
500 mA
Current Sense, Multiplier, and Voltage Feedback Inputs V
in
–1.0 to 10 V
Zero Current Detect Input
High State Forward Current
Low State Reverse Current
I
in
50
–10
mA
Power Dissipation and Thermal Characteristics
P Suffix, Plastic Package Case 626
Maximum Power Dissipation @ TA = 70°C
Thermal Resistance, Junction–to–Air
D Suffix, Plastic Package Case 626
Maximum Power Dissipation @ TA = 70°C
Thermal Resistance, Junction–to–Air
P
D
R
θJA
P
D
R
θJA
800
100
450
178
mW
°C/W
mW
°C/W
Operating Junction Temperature T
J
+150 °C
Operating Ambient Temperature (Note 3)
MC34261
MC33261
T
A
0 to +70
–40 to +85
°C
Storage Temperature T
stg
–55 to +150 °C
ELECTRICAL CHARACTERISTICS (V
CC
= 12 V, for typical values TA = 25°C, for min/max values TA is the operating ambient
temperature range that applies [Note 3], unless otherwise noted.)
Characteristic
Symbol Min Typ Max Unit
ERROR AMPLIFIER
Voltage Feedback Input Threshold
TA = 25°C
TA = T
low
to T
high
(VCC = 12 V to 28 V)
V
FB
2.465
2.44
2.5 2.535
2.54
V
Line Regulation (VCC = 12 V to 28 V, TA = 25°C) Reg
line
– 1.0 10 mV
Input Bias Current (VFB = 0 V) I
IB
– –0.3 –1.0 µA
Open Loop Voltage Gain A
VOL
65 85 – dB
Gain Bandwidth Product (TA = 25°C) GBW 0.7 1.0 – MHz
Output Source Current (VO = 4.0 V , VFB = 2.3 V) I
Source
0.25 0.5 0.75 mA
Output Voltage Swing
High State (I
Source
= 0.2 mA, VFB = 2.3 V)
Low State (I
Sink
= 0.4 mA, VFB = 2.7 V)
V
OH
V
OL
5.0
–
5.7
2.1
–
2.44
V
MULTIPLIER
Dynamic Input Voltage Range
Multiplier Input (Pin 3)
Compensation (Pin 2)
V
Pin 3
V
Pin 2
0 to 2.5
VFB to
(VFB + 1.0)
0 to 3.5
VFB to
(VFB + 1.5)
–
–
V
Input Bias Current (VFB = 0 V) I
IB
– –0.3 –1.0 µA
Multiplier Gain (V
Pin 3
= 0.5 V , V
Pin 2
= VFB + 1.0 V) (Note 2) K 0.4 0.62 0.8 1/V
ZERO CURRENT DETECTOR
Input Threshold Voltage (Vin Increasing) V
th
1.3 1.6 1.8 V
Hysteresis (Vin Decreasing) V
H
40 110 200 mV
Input Clamp Voltage
High State (I
DET
= 3.0 mA)
Low State (I
DET
= –3.0 mA)
V
IH
V
IL
6.1
0.3
6.7
0.7
–
1.0
V
NOTES: 1. Maximum package power dissipation limits must be observed.
3. T
low
= –40°C for MC34261
3. T
low
= –40°C for MC33261
T
high
= +70°C for MC34261
T
high
= +85°C for MC33261
Pin 4 Threshold Voltage
V
Pin 3(VPin 2
– VFB)
2. K =
Page 3
MC34261 MC33261
3
MOTOROLA ANALOG IC DEVICE DATA
ELECTRICAL CHARACTERISTICS (V
CC
= 12 V, for typical values TA = 25°C, for min/max values TA is the operating ambient
temperature range that applies [Note 3], unless otherwise noted.)
Characteristic
Symbol Min Typ Max Unit
CURRENT SENSE COMPARATOR
Input Bias Current (V
Pin 4
= 0 V) I
IB
– –0.5 –2.0 µA
Input Offset Voltage (V
Pin 2
= 1.1 V , V
Pin 3
= 0 V) V
IO
– 3.5 15 mV
Delay to Output t
PHL (in/out)
– 200 400 ns
DRIVE OUTPUT
Output Voltage (VCC = 12 V)
Low State (I
Sink
= 20 mA)
Low State (I
Sink
= 200 mA)
High State (I
Source
= 20 mA)
High State (I
Source
= 200 mA)
V
OL
V
OH
–
1.8
9.8
7.8
0.3
2.4
10.3
8.3
0.8
3.3
–
8.8
V
Output Voltage (VCC = 30 V)
High State (I
Source
= 20 mA, CL = 15 pF)
V
O(max)
14 16 18
V
Output Voltage Rise T ime (CL = 1.0 nF) t
r
– 50 120 ns
Output Voltage Fall T ime (CL = 1.0 nF) t
f
– 50 120 ns
Output Voltage with UVLO Activated (VCC = 7.0 V , I
Sink
= 1.0 mA) V
OH(UVLO)
– 0.2 0.8 V
RESTART TIMER
Restart Time Delay t
DLY
150 400 – µs
UNDERVOLTAGE LOCKOUT
Startup Threshold (VCC Increasing) V
th
9.2 10.0 10.8 V
Minimum Operating Voltage After Turn–On (VCC Decreasing) V
Shutdown
7.0 8.0 9.0 V
Hysteresis V
H
1.75 2.0 2.5 V
TOTAL DEVICE
Power Supply Current
Startup (VCC = 7.0 V)
Operating
Dynamic Operating (50 kHz, CL = 1.0 nF)
I
CC
–
–
–
0.3
7.1
9.0
0.5
12
20
mA
Power Supply Zener Voltage V
Z
30 36 – V
NOTES: 1. Maximum package power dissipation limits must be observed.
3. T
low
= –40°C for MC34261
3. T
low
= –40°C for MC33261
T
high
= +70°C for MC34261
T
high
= +85°C for MC33261
Pin 4 Threshold Voltage
V
Pin 3(VPin 2
– VFB)
2. K =
, CURRENT SENSE THRESHOLD VOLTAGE (V)
CS
V
1.0 1.5
, CURRENT SENSE THRESHOLD VOLTAGE (V)
VM, MULTIPLIER INPUT VOLTAGE (V)
–0.5 4.0
Figure 1. Current Sense Input Threshold
versus Multiplier Input
Figure 2. Current Sense Input Threshold
versus Multiplier Input
–0.12
VM, MULTIPLIER INPUT VOLTAGE (V)
–0.08 0 0.04 0.08 0.120 0.5 2.0 2.5 3.0 3.5 –0.04
CS
V
0
3.0
–0.5
0.16
–0.02
2.5
2.0
1.5
1.0
0.5
0
0.14
0.12
0.10
0.08
0.06
0.04
0.02
See Figure 2
Page 4
MC34261 MC33261
4
MOTOROLA ANALOG IC DEVICE DATA
Figure 3. Voltage Feedback Input Threshold
Change versus Temperature
0 0.5 1.0 1.5
I
Sink
, OUTPUT SINK CURRENT (mA)
V
sat
, OUTPUT SA TURATION VOLTAGE (V)
Figure 4. Error Amp Open Loop Gain and
Phase versus Frequency
Gain
Phase
A
VOL
, OPEN LOOP VOL TAGE GAIN (dB)
100
80
60
40
20
–20
10
f, FREQUENCY (Hz)
100 1.0 k 10 k 100 k 1.0 M 10 M
0
φ
, EXCESS PHASE ( C)
120
180
150
Figure 5. Error Amp Small Signal
Transient Response
V
FB
, VOLTAGE FEEDBACK THRESHOLD CHANGE (mV)
+4.0
–55
TA, AMBIENT TEMPERATURE (
°
C)
–4.0
–8.0
–12
–16
–25 0 25 50 75 100 125
∆
0
Figure 6. Error Amp Large Signal
Transient Response
Figure 7. Error Amp Output Saturation
versus Sink Current
–55
TA, AMBIENT TEMPERATURE (°C)
–25 0 25 50 75 100 125
Figure 8. Restart Time Delay versus Temperature
t
DLY
, RESTART TIME DELAY ( s)
µ
2.0
°
0
30
60
90
2.55 V
2.5 V
2.45 V
0.5
µ
s/DIV
20 mV/DIV
VCC = 12 V
AV = –1.0
TA = 25
°
C
VCC = 12 V
AV = –1.0
TA = 25
°
C
200 mV/DIV
1.0 µs/DIV
3.0 V
2.5 V
2.0 V
VCC = 12 V
Pins 1 to 2
VCC = 12 V
VO = 3.0 V to 3.5 V
RL = 100 k
TA = 25
°
C
5.0
4.0
3.0
2.0
1.0
0
525
475
425
375
325
275
VCC = 12 V
VFB = 2.7 V
TA = 25
°
C
VCC = 12 V
Page 5
MC34261 MC33261
5
MOTOROLA ANALOG IC DEVICE DATA
Figure 9. Zero Current Detector Input Threshold
Voltage Change versus Temperature
–55 –25 0 25 50 75 100 125
TA, AMBIENT TEMPERATURE (°C)
V
CC
, SUPPLY VOLTAGE (V)
Minimum Operating Threshold
(VCC Decreasing)
Figure 10. Output Saturation Voltage
versus Load Current
Gnd
V
CC
V
sat
, OUTPUT SA TURATION VOLTAGE (V)
0 80 160 240 320
IO, OUTPUT LOAD CURRENT (mA)
Source Saturation
(Load to Ground)
Sink Saturation
(Load to VCC)
VCC = 12 V
80
µ
s Pulsed Load
120 Hz Rate
Figure 11. Drive Output Waveform
V
th
, THRESHOLD VOLTAGE CHANGE (mV)
–55 –25 0 25 50 75 100 125
TA, AMBIENT TEMPERATURE (
°
C)
∆
VCC = 12 V
Upper Threshold
(Vin Increasing)
Lower Threshold
(Vin Decreasing)
Figure 12. Drive Output Cross Conduction
Figure 13. Supply Current versus Supply Voltage
Figure 14. Undervoltage Lockout Thresholds
versus Temperature
I
CC
, SUPPLY CURRENT (mA)
10 20 30 40
VCC, SUPPLY VOLTAGE (V)
VFB = 0 V
Current Sense = 0 V
Multiplier = 0 V
CL = 1.0 nF
f = 50 kHz
TA = 25
°
C
VCC = 12 V
CL = 1.0 nF
TA = 25
°
C
VCC = 12 V
CL = 15 pF
TA = 25
°
C
5.0 V/DIV
90
%
100 mA/DIV
10
%
100 ns/DIV 100 ns/DIV
I
CC
, SUPPLY CURRENT V
O
, OUTPUT VOL TAGE
12
11
10
9.0
8.0
6.0
7.0
0
–2.0
–4.0
–6.0
2.0
0
4.0
40
20
0
–20
–40
16
12
8.0
4.0
0
0
Startup Threshold
(VCC Increasing)
Page 6
MC34261 MC33261
6
MOTOROLA ANALOG IC DEVICE DATA
FUNCTIONAL DESCRIPTION
Introduction
Most electronic ballasts and switching power supplies use
a bridge rectifier and a filter capacitor to derive raw dc voltage
from the utility ac line. This simple rectifying circuit draws
power from the line when the instantaneous ac voltage
exceeds the capacitor’s voltage. This occurs near the line
voltage peak and results in a high charge current spike.
Since power is only taken near the line voltage peaks, the
resulting spikes of current are extremely nonsinusoidal with a
high content of harmonics. This results in a poor power factor
condition where the apparent input power is much higher
than the real power.
The MC34261, MC33261 are high performance, critical
conduction, current mode power factor controllers
specifically designed for use in off–line active preconverters.
These devices provide the necessary features required to
significantly enhance poor power factor loads by keeping the
ac line current sinusoidal and in phase with the line voltage.
With proper control of the preconverter, almost any complex
load can be made to appear resistive to the ac line, thus
significantly reducing the harmonic current content.
Operating Description
The MC34261, MC33261 contains many of the building
blocks and protection features that are employed in modern
high performance current mode power supply controllers.
There are, however, two areas where there is a major
difference when compared to popular devices such as the
UC3842 series. Referring to the block diagram in Figure 15,
note that a multiplier has been added to the current sense
loop and that this device does not contain an oscillator. A
description of each of the functional blocks is given below.
Error Amplifier
A fully compensated Error Amplifier with access to the
inverting input and output is provided. It features a typical dc
voltage gain of 85 dB, and a unity gain bandwidth of 1.0 MHz
with 58° of phase margin (Figure 4). The noninverting input is
internally biased at 2.5 V ±2.0% and is not pinned out. The
output voltage of the power factor converter is typically
divided down and monitored by the inverting input. The
maximum input bias current is –1.0 µA which can cause an
output voltage error that is equal to the product of the input
bias current and the value of the upper divider resistor R2.
The Error Amp Output is internally connected to the Multiplier
and is pinned out (Pin 2) for external loop compensation.
Typically, the bandwidth is set below 20 Hz, so that the Error
Amp output voltage is relatively constant over a given ac line
cycle. The output stage consists of a 500 µA current source
pull–up with a Darlington transistor pull–down. It is capable of
swinging from 2.1 V to 5.7 V, assuring that the Multiplier can
be driven over its entire dynamic range.
Multiplier
A single quadrant, two input multiplier is the critical
element that enables this device to control power factor. The
ac haversines are monitored at Pin 3 with respect to ground
while the Error Amp output at Pin 2 is monitored with respect
to the Voltage Feedback Input threshold. A graph of the
Multiplier transfer curve is shown in Figure 1. Note that both
inputs are extremely linear over a wide dynamic range, 0 V to
3.2 V for the Multiplier input (Pin 3), and 2.5 V to 4.0 V for the
Error Amp output (Pin 2). The Multiplier output controls the
Current Sense Comparator threshold (Pin 4) as the ac
voltage traverses sinusoidally from zero to peak line. This
has the effect of forcing the MOSFET peak current to track
the input line voltage, thus making the preconverter load
appear to be resistive.
Pin 4 Threshold ≈ 0.62(V
Pin 2
– VFB)V
Pin 3
Zero Current Detector
The MC34261 operates as a critical conduction current
mode controller, whereby output switch conduction is
initiated by the Zero Current Detector and terminated when
the peak inductor current reaches the threshold level
established by the Multiplier output. The Zero Current
Detector initiates the next on–time by setting the RS Latch at
the instant the inductor current reaches zero. This critical
conduction mode of operation has two significant benefits.
First, since the MOSFET cannot turn on until the inductor
current reaches zero, the output rectifier’s reverse recovery
time becomes less critical allowing the use of an inexpensive
rectifier. Second, since there are no deadtime gaps between
cycles, the ac line current is continuous thus limiting the peak
switch to twice the average input current.
The Zero Current Detector indirectly senses the inductor
current by monitoring when the auxiliary winding voltage falls
below 1.6 V . To prevent false tripping, 1 10 mV of hysteresis is
provided. The Zero Current Detector input is internally
protected by two clamps. The upper 6.7 V clamp prevents
input overvoltage breakdown while the lower 0.7 V clamp
prevents substrate injection. Device destruction can result if
this input is shorted to ground. An external resistor must be
used in series with the auxiliary winding to limit the current
through the clamps.
Current Sense Comparator and RS Latch
The Current Sense Comparator RS Latch configuration
ensures that only a single pulse appears at the Drive Output
during a given cycle. The inductor current is converted to a
voltage by inserting a ground referenced sense resistor R9 in
series with the source of output switch Q1. This voltage is
monitored by the Current Sense Input and compared to the
Multiplier output voltage. The peak inductor current is
controlled by the threshold voltage of Pin 4 where:
Pin 4 Threshold
R
9
Ipk =
With the component values shown in Figure 16, the
Current Sense Comparator threshold, at the peak of the
haversine varies from 1.1 V at 90 Vac to 100 mV at 268 Vac.
The Current Sense Input to Drive Output propagation delay is
typically 200 ns.
Page 7
MC34261 MC33261
7
MOTOROLA ANALOG IC DEVICE DATA
Timer
A watchdog timer function was added to the IC to eliminate
the need for an external oscillator when used in stand alone
applications. The Timer provides a means to automatically
start or restart the preconverter if the Drive Output has been
off for more than 400 µs after the inductor current reaches
zero.
Undervoltage Lockout
An Undervoltage Lockout comparator guarantees that the
IC is fully functional before enabling the output stage. The
positive power supply terminal (VCC) is monitored by the
UVLO comparator with the upper threshold set at 10 V and
the lower threshold at 8.0 V (Figure 14). In the standby mode,
with VCC at 7.0 V, the required supply current is less than
0.5 mA (Figure 13). This hysteresis and low startup current
allow the implementation of efficient bootstrap startup
techniques, making these devices ideally suited for wide
input range off line preconverter applications. An internal 36
V clamp has been added from VCC to ground to protect the IC
and capacitor C5 from an overvoltage condition. This feature
is desirable if external circuitry is used to delay the startup of
the preconverter.
Output
The MC34261/MC33261 contain a single totem pole
output stage specifically designed for direct drive of power
MOSFETs. The Drive Output is capable of up to ±500 mA
peak current with a typical rise and fall time of 50 ns with a
1.0 nF load. Additional internal circuitry has been added to
keep the Drive Output in a sinking mode whenever the
Undervoltage Lockout is active. This characteristic
eliminates the need for an external gate pull–down resistor.
The totem pole output has been optimized to minimize cross
conduction current during high speed operation. The addition
of two 10 Ω resistors, one in series with the source output
transistor and one in series with the sink output transistor,
reduces the cross conduction current, as shown in Figure 12.
A 16 V clamp has been incorporated into the output stage to
limit the high state VOH. This prevents rupture of the
MOSFET gate when V
CC
exceeds 20 V.
Table 1. Design Equations
Notes Calculation Formula
Calculate the maximum required output power. Required Converter Output Power PO = VO I
O
Calculated at the minimum required ac line for
regulation. Let the efficiency n = 0.95.
Peak Inductor Current
I
L(pk)
=
22 P
O
ηVac
(LL)
Let the switching cycle t = 20 µs.
Inductance
L =
2t
2
VO Vac
(LL) IL(pk)
V
O
– Vac Vac
2
ǒǓ
In theory the on–time ton is constant. In practice t
on
tends to increase at the ac line zero crossings due to
the charge on capacitor C6.
Switch On–Time
η Vac
2
ton =
2 PO L
The off–time t
off
is greatest at peak ac line and
approaches zero at the ac line zero crossings.
Theta (θ) represents the angle of
the ac line voltage.
Switch Off–Time
V
O
– 1
t
off
=
2 Vac
Sin θ
t
on
The minimum switching frequency occurs at peak ac
line and increases as t
off
decreases.
Switching Frequency
f =
ton + t
off
1
Set the current sense threshold VCS to 1.0 V for
universal input (85 Vac to 265 Vac) operation and
to 0.5 V for fixed input (92 Vac to 138 Vac, or
184 to 276 Vac) operation.
Peak Switch Current
R9 =
I
L(pk)
V
CS
Set the multiplier input voltage VM to 3.0 V at high
line. Empirically adjust VM for the lowest distortion
over the ac line range while guaranteeing startup at
minimum line.
Multiplier Input Voltage
+ 1
Vac
Ǔǒ
VM =
R
7
2
R
3
The IIB R1 error term can be minimized with a divider
current in excess of 100 µA.
Converter Output Voltage
– IIB R
2
Ǔǒ
VO = V
ref
R
2
+ 1
R
1
The bandwidth is typically set to 20 Hz for minimum
output ripple over the ac line haversine.
Error Amplifier Bandwidth
BW =
R1 R
2
1
R1 + R
2
2 π C
1
The following converter characteristics must be chosen:
V
O
I
O
Vac
Vac
(LL)
– Desired output voltage – AC RMS line voltage
– Desired output current – AC RMS low line voltage
Page 8
MC34261 MC33261
8
MOTOROLA ANALOG IC DEVICE DATA
+
+
100
C
4
100
C
5
10V
MTP
8N50E
Q
1
2.2M
R
7
Figure 15. 80 W Power Factor Controller
+
+
+
+
+
RFI
Filter
R
6
R
4
C
6
D
4
D
3
D
2
D
1
0.01
C
2
330
1.0nF
C
3
0.5mA
6.7V
Zero Current
Detector
V
O
T
UVLO
V
ref
Error Amp
Current Sense
Comparator
RS
Latch
1.2V
1.6V
36V
2.5V
Reference
16V
10
Drive
Output
10
Timer
Multiplier
Delay
92 to
138 Vac
1
7.5k
R
3
22k
R
5
10
100k
R
8
1N4934
D
6
11k
R
1
1.0M
R
2
0.1
R
9
4
7
8
5
3
6
0.68
C
1
2
1
MUR130
D
5
R
230V/0.35A
Power Factor Controller Test Data
AC Line Input DC Output
Current Harmonic Distortion (%)
V
rms
P
in
PF THD 2357V
O(pp)
V
O
I
O
P
O
n(%)
90 85.6 –0.998 2.4 0.11 0.52 1.3 0.67 10.0 230 0.350 80.5 94.0
100 85.1 –0.997 5.0 0.13 1.7 2.4 1.4 10.1 230 0.350 80.5 94.6
110 84.8 –0.997 5.3 0.12 2.5 2.6 1.5 10.2 230 0.350 80.5 94.9
120 84.5 –0.997 5.8 0.12 3.2 2.7 1.4 10.2 230 0.350 80.5 95.3
130 84.2 –0.996 6.6 0.12 4.0 2.8 1.5 10.2 230 0.350 80.5 95.6
138 84.1 –0.995 7.2 0.13 4.5 3.0 1.6 10.2 230 0.350 80.5 95.7
= Coilcraft N2881–A
Primary: 62 turns of # 22 AWG
Secondary: 5 turns of # 22 AWG
Core: Coilcraft PT2510, EE 25
Gap: 0.072″ total for a primary inductance of 320 µH
= AAVID Engineering Inc. 5903B, or 5930B
T
Heatsink
This data was taken with the test set–up shown in Figure 17.
Page 9
MC34261 MC33261
9
MOTOROLA ANALOG IC DEVICE DATA
+
+
1.6V
Timer R
180
C
4
100
C
5
10V
MTW
14N50E
Q
1
1.3M
R
7
Figure 16. 175 W Universal Input Power Factor Controller
+
+
+
+
+
RFI
Filter
R
6
R
4
C
6
D
4
D
3
D
2
D
1
0.01
C
2
330
1.0nF
C
3
0.5mA
6.7V
Zero Current
Detector
V
O
T
UVLO
V
ref
Error Amp
Current Sense
Comparator
RS
Latch
1.2V
36V
2.5V
Reference
16V
10
Drive
Output
10
Multiplier
Delay
85 to 265
Vac
1
12k
R
3
22k
R
5
10
100k
R
8
1N4934
D
6
10k
R
1
1.6M
R
2
0.1
R
9
4
7
8
5
3
6
0.68
C
1
2
1
MUR460
D
5
400V/0.44A
Power Factor Controller Test Data
AC Line Input DC Output
Current Harmonic Distortion (%)
V
rms
P
in
PF THD 2357V
O(pp)
V
O
I
O
P
O
n(%)
90 187.5 –0.998 2.0 0.10 0.98 0.90 0.78 8.0 400.7 0.436 174.7 93.2
120 184.6 –0.997 1.8 0.09 1.3 1.3 0.93 8.0 400.7 0.436 174.7 94.6
138 183.6 –0.997 2.3 0.05 1.6 1.5 1.0 8.0 400.7 0.436 174.7 95.2
180 181.0 –0.995 4.3 0.16 2.5 2.0 1.2 8.0 400.6 0.436 174.7 95.6
240 179.3 –0.993 6.0 0.08 3.7 2.7 1.4 8.0 400.6 0.436 174.7 97.4
268 178.6 –0.992 6.7 0.16 2.8 3.7 1.7 8.0 400.6 0.436 174.7 97.8
= Coilcraft N2880–A
Primary: 78 turns of # 16 AWG
Secondary: 6 turns of # 18 AWG
Core: Coilcraft PT4215, EE 42–15
Gap: 0.104″ total for a primary inductance of 870 µH
= AAVID Engineering Inc. 5903B
T
Heatsink
This data was taken with the test set–up shown in Figure 17.
Page 10
MC34261 MC33261
10
MOTOROLA ANALOG IC DEVICE DATA
Figure 17. Power Factor Test Set–Up
0.005
1.0
0.005
HARMFREQ
11
LO
0.1
OI
T
0 to 270 Vac
Output Power Factor
Controller Circuit
Earth
Line
Neutral
115 Vac
Input
RFI Filter
Autoformer
2X Step–Up
Isolation
Transformer
LO
HIHI
VA
AinstAcfVcf
ArmsVrmsPFVAW
1397
53210
Voltech
AC POWER ANALYZER
PM 1000
An RFI filter is required for best performance when connecting the preconverter directly to the AC line. Commercially available two stage filters
such as the Delta Electronics 03DPCG5 work excellent. The simple single stage test filter shown above can easily be constructed with a common
mode transformer. Transformer (T) is a Coilcraft CMT3–28–2 with 28 mH minimum inductance and a 2.0 A maximum current rating.
+
0.5 mA
2
1
Figure 18. Soft–Start Circuit
+
t
Soft–Start
≈
9000C in µF
1.0M
To V
CC
C
To V
O
Startup overshoot can be eliminated with the
addition of a Soft–Start circuit.
Figure 19. Error Amp Compensation
2
C
1
Error Amp
+
10µA
R
1
1
6
R
2
Page 11
MC34261 MC33261
11
MOTOROLA ANALOG IC DEVICE DATA
Figure 20. Printed Circuit Board and Component Layout
(Circuits of Figures 15 and 16)
Page 12
MC34261 MC33261
12
MOTOROLA ANALOG IC DEVICE DATA
OUTLINE DIMENSIONS
P SUFFIX
PLASTIC PACKAGE
CASE 626–05
ISSUE K
D SUFFIX
PLASTIC PACKAGE
CASE 751–05
(SO–8)
ISSUE N
NOTES:
1. DIMENSION L TO CENTER OF LEAD WHEN
FORMED PARALLEL.
2. PACKAGE CONTOUR OPTIONAL (ROUND OR
SQUARE CORNERS).
3. DIMENSIONING AND TOLERANCING PER ANSI
Y14.5M, 1982.
14
58
F
NOTE 2
–A–
–B–
–T–
SEATING
PLANE
H
J
G
D
K
N
C
L
M
M
A
M
0.13 (0.005) B
M
T
DIM MIN MAX MIN MAX
INCHESMILLIMETERS
A 9.40 10.16 0.370 0.400
B 6.10 6.60 0.240 0.260
C 3.94 4.45 0.155 0.175
D 0.38 0.51 0.015 0.020
F 1.02 1.78 0.040 0.070
G 2.54 BSC 0.100 BSC
H 0.76 1.27 0.030 0.050
J 0.20 0.30 0.008 0.012
K 2.92 3.43 0.115 0.135
L 7.62 BSC 0.300 BSC
M ––– 10 ––– 10
N 0.76 1.01 0.030 0.040
__
NOTES:
1. DIMENSIONING AND TOLERANCING PER
ANSI Y14.5M, 1982.
2. CONTROLLING DIMENSION: MILLIMETER.
3. DIMENSIONS A AND B DO NOT INCLUDE
MOLD PROTRUSION.
4. MAXIMUM MOLD PROTRUSION 0.15 (0.006)
PER SIDE.
5. DIMENSION D DOES NOT INCLUDE DAMBAR
PROTRUSION. ALLOWABLE DAMBAR
PROTRUSION SHALL BE 0.127 (0.005) TOTAL
IN EXCESS OF THE D DIMENSION AT
MAXIMUM MATERIAL CONDITION.
SEATING
PLANE
14
58
C
K
4X P
A0.25 (0.010)MTB
SS
0.25 (0.010)MB
M
8X D
R
M
J
X 45
_
_
F
–A–
–B–
–T–
DIM MIN MAX MIN MAX
INCHESMILLIMETERS
A 4.80 5.00 0.189 0.196
B 3.80 4.00 0.150 0.157
C 1.35 1.75 0.054 0.068
D 0.35 0.49 0.014 0.019
F 0.40 1.25 0.016 0.049
G 1.27 BSC 0.050 BSC
J 0.18 0.25 0.007 0.009
K 0.10 0.25 0.004 0.009
M 0 7 0 7
P 5.80 6.20 0.229 0.244
R 0.25 0.50 0.010 0.019
____
G
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the suitability of its products for any particular purpose, nor does Motorola assume any liability arising out of the application or use of any product or circuit, and
specifically disclaims any and all liability, including without limitation consequential or incidental damages. “T ypical” parameters which may be provided in Motorola
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