Datasheet MC1496P1, MC1496BP, MC1496D, MC1496DR2, MC1496P Datasheet (Motorola)

 


These devices were designed for use where the output voltage is a
product of an input voltage (signal) and a switching function (carrier). Typical
applications include suppressed carrier and amplitude modulation,
synchronous detection, FM detection, phase detection, and chopper
applications. See Motorola Application Note AN531 for additional design
information.

• Excellent Carrier Suppression –65 dB typ @ 0.5 MHz

Excellent Carrier Suppression –50 dB typ @ 10 MHz

• Adjustable Gain and Signal Handling

• Balanced Inputs and Outputs

• High Common Mode Rejection –85 dB typical

This device contains 8 active transistors.

Order this document by MC1496/D

 

BALANCED

MODULATORS/DEMODULA T ORS

SEMICONDUCTOR

TECHNICAL DATA

D SUFFIX

PLASTIC PACKAGE

CASE 751A

14

1

P SUFFIX

PLASTIC PACKAGE

CASE 646

(SO–14)

14

1

0

20

Log Scale Id

40
60

IC = 500 kHz, IS = 1.0 kHz

499 kHz 500 kHz 501 kHz

IC = 500 kHz
IS = 1.0 kHz

Figure 1. Suppressed

Carrier Output

Waveform

Figure 2. Suppressed

Carrier Spectrum

PIN CONNECTIONS

Signal Input
Gain Adjust
Gain Adjust
Signal Input

Bias

Output

N/C

1
2
3
4
5
6
7

14

V

EE

13

N/C

12

Output

11

N/C

10

Carrier Input

9

N/C

8

Input Carrier

ORDERING INFORMATION

Operating

Device

MC1496D
MC1496P
MC1496BP Plastic DIPTA = –40°C to +125°C

Temperature Range

TA = 0°C to +70°C

Package

SO–14

Plastic DIP

Figure 4. Amplitude–Modulation Spectrum

10

8.0

IC = 500 kHz
IS = 1.0 kHz

IC = 500 kHz
IS = 1.0 kHz

MOTOROLA ANALOG IC DEVICE DATA

Figure 3. Amplitude

Modulation Output

Waveform

6.0

4.0

Linear Scale

2.0

0

 Motorola, Inc. 1996 Rev 4

499 kHz 500 kHz 501 kHz

1

MC1496, B

MAXIMUM RATINGS

Applied Voltage

(V6 – V8, V10 – V1, V12 – V8, V12 – V10, V8 – V4,

V8 – V1, V10 – V4, V6 – V10, V2 – V5, V3 – V5)

Differential Input Signal V8 – V10

Maximum Bias Current I
Thermal Resistance, Junction–to–Air

Plastic Dual In–Line Package
Operating Temperature Range T
Storage Temperature Range T

NOTE: ESD data available upon request.

ELECTRICAL CHARACTERISTICS (V

all input and output characteristics are single–ended, unless otherwise noted.)

Carrier Feedthrough

VC = 60 mVrms sine wave and

offset adjusted to zero

VC = 300 mVpp square wave:

offset adjusted to zero
offset not adjusted

Carrier Suppression

fS = 10 kHz, 300 mVrms

fC = 500 kHz, 60 mVrms sine wave
fC = 10 MHz, 60 mVrms sine wave

Transadmittance Bandwidth (Magnitude) (RL = 50 Ω)

Carrier Input Port, VC = 60 mVrms sine wave

fS = 1.0 kHz, 300 mVrms sine wave

Signal Input Port, VS = 300 mVrms sine wave

|VC| = 0.5 Vdc
Signal Gain (VS = 100 mVrms, f = 1.0 kHz; |VC|= 0.5 Vdc) 10 3 A
Single–Ended Input Impedance, Signal Port, f = 5.0 MHz

Parallel Input Resistance
Parallel Input Capacitance

Single–Ended Output Impedance, f = 10 MHz

Parallel Output Resistance
Parallel Output Capacitance

Input Bias Current

I1)I4

IbS+

Input Offset Current

I

Average Temperature Coefficient of Input Offset Current

(TA = –55°C to +125°C)
Output Offset Current (I6–I9) 7 – Ioo – 14 80 µA
Average Temperature Coefficient of Output Offset Current

(TA = –55°C to +125°C)
Common–Mode Input Swing, Signal Port, fS = 1.0 kHz 9 4 CMV – 5.0 – Vpp
Common–Mode Gain, Signal Port, fS = 1.0 kHz, |VC|= 0.5 Vdc 9 – ACM – –85 – dB
Common–Mode Quiescent Output V oltage (Pin 6 or Pin 9) 10 – V
Differential Output Voltage Swing Capability 10 – V
Power Supply Current I6 +I12

Power Supply Current I14

DC Power Dissipation 7 5 P

= I1–I4; I

ioS

2

(TA = 25°C, unless otherwise noted.)

Rating

Characteristic

;IbC+

ioC

I8)I10

2

= I8–I10

Symbol Value Unit

∆V 30 Vdc

V4 – V1

5

R

θJA

A

stg

= 12 Vdc, VEE = –8.0 Vdc, I5 = 1.0 mAdc, RL = 3.9 kΩ, Re = 1.0 kΩ, TA = T

CC

fC = 1.0 kHz
fC = 10 MHz

fC = 1.0 kHz
fC = 1.0 kHz

+5.0

±(5+I5Re)

10 mA

100 °C/W

0 to +70

–65 to +150

Fig. Note Symbol Min Typ Max Unit

5 1 V

5 2 V

8 8 BW

6 –

6 –

7 –

7 –

7 – TC

7 – TC

7 6 I

Vdc

°C
°C

I

I

CFT

CS

3dB

VS

r

ip

c

ip

r

op

c

oo

I

bS

I

bC

ioS

ioC

out
out

CC

I

EE

D



Iio

Ioo

–

40

–

140

–

0.04

–

20

40

2.5 3.5 – V/V



 – 2.0 – nA/°C

 – 90 – nA/°C

65

–

50

–

300

–

80

–

200

–

2.0

–

40

–

5.0

–

12

–

12

–

0.7

–

0.7

– 8.0 – Vpp
– 8.0 – Vpp
–

2.0

–

3.0

– 33 – mW

–
–

0.4

200

–
–

–

–

–
–

–
–

30
30

7.0

7.0

4.0

5.0

low

to T

mVrms

high

µVrms

dB

k

MHz

kΩ
pF

kΩ
pF

µA

µA

mAdc

,

2

MOTOROLA ANALOG IC DEVICE DATA

MC1496, B

GENERAL OPERATING INFORMATION

Carrier Feedthrough

Carrier feedthrough is defined as the output voltage at
carrier frequency with only the carrier applied (signal
voltage = 0).

Carrier null is achieved by balancing the currents in the
differential amplifier by means of a bias trim potentiometer
(R1 of Figure 5).

Carrier Suppression

Carrier suppression is defined as the ratio of each
sideband output to carrier output for the carrier and signal
voltage levels specified.

Carrier suppression is very dependent on carrier input
level, as shown in Figure 22. A low value of the carrier does
not fully switch the upper switching devices, and results in
lower signal gain, hence lower carrier suppression. A higher
than optimum carrier level results in unnecessary device and
circuit carrier feedthrough, which again degenerates the
suppression figure. The MC1496 has been characterized
with a 60 mVrms sinewave carrier input signal. This level
provides optimum carrier suppression at carrier frequencies
in the vicinity of 500 kHz, and is generally recommended for
balanced modulator applications.

Carrier feedthrough is independent of signal level, VS.
Thus carrier suppression can be maximized by operating
with large signal levels. However, a linear operating mode
must be maintained in the signal–input transistor pair – or
harmonics of the modulating signal will be generated and
appear in the device output as spurious sidebands of the
suppressed carrier. This requirement places an upper limit on
input–signal amplitude (see Figure 20). Note also that an
optimum carrier level is recommended in Figure 22 for good
carrier suppression and minimum spurious sideband
generation.

At higher frequencies circuit layout is very important in
order to minimize carrier feedthrough. Shielding may be
necessary in order to prevent capacitive coupling between
the carrier input leads and the output leads.

Signal Gain and Maximum Input Level

Signal gain (single–ended) at low frequencies is defined
as the voltage gain,

AVS+

A constant dc potential is applied to the carrier input terminals
to fully switch two of the upper transistors “on” and two
transistors “off” (VC = 0.5 Vdc). This in effect forms a cascode
differential amplifier.

Linear operation requires that the signal input be below a
critical value determined by RE and the bias current I5.

Note that in the test circuit of Figure 10, VS corresponds to a
maximum value of 1.0 V peak.

Common Mode Swing

The common–mode swing is the voltage which may be
applied to both bases of the signal differential amplifier,
without saturating the current sources or without saturating
the differential amplifier itself by swinging it into the upper

V
V

R

o
S

VS p I5 RE (Volts peak)

+

Re)

L

2r

e

where re+

26 mV
I5(mA)

switching devices. This swing is variable depending on the
particular circuit and biasing conditions chosen.

Power Dissipation

Power dissipation, PD, within the integrated circuit package
should be calculated as the summation of the voltage–current
products at each port, i.e. assuming V12 = V6, I5 = I6 = I12
and ignoring base current, PD = 2 I5 (V6 – V14) + I5)
V5 – V14 where subscripts refer to pin numbers.

Design Equations

The following is a partial list of design equations needed to
operate the circuit with other supply voltages and input
conditions.

A. Operating Current

The internal bias currents are set by the conditions at Pin 5.
Assume:

I5 = I6 = I12,
IBtt

IC for all transistors

then :

V

*

*

R5

+

The MC1496 has been characterized for the condition
I5 = 1.0 mA and is the generally recommended value.

B. Common–Mode Quiescent Output Voltage

Biasing

The MC1496 requires three dc bias voltage levels which
must be set externally. Guidelines for setting up these three
levels include maintaining at least 2.0 V collector–base bias
on all transistors while not exceeding the voltages given in
the absolute maximum rating table;

The foregoing conditions are based on the following
approximations:

Bias currents flowing into Pins 1, 4, 8 and 10 are transistor
base currents and can normally be neglected if external bias
dividers are designed to carry 1.0 mA or more.

Transadmittance Bandwidth

Carrier transadmittance bandwidth is the 3.0 dB bandwidth
of the device forward transadmittance as defined by:

Signal transadmittance bandwidth is the 3.0 dB bandwidth
of the device forward transadmittance as defined by:

f

*

500

I5

30 Vdc w [(V6, V12) – (V8, V10)] w2 Vdc
30 Vdc w [(V8, V10) – (V1, V4)] w2.7 Vdc
30 Vdc w [(V1, V4) – (V5)] w2.7 Vdc

V6 = V12, V8 = V10, V1 = V4

+

g

21C

io(signal)

+

g

21S

vs(signal)

where: R5 is the resistor between

W

where: Pin 5 and ground
where: φ = 0.75 at TA = +25°C

V6 = V12 = V+ – I5 R

io(each sideband)

vs(signal)

Vc+



L

Vo+



0.5 Vdc, Vo+

0

0

MOTOROLA ANALOG IC DEVICE DATA

3

MC1496, B

Coupling and Bypass Capacitors

Capacitors C1 and C2 (Figure 5) should be selected for a

reactance of less than 5.0 Ω at the carrier frequency.

Output Signal

The output signal is taken from Pins 6 and 12 either
balanced or single–ended. Figure 1 1 shows the output levels
of each of the two output sidebands resulting from variations
in both the carrier and modulating signal inputs with a
single–ended output connection.

Negative Supply

VEE should be dc only. The insertion of an RF choke in
series with VEE can enhance the stability of the internal
current sources.

TEST CIRCUITS

Figure 5. Carrier Rejection and Suppression

V

CC

Carrier

Input

V

C

V

S

Modulating

Signal Input

0.1

C

2

µ

10 k

1.0 k

F

R1

51

50 k

Carrier Null

0.1

C1

µ

1.0 k
R

e

F

515110 k

2

8

10

1
4

–8.0 Vdc

V

EE

1.0 k

MC1496

14 5

I5

I10

–

V

3.9 k

3

6.8 k

R

6

12

12 Vdc

L

R

3.9 k

I6

I9

Signal Port Stability

Under certain values of driving source impedance,
oscillation may occur. In this event, an RC suppression
network should be connected directly to each input using
short leads. This will reduce the Q of the source–tuned
circuits that cause the oscillation.

Signal Input

(Pins 1 and 4)

510

An alternate method for low–frequency applications is to
insert a 1.0 kΩ resistor in series with the input (Pins 1, 4). In
this case input current drift may cause serious degradation of
carrier suppression.

Figure 6. Input–Output Impedance

Re = 1.0 k

L

+V

–V

0.5 V

Z

o
o

in

NOTE: Shielding of input and output leads may be needed

to properly perform these tests.

2

8

–

+

10

MC1496

1

4

–8.0 Vdc

3

6
12

14 5

6.8 k

Z

+V

out
–V

10 pF

o
o

Figure 7. Bias and Offset Currents

V

CC

12 Vdc

Re = 1.0 k

2

8

10

MC1496

1
4

–8.0 Vdc

V

EE

14 5

I10

3

6
12

6.8 k

2.0 k

I6
I9

Carrier

Input

Modulating

Signal Input

1.0 k

1.0 k
I7

I8
I1
I4

4

Figure 8. Transconductance Bandwidth

1.0 k

51

µ

F

0.1

V

C

V

S

10 k

50 k

Carrier Null

0.1

51

µ

F

1.0 k
R

1.0 k

23

8

10

MC1496

1
4

14

5110 k

–

V

–8.0 Vdc

V

EE

MOTOROLA ANALOG IC DEVICE DATA

e

6

12

5

6.8 k

V

CC

12 Vdc

2.0 k

50 50

+V

0.01

–V

µ

F

o
o

V

1.0 k

S

MC1496, B

Figure 9. Common Mode Gain Figure 10. Signal Gain and Output Swing

V

CC

50

1.0 k

0.5 V
+

12 Vdc

–

10

Re = 1.0 k

2

8

1

MC1496

4

14 5

–8.0 Vdc

V

EE

3.9 k

3

6

12

6.8 k
A

CM

+

3.9 k

20log

+V

–V

o

V

o



Vo

V

S

S

50

1.0 k

1.0 k

0.5 V
+

–

10

8

1
4

–8.0 Vdc

TYPICAL CHARACTERISTICS

Typical characteristics were obtained with circuit shown in Figure 5, fC = 500 kHz (sine wave),

VC = 60 mVrms, fS = 1.0 kHz, VS = 300 mVrms, TA = 25°C, unless otherwise noted.

Re = 1.0 k

2

MC1496

14 5

I5 =

1.0 mA

V

EE

3.9 k

3

6

12

6.8 k

12 Vdc

V

CC

3.9 k

+V
–V

o

o

2.0

1.6

1.2

0.8

0.4

O

V , OUTPUT AMPLITUDE OF EACH SIDEBAND (Vrms)

5.0

4.0

3.0

Figure 11. Sideband Output versus

Carrier Levels

Signal Input = 600 mV

400 mV
300 mV

200 mV
100 mV

0

0

VC, CARRIER LEVEL (mVrms)

10050 150

Figure 13. Signal–Port Parallel–Equivalent

Input Capacitance versus Frequency

200

Figure 12. Signal–Port Parallel–Equivalent

Input Resistance versus Frequency

1.0 M

)r , PARALLEL OUTPUT RESISTANCE (k

Ω

500

100

50

10

5.0

ip

1.0

r , PARALLEL INPUT RESISTANCE (k

1.0

+r

ip

–r

5.0 100

10

f, FREQUENCY (MHz)

Figure 14. Single–Ended Output Impedance

versus Frequency

140

)

Ω

120
100

r

80

op

ip

50

14
12

10

8.0

2.0

1.0

ip

c , PARALLEL INPUT CAPACITANCE (pF)

0

1.0

5.0

MOTOROLA ANALOG IC DEVICE DATA

60
40
20

0

5020

100102.0

op

0

1.0

c

op

f, FREQUENCY (MHz)f, FREQUENCY (MHz)

6.0

4.0

2.0
op

c , PARALLEL OUTPUT CAPACITANCE (pF)

0

10010

5

MC1496, B

TYPICAL CHARACTERISTICS (continued)

Typical characteristics were obtained with circuit shown in Figure 5, fC = 500 kHz (sine wave),

VC = 60 mVrms, fS = 1.0 kHz, VS = 300 mVrms, TA = 25°C, unless otherwise noted.

1.0

0.9

0.8

0.7

0.6

0.5

0.4

0.3

0.2

21, TRANSADMITT ANCE (mmho)

γ

0.1

20

10

–10

–20

S

V

A , SINGLE-ENDED VOLTAGE GAIN (dB)

–30

Figure 15. Sideband and Signal Port

Transadmittances versus Frequency

Signal Port

Side Band

Sideband Transadmittance

I

(Each Sideband)

out

g21+

g21+

0

0.1

Vin(Signal)

Signal Port Transadmittance

I

out

V

+

out



V

in

fC, CARRIER FREQUENCY (MHz)

V

+

0

out



0|VC|+0.5 Vdc

10

1001.0

Figure 17. Signal–Port Frequency Response

RL = 3.9 k
Re = 500

RL = 3.9 k (Standard

0

Re = 1.0 k Test Circuit)

|VC| = 0.5 Vdc

0.1 1.0 10 1000.01

RL = 3.9 k
Re = 2.0 k

RL = 500
Re = 1.0 k

R

AV+

L

R

)

2r

e

e

f, FREQUENCY (MHz)

Ω

Figure 16. Carrier Suppression

versus T emperature

0

10
20

MC1496

TA, AMBIENT TEMPERATURE

°

(

(70°C)

100 125 150 175

7550250–25

C)

1000

30
40
50

CS

60

V , CARRIER SUPPRESION (dB)

70

–75 –50

Figure 18. Carrier Suppression

versus Frequency

0

Ω

10

20
30
40
50

CARRIER SIDEBAND (dB)

60
70

SUPPRESSION BELOW EACH FUNDAMENTAL

2f

C

f

C

fC, CARRIER FREQUENCY (MHz)

3f

C

505.00.05 0.1 0.5 1.0 10

CFT

V , CARRIER OUTPUT VOL TAGE (mVrms)

6

10

1.0

0.1

0.01

Figure 19. Carrier Feedthrough

versus Frequency

1.0 5.00.05 0.1 0.5

fC, CARRIER FREQUENCY (MHz)

Figure 20. Sideband Harmonic Suppression

versus Input Signal Level

0

10
20

30
40
50
60

CARRIER SIDEBAND (dB)

70
80

SUPPRESSION BELOW EACH FUNDAMENTAL

5010

0

VS, INPUT SIGNAL AMPLITUDE (mVrms)

fC ±3f

fC ±2f

S

S

800600400200

MOTOROLA ANALOG IC DEVICE DATA

MC1496, B

Figure 21. Suppression of Carrier Harmonic

Sidebands versus Carrier Frequency

0

10

3fC ±f

2fC ±f

2fC ±2f

S

S

S

50101.0 5.00.05 0.1 0.5

20
30
40

50

CARRIER SIDEBAND (dB)

60
70

SUPPRESSION BELOW EACH FUNDAMENTAL

fC, CARRIER FREQUENCY (MHz)

OPERATIONS INFORMATION

The MC1496, a monolithic balanced modulator circuit, is

shown in Figure 23.

This circuit consists of an upper quad differential amplifier
driven by a standard differential amplifier with dual current
sources. The output collectors are cross–coupled so that
full–wave balanced multiplication of the two input voltages
occurs. That is, the output signal is a constant times the
product of the two input signals.

Mathematical analysis of linear ac signal multiplication
indicates that the output spectrum will consist of only the sum
and difference of the two input frequencies. Thus, the device
may be used as a balanced modulator, doubly balanced mixer,
product detector, frequency doubler, and other applications
requiring these particular output signal characteristics.

The lower differential amplifier has its emitters connected
to the package pins so that an external emitter resistance
may be used. Also, external load resistors are employed at
the device output.

Signal Levels

The upper quad differential amplifier may be operated
either in a linear or a saturated mode. The lower differential
amplifier is operated in a linear mode for most applications.

For low–level operation at both input ports, the output
signal will contain sum and difference frequency components

Figure 22. Carrier Suppression versus

Carrier Input Level

0
10
20
30
40
50
60

CS

V , CARRIER SUPPRESSION (dB)

70

VC, CARRIER INPUT LEVEL (mVrms)

fC = 10 MHz

fC = 500 kHz

500100 4003000 200

and have an amplitude which is a function of the product of
the input signal amplitudes.

For high–level operation at the carrier input port and linear
operation at the modulating signal port, the output signal will
contain sum and difference frequency components of the
modulating signal frequency and the fundamental and odd
harmonics of the carrier frequency . The output amplitude will
be a constant times the modulating signal amplitude. Any
amplitude variations in the carrier signal will not appear in the
output.

The linear signal handling capabilities of a differential
amplifier are well defined. With no emitter degeneration, the
maximum input voltage for linear operation is approximately
25 mV peak. Since the upper differential amplifier has its
emitters internally connected, this voltage applies to the
carrier input port for all conditions.

Since the lower differential amplifier has provisions for an
external emitter resistance, its linear signal handling range
may be adjusted by the user. The maximum input voltage for
linear operation may be approximated from the following
expression:

V = (I5) (RE) volts peak.

This expression may be used to compute the minimum
value of RE for a given input voltage amplitude.

Figure 23. Circuit Schematic Figure 24. T ypical Modulator Circuit

Input

Input

Bias

EE

V

C

V

S

5

14V

10 (–)

8 (+)
4 (–)

1 (+)

500500 500

Carrier

Signal

MOTOROLA ANALOG IC DEVICE DATA

(–) 12

Vo,
Output

(+) 6

2

Gain
Adjust

3

(Pin numbers
per G package)

V

C

Carrier

Input

V

S

Modulating

Signal

Input

0.1

10 k

µ

51

F

10 k

50 k

Carrier Null

0.1

51351

R

3.9 k
6

12

12 Vdc

R

L

L

3.9 k
+V

o

–V

o

1.0 k1.0 k

µ

F

2

R

1.0 k

e

8
10

1

MC1496

4

14

–8.0 Vdc

V

EE

5

I5

6.8 k

7

MC1496, B

Figure 25. V oltage Gain and Output Frequencies

Carrier Input Signal (VC) Approximate Voltage Gain Output Signal Frequency(s)

RLV

Low–level dc

High–level dc

Low–level ac

High–level ac

NOTES: 1. Low–level Modulating Signal, VM, assumed in all cases. VC is Carrier Input Voltage.

2.When the output signal contains multiple frequencies, the gain expression given is for the output amplitude of
each of the two desired outputs, fC + fM and fC – fM.

3.All gain expressions are for a single–ended output. For a differential output connection, multiply each
expression by two.

4.RL = Load resistance.

5.RE = Emitter resistance between Pins 2 and 3.

6.re = Transistor dynamic emitter resistance, at 25°C;

7. K = Boltzmann′s Constant, T = temperature in degrees Kelvin, q = the charge on an electron.

2(RE)

Ǹ

22

KT

[

q

C

KT

ǒ

L

2r

e

(RE)

L

2r

e

26 mV

I5(mA)

q

Ǔ

2re)

2re)

R

RE)

RLVC(rms)

KT

ǒ

Ǔ

q

0.637 R
RE)

re

[

26 mV at room temperature

f

M

f

M

fC ± f

M

fC ± fM, 3fC ± fM, 5fC ± fM, . . .

The gain from the modulating signal input port to the
output is the MC1496 gain parameter which is most often of
interest to the designer. This gain has significance only when
the lower differential amplifier is operated in a linear mode,
but this includes most applications of the device.

As previously mentioned, the upper quad differential
amplifier may be operated either in a linear or a saturated
mode. Approximate gain expressions have been developed
for the MC1496 for a low–level modulating signal input and
the following carrier input conditions:

1) Low–level dc

2) High–level dc

3) Low–level ac

4) High–level ac

These gains are summarized in Figure 25, along with the
frequency components contained in the output signal.

APPLICATIONS INFORMATION

Double sideband suppressed carrier modulation is the
basic application of the MC1496. The suggested circuit for
this application is shown on the front page of this data sheet.

In some applications, it may be necessary to operate the
MC1496 with a single dc supply voltage instead of dual
supplies. Figure 26 shows a balanced modulator designed
for operation with a single 12 Vdc supply . Performance of this
circuit is similar to that of the dual supply modulator.

AM Modulator

The circuit shown in Figure 27 may be used as an
amplitude modulator with a minor modification.

All that is required to shift from suppressed carrier to AM
operation is to adjust the carrier null potentiometer for the
proper amount of carrier insertion in the output signal.

However, the suppressed carrier null circuitry as shown in
Figure 27 does not have sufficient adjustment range.
Therefore, the modulator may be modified for AM operation
by changing two resistor values in the null circuit as shown in
Figure 28.

Product Detector

The MC1496 makes an excellent SSB product detector
(see Figure 29).

This product detector has a sensitivity of 3.0 microvolts
and a dynamic range of 90 dB when operating at an
intermediate frequency of 9.0 MHz.

The detector is broadband for the entire high frequency
range. For operation at very low intermediate frequencies
down to 50 kHz the 0.1 µF capacitors on Pins 8 and 10
should be increased to 1.0 µF. Also, the output filter at Pin 12
can be tailored to a specific intermediate frequency and audio
amplifier input impedance.

As in all applications of the MC1496, the emitter resistance
between Pins 2 and 3 may be increased or decreased to
adjust circuit gain, sensitivity , and dynamic range.

This circuit may also be used as an AM detector by
introducing carrier signal at the carrier input and an AM signal
at the SSB input.

The carrier signal may be derived from the intermediate
frequency signal or generated locally . The carrier signal may
be introduced with or without modulation, provided its level is
sufficiently high to saturate the upper quad differential

8

MOTOROLA ANALOG IC DEVICE DATA

MC1496, B

amplifier. If the carrier signal is modulated, a 300 mVrms
input level is recommended.

Doubly Balanced Mixer

The MC1496 may be used as a doubly balanced mixer
with either broadband or tuned narrow band input and output
networks.

The local oscillator signal is introduced at the carrier input
port with a recommended amplitude of 100 mVrms.

Figure 30 shows a mixer with a broadband input and a
tuned output.

Frequency Doubler

The MC1496 will operate as a frequency doubler by
introducing the same frequency at both input ports.

TYPICAL APPLICATIONS

Figure 26. Balanced Modulator

(12 Vdc Single Supply)

V

10 k

CC

12 Vdc

µ

F

0.1

25

Carrier Input
60 mVrms

Modulating
Signal Input

300 mVrms
Carrier

Null

50 k

1.0 k

0.1

+

µ

F

15 V

–R1+

µ

F

10
15 V

10 k 100 100

10 k

0.1

1.3 k820

µ

F

51

µ

F

8

10

1
4

25
15 V

+

1.0 k

2

MC1496

µ

F
–

14 5

3.0 k 3.0 k

3

6

12

DSB
Output

Figures 31 and 32 show a broadband frequency doubler
and a tuned output very high frequency (VHF) doubler,
respectively.

Phase Detection and FM Detection

The MC1496 will function as a phase detector. High–level
input signals are introduced at both inputs. When both inputs
are at the same frequency the MC1496 will deliver an output
which is a function of the phase difference between the two
input signals.

An FM detector may be constructed by using the phase
detector principle. A tuned circuit is added at one of the inputs
to cause the two input signals to vary in phase as a function
of frequency. The MC1496 will then provide an output which
is a function of the input signal frequency .

Figure 27. Balanced Modulator–Demodulator

V

CC

12 Vdc

R

L

R

3.9 k

V

C

Carrier

Input

V

S

Modulating

Signal

Input

0.1

51

µ

F

10 k10 k 51 51

50 k

Carrier Null

1.0 k1.0 k

0.1

µ

F

2

8

10

1
4

14 5

R

1.0 k

e

MC1496

V

EE

–8.0 Vdc

3

3.9 k
6

12

I5

6.8 k

L

+V

o

–V

o

0.1

V

C

Carrier

Input

V

S

Modulating

Signal

Input

Figure 28. AM Modulator Circuit

1.0 k1.0 k

µ

F

51

µ

F

50 k

Carrier Adjust

0.1

750 51 51750

R

23

8

10

1

MC1496

4

14 5

V
–8.0 Vdc

e

EE

1.0 k

15

3.9 k

6

12

6.8 k

Figure 29. Product Detector

(12 Vdc Single Supply)

V

V

CC

12 Vdc

R

L

3.9 k

+V

–V

R

L

Carrier Input

o

300 mVrms

SSB Input

o

1.0 k

0.1

0.1

1.0 k

51

1.0 k

8

10

1
4

0.1

µ

µ

F

µ

F

µ

0.1
2

MC1496

14 5

F

F

100

1.3 k820

3.0 k 3.0 k

3

6

12

10 k

CC

12 Vdc

0.005

µ

F

1.0 k

0.005

µ

F

1.0

0.005

µ

F

µ

F

R

L

AF

Output

q

10 k

MOTOROLA ANALOG IC DEVICE DATA

9

Figure 30. Doubly Balanced Mixer

(Broadband Inputs, 9.0 MHz Tuned Output)

1.0 k

0.001 µF

Local

Oscillator

Input

100 mVrms

51

0.001

µ

RF Input

10 k

51

10 k 51

50 k

Null Adjust

L1 = 44 Turns AWG No. 28 Enameled Wire, Wound
on Micrometals Type 44–6 Toroid Core.

1.0 k

0.01

µ

F

3

2

8

10

F

1

MC1496

6

4

14

12

5

5.0–80

6.8 k

V

EE

–8.0 Vdc

0.001

150 MHz

Input

MC1496, B

V

CC

+8.0 Vdc

RFC

µ

H

100

µ

F

0.001

9.5 µF
L1

pF

9.0 MHz
Output
RL = 50

90–480 pF

Figure 32. 150 to 300 MHz Doubler

1.0 k1.0 k

0.001

0.001

µ

F

8

10

1
4

100

–8.0 Vdc

100

100

µ

F

10 k

10 k

50 k

Balance

1.0 k

Input
15 mVrms

Ω

10 k 10 k

µ

F

23

MC1496

14 5

V

EE

18 pF

0.68
6

12

6.8 k

Figure 31. Low–Frequency Doubler

1.0 k

C2

µ

F

100
15 Vdc Max

50 k

Balance

V

CC

+8.0 Vdc

+

V

FC

µ

L1

H

18 nH

R

1.0–10 pF

1.0–10 pF

L1 = 1 Turn AWG
No. 18 Wire, 7/32″ ID

+
–

100

µ

F

100
25 Vdc

C2

+–

100 µF 15 Vdc

100

100

300 MHz
Output
RL = 50

10

8

1
4

Ω

2

14

1.0 k

MC1496

V

EE

–8.0 Vdc

V

CC

12 Vdc

3.9 k

3

3.9 k

6

Output

12

5

6.8 k

I5

10

AMPLITUDE

C S

C S

(f – f )

(f + f )

C

C S

(f )

(f – 2f )

(f + 2f )

Frequency Balanced Modulator Spectrum

f

Carrier Fundamental

C

f

Modulating Signal

S

fC ± f

Fundamental Carrier Sidebands

S

C S

C S

(2f – 2f )

C S

C

(2f )

(2f – 2f )

DEFINITIONS

fC ± nf

nf

nfC ± nf

C S

(2f + 2f )

C S

(2f + 2f )

Fundamental Carrier Sideband Harmonics

S

Carrier Harmonics

C

Carrier Harmonic Sidebands

S

MOTOROLA ANALOG IC DEVICE DATA

C S

(3f – f )

C

C S

(3f – 2f )

(3f )

C S

(3f + f )

C S

(3f + 2f )

–T–

SEATING
PLANE

–A–

14 8

G

D 14 PL

0.25 (0.010) A

MC1496, B

OUTLINE DIMENSIONS

D SUFFIX

PLASTIC PACKAGE

CASE 751A–03

(SO–14)

ISSUE F

–B–

P 7 PL

M

71

0.25 (0.010) B

C

X 45

R

K

M

S

B

T

S

M

_

M

J

NOTES:

1. DIMENSIONING AND TOLERANCING PER ANSI
Y14.5M, 1982.

2. CONTROLLING DIMENSION: MILLIMETER.

3. DIMENSIONS A AND B DO NOT INCLUDE
MOLD PROTRUSION.

4. MAXIMUM MOLD PROTRUSION 0.15 (0.006)
PER SIDE.

5. DIMENSION D DOES NOT INCLUDE DAMBAR
PROTRUSION. ALLOWABLE DAMBAR
PROTRUSION SHALL BE 0.127 (0.005) TOTAL
IN EXCESS OF THE D DIMENSION AT
MAXIMUM MATERIAL CONDITION.

F

DIM MIN MAX MIN MAX

A 8.55 8.75 0.337 0.344
B 3.80 4.00 0.150 0.157
C 1.35 1.75 0.054 0.068
D 0.35 0.49 0.014 0.019
F 0.40 1.25 0.016 0.049
G 1.27 BSC 0.050 BSC
J 0.19 0.25 0.008 0.009
K 0.10 0.25 0.004 0.009
M 0 7 0 7

____

P 5.80 6.20 0.228 0.244
R 0.25 0.50 0.010 0.019

INCHESMILLIMETERS

P SUFFIX

PLASTIC PACKAGE

CASE 646–06

ISSUE L

14 8

B

17

A
F

L

C

N

SEATING

HG D

PLANE

K

J

M

NOTES:

1. LEADS WITHIN 0.13 (0.005) RADIUS OF TRUE
POSITION AT SEATING PLANE AT MAXIMUM
MATERIAL CONDITION.

2. DIMENSION L TO CENTER OF LEADS WHEN
FORMED PARALLEL.

3. DIMENSION B DOES NOT INCLUDE MOLD
FLASH.

4. ROUNDED CORNERS OPTIONAL.

DIM MIN MAX MIN MAX

A 0.715 0.770 18.16 19.56
B 0.240 0.260 6.10 6.60
C 0.145 0.185 3.69 4.69
D 0.015 0.021 0.38 0.53
F 0.040 0.070 1.02 1.78
G 0.100 BSC 2.54 BSC
H 0.052 0.095 1.32 2.41
J 0.008 0.015 0.20 0.38
K 0.115 0.135 2.92 3.43
L 0.300 BSC 7.62 BSC

M 0 10 0 10

____

N 0.015 0.039 0.39 1.01

MILLIMETERSINCHES

MOTOROLA ANALOG IC DEVICE DATA

11

MC1496, B

Motorola reserves the right to make changes without further notice to any products herein. Motorola makes no warranty , representation or guarantee regarding
the suitability of its products for any particular purpose, nor does Motorola assume any liability arising out of the application or use of any product or circuit, and
specifically disclaims any and all liability, including without limitation consequential or incidental damages. “T ypical” parameters which may be provided in Motorola
data sheets and/or specifications can and do vary in different applications and actual performance may vary over time. All operating parameters, including “Typicals”
must be validated for each customer application by customer’s technical experts. Motorola does not convey any license under its patent rights nor the rights of
others. Motorola products are not designed, intended, or authorized for use as components in systems intended for surgical implant into the body, or other
applications intended to support or sustain life, or for any other application in which the failure of the Motorola product could create a situation where personal injury
or death may occur. Should Buyer purchase or use Motorola products for any such unintended or unauthorized application, Buyer shall indemnify and hold Motorola
and its officers, employees, subsidiaries, affiliates, and distributors harmless against all claims, costs, damages, and expenses, and reasonable attorney fees
arising out of, directly or indirectly, any claim of personal injury or death associated with such unintended or unauthorized use, even if such claim alleges that
Motorola was negligent regarding the design or manufacture of the part. Motorola and are registered trademarks of Motorola, Inc. Motorola, Inc. is an Equal
Opportunity/Affirmative Action Employer.

How to reach us:
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12

◊

MOTOROLA ANALOG IC DEVICE DATA

MC1496/D

*MC1496/D*