Datasheet MC13030DW Datasheet (Motorola)

Device

Operating

Temperature Range

Package



SEMICONDUCTOR

TECHNICAL DATA

DUAL CONVERSION

AM RECEIVER

ORDERING INFORMATION

MC13030DW TA = –40° to +85°C SOIC–28

DW SUFFIX

PLASTIC PACKAGE

CASE 751F

28

1

(Top View)

PIN CONNECTIONS

Order this document by MC13030/D

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8

9
10
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12
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14

28
27
26
25
24
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20
19
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17
16
15

Mix1 In
Mix1 In
RF Gnd
FET RF AGC
RF AGC2
RF AGC Adj
Mix1 RF AGC Adj
SD Level
IF Gnd
SD IF Out
S Level Out
IF AGC In
AF Out
V

CC

VCO Out

VCO
VCO Ref
Mix1 Out
Mix1 Out

V

ref

Mix2 In
Mix2 Out
Mix2 Out

Xtal Osc E
Xtal Osc B

IF In

Det V

ref

Det In

1

MOTOROLA ANALOG IC DEVICE DATA

 

 
 

The MC13030 is a dual conversion AM receiver designed for car radio
applications. It includes a high dynamic range first mixer, local oscillator,
second mixer and second oscillator, and a high gain AGC’d IF and
detector. Also included is a signal strength output, two delayed RF AGC
outputs for a cascode FET/bipolar RF amplifier and diode attenuator, a
buffered IF output stage and a first local oscillator output buf fer for driving
a synthesizer . Frequency range of the first mixer and oscillator is 100 kHz
to 50 MHz.

Applications include single band and multi–band car radio receivers, and
shortwave receivers.

• Operation from 7.5 to 9.0 Vdc

• First Mixer, 3rd Order Intercept = 20 dBm

• Buffered First Oscillator Output

• Second Mixer, 3rd Order Intercept = +5.0 dBm

• No Internal Beats Between 1st and 2nd Oscillator Harmonics

• Signal Strength Output

• Limited 2nd IF Output for Frequency Counter Station Detector

• Adjustable IF Output Station Detector Level

• Adjustable RF AGC Threshold for Both Mixer Inputs

• Two Delayed AGC Outputs for Cascode RF Stage and Diode Attenuator

Representative Block Diagram

This device contains 335 active transistors.

1413121110987654321

1516171819202122232425262728

V

CC

VCO

5.1 V 6.5 V
Mix1

Mix2 XTal

Osc

4.1 V

3.0 mA
IF Amp

AGC

6.6 mA

 Motorola, Inc. 1996 Rev 1

MC13030

2

MOTOROLA ANALOG IC DEVICE DATA

MAXIMUM RATINGS (T

A

= 25°C, unless otherwise noted.)

Rating

Symbol Value Unit

Power Supply V

CC

10 V

Operating Temperature T

A

–40 to +85 °C

Storage Temperature T

stg

–65 to +150 °C

Junction Temperature T

J

150 °C

NOTE: ESD data available upon request.

ELECTRICAL CHARACTERISTICS (T

A

= 25°C, VCC = 8.0 V, unless otherwise noted.)

Characteristic

Condition/Pin Symbol Min Typ Max Unit

Power Supply Voltage – V

CC

7.5 8.0 9.0 V

Power Supply Current VCC = 8.0 V I

CC

26 32 44 mA
Detector Output Level Vin = 1.0 mV , 30% Mod. V13 160 200 240 mVrms
Audio S/N Ratio Vin = 1.0 mV , 30% Mod. S/N 48 52 – dB
Audio THD Vin = 1.0 mV , 30% Mod.

THD – 0.3

1.0

%

Vin = 1.0 mV , 80% Mod.

– 0.3

1.0

Vin = 2.0 mV , 80% Mod. – 0.4 1.5

Signal Strength Output Vin = 0 to 2.0 V V11 0 – 5.2 V
VCO Buffer Output – V28 178 224 282 mV
SD Output Level Vin = 1.0 mV , V11 > V8 V10 2.3 2.7 3.3 Vpp

MIXER1

Input Resistance 1 or 2 to Gnd – – 10 – kΩ
Third Order Intercept Point 1 or 2 IP3 – 127 – dBµV
Conversion Transconductance 1 or 2 to 24 + 25 g

c

– 2.2 – mS

Total Collector Current 24 + 25 I

C

– 4.6 – mA

Input IF Rejection 1 or 2 – – 45 – dB

MIXER2

Input Resistance 22 – – 2.4 – kΩ
Third Order Intercept Point 22 IP3 – 112 – dBµV
Conversion Transconductance 22 to 20 + 21 g

c

– 4.6 – mS

Total Collector Current 20 + 21 I

C

– 3.0 – mA

VCO

Minimum Oscillator Coil Parallel Impedance 27 to 26 R

P

– 3.0 – kΩ

Buffer Output Level 28 V

O

– 224 – mVrms

Stray Capacitance 27 C

S

– 7.0 – pF

IF AMPLIFIER

Input Resistance 17 R

in

– 2.0 – kΩ

Transconductance 17 to 15 g

m

– 28 – mS

Maximum Input Level 17 V

in

– 125 – mVrms

Minimum Detector Coil Parallel Impedance 17 to 15 R

L

– 15 – kΩ
RF Output Level 15, Vin = 1.0 mV – – 2.0 – Vpp
Audio Output Impedance 13 R

out

– 120 – Ω
Audio Output Level 13 @ 30% Mod. V

out

– 200 – mVrms

MC13030

3

MOTOROLA ANALOG IC DEVICE DATA

NOTES: 1. The transformers used for at the output of the mixers are wideband 1:4 impedance ratio. The secondary load is the 50 Ω input of the spectrum

analyzer, so the impedance across the collectors of the mixer output is 200 Ω.

2.Since the VCO frequency is not critical for this measurement, a fixed tuned oscillator tuned to 11.7 MHz is used. This gives an input frequency
of 1.0 MHz.

3.The detector coil is loaded with a 10 k resistor to reduce the tuned circuit Q and to present a 10 kΩ load to the IF output for determination of IF
transconductance.

4.The RF AGC current, S output current and Pin 6 current are measured by connecting a current measuring meter to these pins, so they are effectively
shorted to ground.

5.SD adjust is adjusted by connecting a power supply or potentiometer and voltmeter to Pin 8.

Figure 1. Test Circuit

1516171819202122232425262728

VCO

Out

VCO VCO

Ref

Mix1

Out

Mix1

OutRFV

ref

Mix2InMix2

Out

Mix2

Out

Xtal

Osc E

Xtal

Osc B

IF In Det

V

ref

Det

In

Mix1InMix1InRF

Gnd

FET
RF

AGC

RF

AGC2

RF

AGC

Adj

Mix1

RF AGC

Adj

SD

LevelIFGnd

SD IF

Out

S Level

OutIFAGC InAFOut

V

CC

Mixer1 Out Mixer2 Out

8.0 V

Mixer2 In

Osc Out

Mixer1 Input

FO = 1.0 MHz

FET RF AGC Voltage

RF AGC Current

Pin 6 Current

SD Adjust

IF Signal Out

S Output Current

Audio Out

IF Output/
Det Input

IF

Input

Adj to 11.7 MHz

2.2

µ

H

82 pF

680

µ

H

47

µ

F

8.0 V

10 k 10 k

++

22

0.1

0.1

10.245

47

0.1

1.0

µ

F

+

0.1

0.01

47

47

1:4 1:4

10 k 180 pF

0.1

0.1

R7

0.1

4.7

µ

F

+

1413121110987654321

FUNCTIONAL DESCRIPTION

The MC13030 contains all the necessary active circuits for

an AM car radio or shortwave receiver.

The first mixer is a multiplier with emitter resistors in the
lower, signal input transistors to give a high dynamic range. It
is internally connected to the first oscillator (VCO). The input
pins are 1 and 2. The input can be to either Pins 1 or 2, or
balanced. These pins are internally biased, so a dc path
between them is allowable but not necessary. The mixer
outputs are open collectors on Pins 25 and 26. They are
normally connected to a tuned transformer.

The first oscillator on Pin 27 is a negative resistance type
with automatic level control. The level is low so the signal
does not modulate the tuning diode capacitance and cause

distortion. Pin 26 is the reference voltage for the oscillator
coil. This reference is also the supply for the mixer circuits.
The upper bases of the mixer are 0.7 V below this reference.

The second mixer is similar to the first, but it is single–
ended input on Pin 22. Its outputs are open collectors on
Pins 20 and 21 which are connected to a tuned transformer.
The dynamic range of this mixer is less than the first. It is also
connected internally to an oscillator which is normally crystal
controlled. The oscillator is a standard Colpitts type with the
emitter on Pin 19 and the base on Pin 18.

The IF amplifier input is Pin 17. The AGC operates on the
input stage to obtain maximum dynamic range and minimum
distortion. The IF output, Pin 15, is a current source.

MC13030

4

MOTOROLA ANALOG IC DEVICE DATA

Therefore, its gain is determined by the load impedance
connected between Pins 15 and 16. Pin 16 is a voltage
reference for the output. The output is internally connected to
the AM detector, and Pin 13 is the detector output. This
detector also provides the AGC signal for the IF amplifier. An
RC filter from Pin 13 to 12 removes the audio, leaving a dc
level proportional to the carrier level for AGC.

Pin 11 provides a current proportional to signal strength.
It is a current source so a resistor must be connected from
Pin 11 to ground to select the desired dc voltage range. The
current is proportional to the signal level at Pin 17, the IF
amplifier input.

A high–gain limiting amplifier is used to derive the station
detect (SD) signal output on Pin 10; this output is present only if
it is turned on by the voltage on Pin 8. If the voltage on
Pin 8 is less than the voltage on Pin 11, the output on Pin 10 is
“on”. The station detector IF output on Pin 10 is used with
synthesizers which have a frequency counting signal detector.

The RF AGC outputs on Pins 4 and 5 are controlled by the
signal levels at Mixer1 or Mixer2. Bypass capacitors are
required on Pins 6 and 4 to remove audio signals from the
AGC outputs. Pin 4 is designed to control the NPN transistor
in series with the RF amplifier FET. The voltage on Pin 4 is

5.1 V with no input signal and decreases with increasing input
signal. Pin 5 is designed to control an additional AGC circuit
at the antenna input. The voltage on Pin 5 is at 0 V with no
input signal and increases with increasing input signals. The
voltage on Pin 5 does not increase until the voltage on Pin 4
has decreased to about 1.3 V . In most cases, Pin 5 is used to
drive a diode shunt. Maximum output current is about 850 µA.

The RF AGC sensitivity is about 40 mVrms input to Mixer1
or about 2.0 mVrms input to Mixer2 at 1.0 MHz. The AGC
sensitivity for both mixers can be decreased by adding a
resistor from Pin 6 to ground. There is also an additional
amplifier between Mixer1 and its AGC rectifier. The gain of
this amplifier and AGC sensitivity for Mixer1 can be increased
by adding a resistor from Pin 7 to ground. Therefore, the
desired AGC sensitivity for both mixers can be achieved by
changing the resistors on Pins 6 and 7.

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2
3
4
5
6
7
8

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10
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12
13
14

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25
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22
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20
19
18
17
16
15

Mix1 In
Mix1 In
RF Gnd
FET RF AGC
RF AGC2
RF AGC Adj
Mix1 RF AGC Adj
SD Level
IF Gnd
SD IF Out
S Level Out
IF AGC In
AF Out
V

CC

VCO Out

VCO
VCO Ref
Mix1 Out
Mix1 Out

V

ref

Mix2 In
Mix2 Out
Mix2 Out

Xtal Osc E
Xtal Osc B

IF In

Det V

ref

Det In

Figure 2. Pin Connections and DC Voltages

5.1 V

5.1 V

5.1 V

7.8 V

7.8 V

6.5 V

3.7 V

7.9 V

7.9 V

4.4 V

5.0 V

4.8 V

4.1 V

4.1 V

3.3 V

3.3 V
0 V

5.1 to 0 V

0 to 850

µ

A

0 to 2.8 V

200 mV

43 mV

0 to 4.8 V

0 V

6.5 V

0 to 4.8 V

3.6 to 4.5 V

3.6 to 4.5 V

8.0 V

S Out versus IF Input:

The S output current at Pin 11 is provided by two
collectors, one a PNP source and the other a sink to ground.
The desired S output voltage can be selected using the curve
of Figure 3 and calculating the value of the required resistor.

Figure 3. S Output Current versus IF Input Level

IF INPUT LEVEL (dBµV)

30 40 50 100

0

20

40

60

70

PIN 11 CURRENT ( A)

60 70 80 90

µ

RF FET AGC versus Mixer1 and Mixer2 Input Level:

Figures 4 and 5 are generated with no external resistance
on Pins 4 or 6, so they represent the minimum RF AGC
sensitivity of Mixer1 and Mixer2.

Figure 4. RF AGC Voltage versus Mixer1 Input

85 90 95 100 105

0

1.0

2.0

3.0

4.0

5.0

MIXER1 INPUT LEVEL (dB

µ

V)

PIN 4 VOLTAGE (V)

Figure 5. RF AGC Voltage versus Mixer2 Input

MIXER2 INPUT LEVEL (dBµV)

65 70 75 80

0

1.0

2.0

3.0

4.0

5.0

PIN 4 VOLTAGE (V)

MC13030

5

MOTOROLA ANALOG IC DEVICE DATA

Pin 6 Current versus Mixer1 and Mixer2 Input Level:

The internal resistance from Pin 6 to ground is 39 k.
The RF AGC voltage on Pin 4 is 2.0 V when the voltage on
Pin 6 is 1.2 V. Therefore, the desired AGC thresholds for
either mixer can be set with these curves. The design steps
are described in the design notes.

Figure 6. Pin 6 Current versus Mixer1 Input Level

MIXER1 INPUT LEVEL (dBµV)

90 100 110 120

0

50

100

150

200

250

PIN 6 CURRENT ( A)

µ

PIN 6 CURRENT ( A)

µ

Figure 7. Pin 6 Current versus Mixer2 Input Level

MIXER2 INPUT LEVEL (dBµV)

80 90 120

0

50

100

150

200

100 110

250

Mixer1 AGC Gain Increase versus R7:

Adding a resistor from Pin 7 to ground increases the AGC
sensitivity of Mixer1. The range of increase in dB can be
found from this curve. This is useful after setting up the AGC
threshold of Mixer2.

Figure 8. Mixer1 AGC Gain Increase versus R7

R7

100 10 k

0

5.0

6.0

7.0

8.0

INCREASE IN MIXER1 AGC SENSITIVITY (dB)

1.0 k

1.0

2.0

3.0

4.0

Pin 5 Current versus Pin 4 Voltage:

All the curves give Pin 4 AGC voltage versus some other
input level. This curve can be used to determine the auxiliary
AGC current from Pin 5 at a given Pin 4 voltage.

Figure 9. Pin 5 Current versus Pin 4 Voltage

PIN 5 CURRENT (mA)

0 0.4 0.8 1.2

0

1.0

2.0

3.0

4.0

5.0

PIN 4 VOLTAGE

MC13030

6

MOTOROLA ANALOG IC DEVICE DATA

PIN FUNCTION DESCRIPTION

Pin No. Internal Equivalent Circuit Description

1, 2

12

10 k10 k

3.3 V

6.6 mA

150 150

Mixer1 Input

Pins 1 and 2 are equivalent. In the application circuit, 2 is grounded
with a capacitor and 1 is the input. If a load resistor is needed for the
input filter, it can be placed across Pins 1 and 2. Input impedance for
each pin is 10 k. IP3 (third order intercept) at the input is 20 dBm
(127 dBµ). To guarantee –50 dB IM3, the input level should not be
greater than 3.5 dBm (103 dBµ) (150 mVrms).

3

3

RF Ground

This should be connected to the ground used for the RF circuits.

4

4

5

10 k

5.1 V 4.0 V

3.4 k

FET RF AGC Output

This is the AGC for the cascode transistor connected to the RF amplifier
FET. The no–signal voltage is 5.1 V. The voltage decreases with
increasing input signals. A bypass capacitor and electrolytic capacitor
must be added to filter out RF signals on the transistor and audio signals
in the AGC signal. See Figures 4 and 5.

5

5

100 22 k

V

CC

330

RF AGC2 Output

The voltage on this pin starts at 0 and increases with increasing input
signals. It is normally used to turn on diodes or a transistor connected
across the antenna input and is AGC delayed until Pin 6 reaches 2.7 V .
If the voltage on Pin 5 decreases below 2.0 V , the voltage on this pin will
decrease from 3.1 down to about 1.5 V . The maximum output current is
about 850 µA.

6

6

330

AGC

1.0 k

39 k 3.3 k

RF AGC Adjust

An electrolytic capacitor of 1.0 µF must be connected to prevent audio
modulation of the AGC circuits. If there is no resistor on this pin, the RF
AGC starts at an input level to Mixer1 ≈ 40 mVrms or Mixer2 ≈ 2.0 mVrms.
Connecting a resistor from Pin 6 to ground increases RF levels required
for AGC to start. It should be used to set the desired AGC level of Mixer2.
If a resistor is not connected to Pin 6, unwanted RF signals will cause the
AGC to start at a very low level, and desired signals may be suppressed.

7

7

500

1.5 k

Mixer1 RF Level Adjust

A resistor from Pin 7 to ground will increase the gain of an amplifier from
the input of Mixer1 to the AGC circuit. It can be used to set the RF AGC
level of Mixer1. The minimum value of R7 is about 680 Ω.

8

8

510

3.3 k

SD

S

Station Detector Signal Level Adjust

A voltage on Pin 8 will set the desired signal strength at which the SD IF
Out on Pin 10 appears. The other input to this comparator is the S (signal
strength) signal. If Pin 8 is grounded, a square wave of the 2nd IF (usually
450 of 455 kHz) is present with very small input levels. This output could
also be used to drive an FM detector if desired.

9

9

IF Ground

Pin 9 is the ground for the IF section.

MC13030

7

MOTOROLA ANALOG IC DEVICE DATA

PIN FUNCTION DESCRIPTION (continued)

Pin No. DescriptionInternal Equivalent Circuit

10

IF

10

10 k

SD

510

Station Detector IF Output

This output is “on” when V11 > V8. The output is an amplified and limited
2nd IF signal. The signal level is ≈ 250 mVpp when it is 100% “on”.

11

11

510

1.0 k

1.0 k

V

CC

S Level Output

This is a dc current proportional to IF input level. With a load resistor of
75 k, the dc voltage is 0 to 5.1 V.

12

12

1.0 k

V

CC

IF AGC In

The IF gain is controlled by the dc voltage on this pin. It is normally
connected to Pin 13 through an RC network to filter out the audio signal
on Pin 13. The IF gain is maximum when V13 ≈ 3.6 V. When V13
increases, the IF gain decreases.

13

100

13

V

CC

Audio Output

The dc voltage on Pin 13 is ≈ 3.6 V with no input signal and increases to
≈ 4.5 V at minimum IF gain. A nonpolarized electrolytic capacitor may be

required to couple to the audio circuits if the audio amplifier dc bias
voltage is between these voltages.

14

V

CC

14

Supply Voltage

The nominal operating voltage is 8.0 V .

15

510

510

510

15

IF Amplifier Output and Detector Input

The detector coil must be connected between Pin 15 and 16. The IF
amplifier output is a current source, the IF amplifier is a transconductance
amplifier; the gain is determined by the impedance between Pins 15 and

16. The IF amplifier gm ≈ 0.028 mho. If a wide bandwidth IF is desired, the
detector coil can be connected between Pins 15 and 16 without a tap and
then loaded with a resistor across the coil.

16

16

1.0 k

510

Detector Reference Voltage

One side of the detector coil is connected to this pin. It should be
bypassed with a 0.1 µF capacitor.

MC13030

8

MOTOROLA ANALOG IC DEVICE DATA

PIN FUNCTION DESCRIPTION (continued)

Pin No. DescriptionInternal Equivalent Circuit

17

2.0 k

4.8 V

17

To SD
Circuit

IF Input

The IF input impedance is 2.0 k to match most ceramic 455 or 450 kHz
filters. For a ceramic filter requiring a 1.5 k load, a 5.6 k resistor in
series with a 0.01 µF capacitor should be connected from Pin 17 to
ground.

18

19

18

5.1 k

500

Crystal Oscillator Base

The crystal oscillator is a simple Colpitts type, operating at a low
current. The crystal should operate at 10.250 MHz for 450 kHz IF or

10.245 MHz for 455 kHz IF with a 20 pF load capacitance. The
oscillator signal to the second mixer is coupled from Pin 18 through an
emitter follower. If a synthesizer such as the Motorola MC145170 with
a 15 bit programmable R counter is used, the 10.245 MHz crystal can
be connected to the synthesizer, and a 200 mVpp oscillator signal
from the synthesizer can be capacitively coupled to Pin 18, so only
one crystal is needed.

19 Crystal Oscillator Emitter

The capacitive divider from Pin 18 is connected as shown in the
application circuits of Figures 10, 11, 12.

20, 21

20 21

Mixer2 Output

The maximum AC collector voltage is about 5.8 Vpp or 2.0 Vrms. The
mixer conversion transconductance gc = 0.0046 mho. The load
impedance should be selected so the mixer output does not overload
before the input.

22

5.1 V

To AGC

Circuit

2.4 k

22

51 51

3.0 mA3.7 V

Mixer2 Input

The input impedance is 2.4 k. A series R–C network from Pin 22 to
ground or a resistor from the filter to Pin 22 can be used to properly
match the filter. In most cases, a 10.7 MHz crystal filter can be connected
to Pin 22 directly without any additional components. IP3 (third order
intercept) at the input is 5.0 dBm (1 12 dBµ). T o guarantee –50 dB IM3, the
input level should not be greater than –20 dBm (87 dBµ) (22.7 mVrms).

23

23

6.5 V
V

ref

V

ref

This is the main reference voltage for most of the circuits in the IC and
should be bypassed with a 1.0 µF capacitor.

24, 25

VCO

24

5.1 V

25

Mixer1 Output

The maximum collector voltage is about 5.8 Vpp or 2.0 Vrms. The mixer
conversion transconductance gc = 0.0022. The load impedance should
be selected so the mixer output does not overload before the input.

MC13030

9

MOTOROLA ANALOG IC DEVICE DATA

PIN FUNCTION DESCRIPTION (continued)

Pin No. DescriptionInternal Equivalent Circuit

26

V

CC

V

ref

26

75

VCO Reference

The first oscillator coil is connected from Pin 26 to 27. Pin 26 must be
bypassed to ground with a capacitor which has a low impedance at the
oscillator frequency. This capacitor also will reduce the phase noise of
the VCO.

27

7.5 k

27

to Mixer1

VCO

The VCO is a negative resistance type and has an internal level control
circuit so a tapped coil or one with a secondary is not needed. The level
is fixed at 0.8 Vpp so the oscillator signal does not modulate the tuning
diode, thus keeping the distortion low. The oscillator stray capacitance is
≈ 12 pF and the tuned circuit impedance should be greater than 3.0 k to
guarantee oscillation. Oscillator range is up to 45 MHz so it can be used
for SW receivers.

28

100

28

VCO Out

The output level is 240 mVrms (108 dBµ), high enough to drive any
CMOS synthesizer.

AM CAR RADIO DESIGN NOTES

The MC13030 AM Radio IC is intended for dual
conversion AM radios. In most cases, the 1st IF frequency
(F

IF1

) is upconverted above the highest input frequency. The
first oscillator (VCO) is tuned by a synthesizer and operates
at Fin + F

IF1

. For the 530 to 1700 kHz AM band with a

10.7 MHz first IF, the VCO goes from 11.23 to 12.40 MHz.
Therefore, F

max/Fmin

for VCO is only 1.104, so one low–cost
tuning diode can be used. Since the required tuning voltage
range can be made less than 5.0 V , it may also be possible to
drive the tuning diode directly or from the phase detector of
the synthesizer IC, such as the Motorola MC145170,
operating from 5.0 V, without using a buffer amplifier or
transistor.

If the VCO is above the incoming frequency, the image

frequency of the first mixer is at f

OSC

+ F

IF1

. For th e A M
broadcast receiver, it is around 22 MHz, so a simple LPF
can be used between the RF stage and Mixer1 input.
However, if a LPF is used, an additional coil is still needed
to supply the collector voltage of the RF amplifier. For this
reason, a BPF filter was used in the application circuit
instead, since it uses the same number of coils and gives
better performance. It is simply a lowpass to bandpass
conversion. The lowpass filter is designed to have a cutoff
frequency equal to the desired bandwidth. In this case, it
would be 1700 – 530 kHz = 1170 kHz. Then, it is
transformed to be resonant at 949 kHz, the geometric
mean of the end frequencies:

1700 x 530 = 949 kHz.

p

A balanced–to–unbalanced transformer is required at the
output of both mixers. The first one is designed so that Mixer1
has enough gain to overcome the loss of the 10.7 MHz filter
and so that the output of the mixer will not overload before the
input. The primary impedance of the transformer is relatively
low, and it may be difficult to control with commonly available

7.0 mm transformers because the number of primary turns is

quite small. It would also require a large tuning capacitance.
A better solution is to tune the secondary with a small
capacitance and then use a capacitive divider to match the
tuned circuit to the filter. This allows one transformer to be
used for either a ceramic or crystal filter. The capacitors can
be adjusted to match the filter. The recommended coil is
made this way.

If the formula: Pin = IP3 – DR/2 is used, the maximum input
level to the mixer can be calculated for a desired dynamic
range.

IP3 = 3rd order intercept level in dB (dBm or dBµ)

DR = dynamic range in dB between the desired signals
and 3rd order intermodulation products

Pin = input level in dBm or dBµ

The RF AGC level can then be adjusted so that Pin does
not exceed this level.

Whether or not a narrow bandwidth crystal or wide
bandwidth ceramic filter is used between the first and second
mixers depends on the receiver requirements. It is possible to
achieve about 50 dB adjacent channel and IM rejection with
a ceramic filter because of the wide dynamic range of the
mixers. If more than this is required, a crystal filter should be
used. If a crystal filter is used, a lower cost CFU type of
455 kHz second IF filter can be used. If a ceramic filter is
used, a CFW type filter should be used because there is no
RF section selectivity in this type of radio.

Since the wideband AGC system is quite sensitive, it can
be set to eliminate all spurious responses present at the
receiver output. However, the RF AGC will sometimes
eliminate or reduce the level of desired signals if there is a
strong signal somewhere in the bandpass of the RF circuit.

The second mixer is designed like the first and requires a
balanced output. Since its load impedance is higher, the
transformer can be designed to be tuned on the primary or

MC13030

10

MOTOROLA ANALOG IC DEVICE DATA

secondary, but, like with the one for the first mixer, if the
secondary is tuned, the tap can be adjusted for the
impedance of the 455 kHz filter. Wideband filters usually have
a higher terminating resistance than the narrowband ones.
The recommended coil is made this way.

The IF amplifier is basically a transconductance amplifier
because the output is a current source. The output is also
internally connected to a high impedance AM detector. gm for
the IF amplifier is ≈ 0.028 mho. The voltage gain will be the
detector coil impedance x 0.028. This can be designed to
give the desired audio output level for a given RF input level.
If it is set too high, the receiver may oscillate with no input
signal. The application circuit was designed for a relatively
narrow bandwidth, so a tapped detector coil is used to get the
desired gain. If a wide bandwidth receiver is desired, the
detector coil can be untapped, and a resistor can be added
across the coil to get the desired Q.

The detector output on Pin 13 is a low impedance. It
supplies the IF AGC signal to Pin 12, so the audio must be
filtered out. The time constant of this filter is up to the
designer. The main requirement is usually the allowable
audio distortion at 100 Hz, 80% modulation. If the time
constant is made too long, the audio level will be slow to
correct when changing stations.

The Signal Strength (S) output is dependent only on the
IF amplifier input level. Its maximum voltage is about 5.0 V
with a 75 k load resistor. The range can be reduced by
using a lower value for the resistor on Pin 11. The S signal
will stop increasing when the RF AGC circuits become
active, so if the RF AGC threshold is set too low, or there is
too much loss from the Mixer2 output to the IF input, the
maximum S signal will be reduced. The desired load
resistor on Pin 11 (R 11) can be determined using the curve
of Pin 11 current versus IF input.

Setting the RF AGC threshold is probably the most difficult
because a trade–off between allowable interference and
suppression of desired signals must be made.

First select the values for both mixers:
a. Using the formula Pin = IP3 – DR/2

Select the desired dynamic range and calculate the

maximum input levels for both mixers. Remember that all

levels must be in dB, dBµV or dBm. Let DR = 50 dB. IP3

for M ixer2 = 112 dBµV. Therefore, P

inmax

= 87 dBµV. IP3

for M ixer1 = 127 dBµV. Therefore, P

inmax

= 102 d BµV.

b. First, adjust the resistor from Pin 6 to ground to give

the desired maximum input level to Mixer2. From the

curve of Pin 6 current versus Mixer2 input level,

R6 = 1.2/110 µA = 11 k. R

int

= 39 k, so R

6ext

= 15 k.

c. From the curve of Pin 6 current versus Mixer1 input level,

determine how much more gain would be required in the

Mixer1 AGC circuit to achieve the desired dynamic range

for Mixer1. From the curve of Relative Sensitivity versus

R7 determine the value of R7. Alternatively, R7 can be

adjusted to give the desired maximum input level to

Mixer1.

The resulting R7 may be too small to set the AGC
threshold of Mixer1 as low as desired. Also, if R7 is less than
680 Ω, the AGC sensitivity for the Mixer1 input falls off at
higher frequencies, so in these cases, the resistor from Pin 6
to ground must be reduced to achieve the desired level
because the overload of Mixer1 provides the most important
spurious response rejection. However, if the AGC level is set
too high, the IF in signal may become too large and the IF
amplifier can overload with strong signals. The values used in
the application are more conservative.

The gain from the antenna input to the point being
measured are shown on the AM radio application. These are
helpful when calculating audio sensitivity and troubleshooting
a new radio.

MC13030

11

MOTOROLA ANALOG IC DEVICE DATA

FL1

T3

Figure 10.

2

8.0 V

A1

L6

C30

T1

0.01

CFU455H2

Crystal Filter

Ceramic Filter

8.0 V

8.0 V

10.5 X

Tuning Voltage

D1

C26

10.245

+

R17

C12

R5

R12

56 pF

34

In

5

1

88 X

28 27 26 25 24 23 22 21 20 19 18 17 16 15

123456 7891011121314

AF Out

0 to 4.8 V

IF Output to

RF In

47

1.0–7.0 V

MV209

C4

C20

0.1

C8

1.0

F

µ

9.8 H

µ

19335

T2

12704

C29

330 pF

47

C27

2200 pF

270 pF

C14

47 pF

X1

CFW455H

Out

Gnd Gnd Gnd

130 X

C13

22 pF

10M7A

180 k

0.1

SK107M5–AE–10A

SFE10.7MHY

123

123

C19

22 pF

C25

0.01
R13

33 k

C2

0.1

R3

1.0 k

C16

120 pF

L2

220 H

µ

L4

220 H

µ

C17

120 pF

4.5 X

R4

1.0 k

L3

220 H

µ

C18

120 pF

C15

0.1

R8

47

+

C7

1.0

F

µ

R6

33 k

R7

1.0 k

R14

56 k

R

V1

100 k

R10

68 k

C23

0.01

Signal Detector

C22

0.1

D2

1N4148

C21

0.01

+

C5

µ

C3

0.01

C1

0.1

L1

1.5 mH

R1

1.0 k

L5

33 H

µ

R2

180

Signal Strength

+

C9

+

C10

R9

10 k

R11

10 k

R15

2.7 k

+

C6

C11

0.1

B1

Bead

C28

0.01

R16

390

R18

1.5 k

IC1

MC13030

V

CC

47 F

6.5 X

µ

4.7 F

µ

47 F

AF
IF AGCI

S Out
IF Out

IF Gnd
SD Adj

M1 AGCL
RF AGCL

RF AGC2
FET AGC
RF Gnd
M1 In
M1 In

Osc Out

Osc

Osc VR

M1 Out

M1 Out

RF VR

M2 In

M2 Out

M2 Out

Xtal E

Xtal B

IF In

IF VR

Det In

D3

1N4148

Q1

J309

Q2

2N4401

Figure 10. AM Radio Application

12705

C24

27 nF

C31

0.01

FL2

µ

4.7 F

MC13030

12

MOTOROLA ANALOG IC DEVICE DATA

SW RADIO DESIGN NOTES

The shortwave receiver was designed to cover from 5.0 to
10 MHz. This MC13030 radio has better performance than
most receivers because of the high dynamic range and
spurious rejection of the mixers.

The RF stage bandpass filter for this radio is the same type
as the one used for the car radio, but the series tuned section
was scaled down in impedance to reduce the inductance of
the coil.

Since most SW receivers include an SSB and CW mode,
the detector coil could have a secondary winding to supply
the second IF signal to this section.

The capacitors C10 and C23 have been reduced from
those in the AM radio so that the AGC system can follow
variations in signal level due to fading.

CB RADIO DESIGN NOTES

The RF stage bandpass filter for this radio consists of a
tuned input and a double tuned interstage filter. For lower cost
radios, a single tuned interstage filter could be used.

The schematic also shows a crystal 10.7 MHz 1st IF filter, but
a ceramic or coil filter could als o be used. An intermodulation
rejection of 50 dB can be obtained with a ceramic 1st IF filter.

A bipolar transistor is shown for the RF stage. A dual gate
CMOS FET could also be used with G2 connected to the
AGC voltage on Pin 4. A PIN diode is recommended for D2.

COIL DATA

T1 – Toko A119ANS–19335UH
T2 – Toko A7MNS–12704UH
T3 – Toko A7MCS–12705Y

MC13030

13

MOTOROLA ANALOG IC DEVICE DATA

Figure 11.

2

8.0 V

A1

L6

C26

T1

0.01

Crystal Filter

8.0 V

Tuning

D1

C27

10.245

+

C12

R5

R13

56 pF

34

In

5

1

28 27 26 25 24 23 22 21 20 19 18 17 16 15

1 2 3 4 5 6 7 8 9 10 11 12 13 14

AM AF Out

0 to 4.8 V

IF Output to

RF In

47

MV209

C4

C20

0.1

C8

1.0

F

µ

2.7 H

µ

19335

T2

12704

C25

330 pF

47

C28

2200 pF

330 pF

C14

47 pF

X1

CFW455HT

Out

Gnd Gnd Gnd

FL2

C13

22 pF

10M7A

0.1

123

C19

100 pF

R14

33 k

C2

0.1

R3

1.0 k

C32

68 pF

L2

15 H

µ

L4

15 H

µ

C17

39 pF

R4

1.0 k

L3

15 H

µ

C18

39 pF

C15

0.1

R8

47

+

C7

1.0

F

µ

R6

33 k

R7

1.0 k

R10

75 k

C9

0.01

FM Detector

C22

0.1

D2

1N4148

C21

0.01

+

C5

µ

C3

0.01

C1

0.1

L1

1.5 mH

R1

1.0 k

L5

33 H

µ

R2

180

Signal Strength

+

C23

+

R9

10 k

R11

10 k

R12

2.7 k

+

C6C11

0.1

B1

Bead

R15

1.5 k

IC1

MC13030

V

CC

47 F

µ

1.0 F

µ

47 F

AF
IF AGCI
S Out
IF Out

IF Gnd
SD Adj
M1 AGCL

RF AGCL
RF AGC2
FET AGC
RF Gnd
M1 In
M1 In

Osc Out

Osc

Osc VR

M1 Out

M1 Out

RF VR

M2 In

M2 Out

M2 Out

Xtal E

Xtal B

IF In

IF VR

Det In

D3

1N4148

Q1

J309

Q2

2N4401

Figure 11. 5 to 10 MHz Radio Application

Voltage

C31

100 pF

IF Output to SSB

Demodulator

C30

0.01
T3

12705

C16

68 pF

C10

µ

1.0 F

C24

27 nF

C29

0.01

Osc Output

to Synthesizer

MC13030

14

MOTOROLA ANALOG IC DEVICE DATA

Figure 12.

8.0 V

A1

L5

C26

T1

0.01

CFU455H2

8.0 V

8.0 V

Tuning

D1

C27

+

R5

R12

56 pF

2

In

31

28 27 26 25 24 23 22 21 20 19 18 17 16 15

123456 7891011121314

AF Out

0 to 4.8 V

IF Output to

RF In

47

MV209

C4

C20

0.1

C8

1.0

F

µ

1.0 H

µ

19335

T2

12704

C25

330 pF

47

C28

2200 pF

270 pF

C14

47 pF

Out

Gnd

C13

22 pF

C19

47 pF

R13

33 k

C2

0.1

C15

0.01

R7

47

+

C7

1.0

F

µ

R5

68 k

R6

1.0 k

R14

56 k

R

V1

100 k

R9

75 k

C23

0.01

Signal Detector

C21

0.01

D2

BA243

L1

1.0 mH

Signal Strength

+

C9

+

C10

R8

10 k

R10

10 k

R15

2.7 k

+

C6

C11

0.1

IC1

MC13030

V

CC

µ

4.7 F

µ

47 F

AF
IF AGCI

S Out
IF Out

IF Gnd
SD Adj

M1 AGCL
RF AGCL

RF AGC2
FET AGC
RF Gnd
M1 In
M1 In

Osc Out

Osc

Osc VR

M1 Out

M1 Out

RF VR

M2 In

M2 Out

M2 Out

Xtal E

Xtal B

IF In

IF VR

Det In

Figure 12. CB Radio Application

C30

33 pF

Crystal Filter

10M7A

123

R16

1.5 k

C12 0.1

T3

12705

C16

47 pF

+

C5

µ

47 F

L3

330 nH

L2

330 nH

Q1

MPS9426

R3

10 k

C1

0.01

R2

3.9 k

C17

0.01

L4

1.0 H

µ

R1

100

C3

100 pF

C29

1.8 pF

C18

120 pF

C22

470 pF

Voltage

Osc Out to Synthesizer

16.265 to 16.705 MHz

C

24

27 nF

C31

0.01

µ

4.7 F

FL1

FL2

10.245

X1

MC13030

15

MOTOROLA ANALOG IC DEVICE DATA

R5

R13

C25

C19

R8

C30

C29

FL1

R16

R12

L6

T1

C28

C8

T2

C13

R17

C9

C12

C10

C24

C6

RV1

C7

C23

C5

R2

L1

L5

R1

C3

R3
C16

L2

L3

C17

C15

C20

C2

C4

R18

C26C27

C14

X1

R9

R11

R15

R10

R14

C31

C22

R6

R7

C21

C1

R4

L4

C18

C11

T3

FL2

D1

D2

D3

J

J

AF

GND

+8.0 V

IF OUT

S

ANT IN

GND

GND VCO V+

Q2

Q1

Figure 13. Printed Circuit Board

(Top View)

4.0

″

(Bottom View)

4.0

″

3.0

″

3.0

″

NOTE: J = Jumper

MC13030

16

MOTOROLA ANALOG IC DEVICE DATA

DW SUFFIX

PLASTIC PACKAGE

CASE 751F–04

ISSUE E

OUTLINE DIMENSIONS

NOTES:

1. DIMENSIONING AND TOLERANCING PER
ANSI Y14.5M, 1982.

2. CONTROLLING DIMENSION: MILLIMETER.

3. DIMENSION A AND B DO NOT INCLUDE
MOLD PROTRUSION.

4. MAXIMUM MOLD PROTRUSION 0.15 (0.006)
PER SIDE.

5. DIMENSION D DOES NOT INCLUDE
DAMBAR PROTRUSION.

ALLOWABLE
DAMBAR PROTRUSION SHALL BE 0.13
(0.005) TOTAL IN EXCESS OF D DIMENSION
AT MAXIMUM MATERIAL CONDITION.

J

K

F

1

15

14

28

–A–

–B–

28X

14X

D

P

S

A

M

0.010 (0.25) B

S

T

M

0.010 (0.25) B

M

26X G

–T–

SEATING
PLANE

C

X 45R

_

M

DIM MIN MAX MIN MAX

INCHESMILLIMETERS

A 17.80 18.05 0.701 0.711
B 7.40 7.60 0.292 0.299
C 2.35 2.65 0.093 0.104
D 0.35 0.49 0.014 0.019

F 0.41 0.90 0.016 0.035

G 1.27 BSC 0.050 BSC

J 0.23 0.32 0.009 0.013
K 0.13 0.29 0.005 0.011
M 0 8 0 8
P 10.01 10.55 0.395 0.415
R 0.25 0.75 0.010 0.029

____

Motorola reserves the right to make changes without further notice to any products herein. Motorola makes no warranty , representation or guarantee regarding
the suitability of its products for any particular purpose, nor does Motorola assume any liability arising out of the application or use of any product or circuit, and
specifically disclaims any and all liability, including without limitation consequential or incidental damages. “T ypical” parameters which may be provided in Motorola
data sheets and/or specifications can and do vary in different applications and actual performance may vary over time. All operating parameters, including “Typicals”
must be validated for each customer application by customer’s technical experts. Motorola does not convey any license under its patent rights nor the rights of
others. Motorola products are not designed, intended, or authorized for use as components in systems intended for surgical implant into the body, or other
applications intended to support or sustain life, or for any other application in which the failure of the Motorola product could create a situation where personal injury
or death may occur. Should Buyer purchase or use Motorola products for any such unintended or unauthorized application, Buyer shall indemnify and hold Motorola
and its officers, employees, subsidiaries, affiliates, and distributors harmless against all claims, costs, damages, and expenses, and reasonable attorney fees
arising out of, directly or indirectly, any claim of personal injury or death associated with such unintended or unauthorized use, even if such claim alleges that Motorola
was negligent regarding the design or manufacture of the part. Motorola and are registered trademarks of Motorola, Inc. Motorola, Inc. is an Equal
Opportunity/Affirmative Action Employer.

How to reach us:
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INTERNET: http://Design–NET.com 5 1 Ting Kok Road, Tai Po, N.T., Hong Kong. 852–26629298

MC13030/D

*MC13030/D*

◊