Datasheet LTC3775 Datasheet (LINEAR TECHNOLOGY)

L DESIGN FEATURES

C

B

0.1µF

C

F

220pF

L1

0.36µH

C

OUT

470µF

2.5V
×2

C

IN1

330µF
35V

V

IN

5V TO 26V

V

OUT

1.2V
15A

C

VCC

4.7µF

C2

330pF

C1

3.9nF

R

ILIMB

57.6k

R

SET

38.3k

R2

4.7k

R

B

10k

C

OUT

: SANYO 2R5TPD470M5

D

B

: CMDSH4E
L1: IHLP-4040DZ-ER-R36-M11
Q

B

: RJK0301DPB-00-J0
Q

T

: RJK0305DPB-00-J0

R

A

10k

R

SENSE

0.003Ω

R

ILIMT

732Ω

D

B

C

SS

0.01µF

TG Q

T

Q

B

V

IN

LTC3775

SGND

SENSE

I

LIMT

I

LIMB

INTV

CC

SS

BG

PGND

MODE/SYNC

RUN/SHDNCOMP

BOOST

SW

FREQ

FB

+

+

Produce High DC/DC Step-Down
Ratios in Tight Spaces with 30ns
Minimum On-Time Controller in
3mm × 3mm QFN

Introduction

It can be a challenge to design a DC/
DC converter that takes a high voltage
automotive or industrial power supply
down to the 1.5V or lower voltages
required by today’s microprocessors
and programmable logic chips.

To maintain efficiency and perfor­mance, designers are often forced to
create a 2-stage solution, which first
steps down to an intermediate voltage
and uses another converter to produce
the low voltage from there. 2-stage
solutions can perform well, and are
handy if the application can use the
intermediate voltage elsewhere, but
2-stage solutions always take more
space and are more costly than a single
stage solution.

Many regulators can produce high
step-down ratios in a single stage if the
switching frequency of the step-down
converter is slowed considerably. How­ever, this option sacrifices efficiency
and requires larger, more expensive
external components, doing little to
solve the space and cost problems
incurred in 2-stage solutions.

The LTC3775 is a voltage mode
DC/DC regulator with a very low
minimum on-time of 30ns, allowing
very wide step-down ratios at high
switching frequencies without sacrific­ing performance. Unlike most voltage
mode controllers, the LTC3775 offers
cycle-by-cycle programmable current
limit, excellent short circuit protection
and fast transient response over a wide
input voltage range.

A 1.2V Converter Operating
from 5V–28VIN at 350kHz

The LTC3775 is ideal for generating
low output voltages from high input
voltages, a common requirement for
powering CPUs from wide-ranging

20

by Theo Phillips

application providing a continuous

Current mode controllers

are often favored for their

continuous monitoring of

current through the inductor

or switches. While a typical

voltage mode controller

requires additional circuitry

to monitor current in the

power stage, the LTC3775

requires no ancillary

circuits to oversee the entire

switching cycle.

rails such as those found in automo­tive applications. Figure 1 shows an

Figure 1. A 1.2V, 15A converter

15A from an 5V–26V input.

Current mode controllers are often
favored for their continuous monitor­ing of current through the inductor or
switches, protecting these components
and the load against short circuits and
pre-biased outputs during start-up.
To avoid these difficulties, a typical
voltage mode controller requires ad­ditional circuitry to monitor current in
the power stage. The LTC3775 requires
no ancillary circuits to oversee the
entire switching cycle.

The current limit is programmed
with two resistors (as shown in the
block diagram of Figure 2), corre

­sponding to the current measured
through the top and bottom switches

Linear Technology Magazine • December 2009

during their respective on times. This

V

OUT(AC)

RIPPLE

20mV/DIV

V

SW

10V/DIV

I

L

10A/DIV

1µs/DIVVIN = 26V

V

OUT

= 1.2V
NO LOAD
R

SET

= 38.3k

V

OUT(AC)

100mV/DIV

V

SW

20V/DIV

I

L

10A/DIV

I

LOAD

10A/DIV

5µs/DIVV

IN

= 12V

V

OUT

= 1.2V
LOAD STEP = 0A TO 10A
MODE/SYNC = 0V
SW FREQ = 500kHz

I

L

20A/DIV

V

SS

1V/DIV

20µs/DIVV

IN

= 12V

V

OUT

= 1.2V

C

SS

= 0.01µF

0A LOAD

+

+
–

100µA

R

ILIMB

(OPT)

10µA

t7

ILIMB

R

ILIMT

7

IN

LTC3775

R

SENSE

SENSE

CTLIM

TURN OFF TG

+

–

CBLIM

EXTEND BG

I

LIMB

SW

I

LIMT

TG Q

T

7

IN

BG Q

B

7

OUT

PGND

SGND

arrangement allows cycle-by-cycle
current limit, regardless of the duty
cycle, and ensures that the inductor
is not saturated.

In a current mode converter, the
voltage on the output of the error
amplifier controls the peak switch
current, such that the switch current
must always be monitored, allowing
the introduction of noise. This may be
most pronounced around 50% duty
cycle in some current mode designs.
Contrast this with a voltage mode
converter, where the error voltage
on V

is compared to a saw-tooth

OUT

ramp, which in turn controls duty
cycle; the larger the error voltage, the
longer the top switch stays on. The
LTC3775 senses current through both
MOSFETs to assure that they do not
exceed programmed limits. During
normal operation, these limits do not
come into play, and noise-free opera­tion is assured.

A high side current limit would be of
little value if the circuit was operated
at its maximum VIN, since the bottom
switch would be on most of the time,
and nothing would protect the syn­chronous MOSFET. Fortunately, the
low side current limit, programmed by
I

, can limit the current through

LIMB

the bottom switch. Conversely, a fault
at low VIN during the on-time of the
top switch requires a high side cur­rent limit for immediate response. The
LTC3775 uses both top- and bottom­side current limit circuits to provide

DESIGN FEATURES L

Figure 2. The LTC3775 features high and low side programmable current limits, for cycle-by-cycle
short circuit protection.

optimum protection for the MOSFETs
and inductor.

This current limit approach is ef­fective, as shown by the short circuit
behavior in Figure 3. A hard short
could spell disaster for an unprotected
voltage mode converter. But here, the
inductor does not saturate, and the
input rail maintains its integrity while
the output gracefully drops.

Output voltage is monitored using
an inverting summing amplifier topol­ogy, with the FB pin configured as a
virtual ground. The reference voltage
is accurate to within ±0.75% over
temperature. The LTC3775 uses a true
operational error amplifier with 80dB
of open loop gain, and a 25MHz gain­bandwidth product. Feedback gain
can be tightly controlled by external
components, allowing the use of “Type
3” compensation, which provides a
phase boost at the LC double pole
frequency and significantly improves

control loop phase margin. Figure 4
shows a characteristically fast load
transient response.

The modulator consists of the
PWM generator, the output MOSFET
drivers and the external MOSFETs
themselves. The modulator gain var­ies linearly with the input voltage. The
line feedforward circuit compensates
for this change in gain, and provides a
constant gain from the error amplifier
output to the inductor input regardless
of input voltage.

The application in Figure 1 de

­mands a minimum on time of just
86ns at the maximum input voltage
of 28V. Many controllers turn the top
gate on at the beginning of the clock
cycle and must wait for the response
time of the PWM comparator before
turning off the top gate. This response
time is typically around 100ns or more.
In addition, those controllers would
make the decision at a noisy interval,

Figure 3. Short circuit behavior for the
converter of Figure 1

Linear Technology Magazine • December 2009

Figure 4. Load transient response for the
converter of Figure 1

Figure 5. The converter of Figure 1
demonstrates a clean switching waveform
with a razor-thin on-time.

21

L DESIGN FEATURES

LOAD CURRENT (A)

30

EFFICIENCY (%)

POWER LOSS (W)

90

100

20

10

80

50

70

60

40

0.01 1 10

0

1.0

2.5

0.5

2.0

1.5

0

0.1

EFFICIENCY

POWER LOSS

VIN = 24V
V

OUT

= 12V
CONTINUOUS MODE
SW FREQ = 500kHz

C

B

0.1µF

L1

4.7µH

C

OUT

68µF
16V
×2

C

IN1

330µF
35V

V

IN

24V

V

OUT

12V
5A

C

VCC

4.7µF

C2

330pF

C1

3.3nF

R

ILIMB

56.2k

R

SET

39.2k

R2

7.68k

R

B

10k

C

OUT

: SANYO 16TQC68M

D

B

: CMDSH4E
L1: IHLP-4040DZ-ER-4R7-M11
Q

B

, Q

T

: RJK0305DPB-00-JO

R

A

191k

R3

2.05k

C3
330pF

R

ILIMT

1.24k

R4

69.8k

R5
10k

D

B

C

SS

0.01µF

TG Q

T

Q

B

V

IN

LTC3775

SGND

SENSE

I

LIMT

I

LIMB

INTV

CC

SS

BG

PGND

MODE/SYNC

COMP

BOOST

SW

FREQ

RUN/SHDN
FB

+

+

Figure 6. A 12V, 5A converter operating at 500kHz from 24VIN.

because ringing persists for some time
after the top gate turns on. Thus even
though the minimum on-time could
be as low as 100ns, practical design
considerations such as noise and jitter
would require a nominal on-time of
no less than 150ns to guarantee that
there will be no pulse-skipping mode
at maximum input voltage.

The LTC3775’s leading-edge volt­age mode architecture and very low
minimum on-time of 30ns makes it
practical to run with on-times as low
as 40ns, even in noisy environments.
The LTC3775’s leading edge modula­tion architecture turns on the top

22

Figure 7. Efficiency for the
converter of Figure 6

gate when the PWM comparator trips
and turns off the top gate when the
clock signal goes high. The switching
waveform shows no skipped pulses
and is free from erratic behavior, even
with very short on-times. Figure 5 il
lustrates waveforms for a 36V input,

1.2V output converter operating in
continuous conduction mode (CCM)
at 350kHz with no load. The waveform
shows constant frequency operation
and extremely low switch node jitter.

A 12V Converter Operating
from 24VIN at 500kHz

Because the LTC3775 separately
monitors the current through the top
and bottom switches, its comparators
do not need extended common mode
ranges. Some current mode convert­ers use a sense resistor in series with
the inductor, restricting the range of
V
of their current comparators. Without
this restriction, the LTC3775 is useful
for powering higher output voltages,
as exemplified by the 12V converter of
Figure 6. Also, the absence of a sense
resistor means no loss in efficiency,
and no low amplitude current mode
sense signal which can be a source of
jitter in the SW node waveform.

due to the common mode range

OUT

Current sensing through the top
MOSFET can be measured across a
sense resistor for the highest possible
accuracy. To boost efficiency and save
a component, just omit the sense re­sistor and measure directly across the
top MOSFET. Figure 6 demonstrates
a high efficiency 12V converter that
uses this arrangement. When using
the top MOSFET R

DS(ON)

to measure
current, care must be taken to Kelvin­connect the VIN pin of the IC to the
drain terminal of the power MOSFET
and the SENSE pin to the source of
the MOSFET. Likewise, when a sense
resistor is used for improved current
limit accuracy, Kelvin-connect the
VIN and SENSE pins of the IC to the
positive and negative terminals of the
sense resistor, respectively.

The circuits featured here operate in
forced continuous mode, for constant
frequency operation at any load. If
higher light-load efficiency is desired,
the MODE/SYNC pin can be tied to a
voltage above 1.2V (typically INTVCC)
for pulse skippin operation. This pin
can also be the input for a sync signal,
from 250kHz to 1MHz. No external PLL
components are required for syncing.
The synchronization feature operates

­within ±20% of the free-running fre­quency defined by R

SET

.

Conclusion

The LTC3775 provides unprecedented
performance for today’s demanding
high current, low voltage power sup­ply systems. With a minimum on-time
of 30ns and a high bandwidth true
operational amplifier, the control­ler can operate at frequencies up to
1MHz, maintaining a very small power
supply PCB footprint and reducing
output ripple.

The LTC3775 offers numerous
features in a tiny 3mm × 3mm QFN,
including cycle-by-cycle current
limit, synchronization capability over a
±20% range, a wide input and output
operating voltage range, internal line
feed-forward compensation, a high
bandwidth operational error amplifier,
strong internal gate drivers and very
tight output voltage tolerance (±0.75%
over temperature).

Linear Technology Magazine • December 2009

L