Datasheet LM6172AMJRQML, LM6172AMJ-QMLV, LM6172AMJ-MLS, LM6172IN, LM6172IMX Datasheet (NSC)
...Page 1
LM6172
Dual High Speed, Low Power, Low Distortion, Voltage
Feedback Amplifiers
General Description
The LM6172 is a dual high speed voltage feedback amplifier.
It is unity-gain stable and provides excellent DC and AC performance. With 100 MHz unity-gain bandwidth, 3000V/µs
slew rate and 50 mA of output current per channel, the
LM6172 offers high performance in dual amplifiers; yet it
only consumes 2.3 mA of supply current each channel.
The LM6172 operates on
±
15V power supply for systems
requiring large voltage swings, such as ADSL, scanners and
ultrasound equipment. It is also specified at
±
5V power supply for low voltage applications such as portable video systems.
The LM6172 is built with National’s advanced VIP
™
III (Vertically Integrated PNP) complementary bipolar process. See
the LM6171 datasheet for a single amplifier with these same
features.
Features
(Typical Unless Otherwise Noted)
n Easy to Use Voltage Feedback Topology
n High Slew Rate 3000V/µs
n Wide Unity-Gain Bandwidth 100 MHz
n Low Supply Current 2.3 mA/Channel
n High Output Current 50 mA/channel
n Specified for
±
15V and±5V Operation
Applications
n Scanner I-to-V Converters
n ADSL/HDSL Drivers
n Multimedia Broadcast Systems
n Video Amplifiers
n NTSC, PAL
®
and SECAM Systems
n ADC/DAC Buffers
n Pulse Amplifiers and Peak Detectors
LM6172 Driving Capacitive Load
Connection Diagram
VIP™is a trademark ofNational Semiconductor Corporation.
PAL
®
is a registered trademark of and used under license from Advanced Micro Devices, Inc.
DS012581-50
DS012581-44
8-Pin DIP/SO
DS012581-1
Top View
May 1999
LM6172 Dual High Speed, Low Power, Low Distortion, Voltage Feedback Amplifiers
© 1999 National Semiconductor Corporation DS012581 www.national.com
Page 2
Ordering Information
Package Temperature Range Transport
Media
NSC
Drawing
Industrial Military
−40˚C to +85˚C −55˚C to +125˚C
8-Pin DIP LM6172IN Rails N08E
8-Pin CDIP LM6172AMJ-QML 5962-95604 Rails J08A
10-Pin Ceramic
SOIC
LM6172AMWG-QML 5962-95604 Trays WG10A
8-Pin LM6172IM Rails M08A
Small Outline
LM6172IMX Tape and Reel
www.national.com 2
Page 3
Absolute Maximum Ratings (Note 1)
If Military/Aerospace specified devices are required,
please contact the National Semiconductor Sales Office/
Distributors for availability and specifications.
ESD Tolerance (Note 2)
Human Body Model 3 kV
Machine Model 300V
Supply Voltage (V
+−V−
) 36V
Differential Input Voltage (Note 9)
±
10V
Output Short Circuit to Ground
(Note 3) Continuous
Storage Temp. Range −65˚C to +150˚C
Maximum Junction Temperature
(Note 4) 150˚C
Operating Ratings(Note 1)
Supply Voltage 5.5V ≤ V
S
≤ 36V
Junction Temperature Range
LM6172I −40˚C ≤ T
J
≤ +85˚C
Thermal Resistance (θ
JA
)
N Package, 8-Pin Molded DIP 95˚C/W
M Package, 8-Pin Surface Mount 160˚C/W
±
15V DC Electrical Characteristics
Unless otherwise specified, all limits guaranteed for T
J
=
25˚C,V
+
=
+15V, V
−
=
−15V, V
CM
=
0V, and R
L
=
1kΩ.Boldface
limits apply at the temperature extremes
Typ
(Note 5)
LM6172I
Symbol Parameter Conditions Limit Units
(Note 5)
V
OS
Input Offset Voltage 0.4 3 mV
4 max
TC V
OS
Input Offset Voltage 6 µV/˚C
Average Drift
I
B
Input Bias Current 1.2 3 µA
4 max
I
OS
Input Offset Current 0.02 2 µA
3 max
R
IN
Input Resistance Common Mode 40 MΩ
Differential Mode 4.9
R
O
Open Loop Output Resistance 14 Ω
CMRR Common Mode Rejection Ratio V
CM
=
±
10V 110 70 dB
65 min
PSRR Power Supply Rejection Ratio V
S
=
±
15V to±5V 95 75 dB
70 min
A
V
Large Signal Voltage R
L
=
1kΩ 86 80 dB
Gain (Note 6) 75 min
R
L
=
100Ω 78 65 dB
60 min
V
O
Output Swing R
L
=
1kΩ 13.2 12.5 V
12 min
−13.1 −12.5 V
−12 max
R
L
=
100Ω 96V
5min
−8.5 −6 V
−5 max
Continuous Output Current Sourcing, R
L
=
100Ω 90 60 mA
(Open Loop) (Note 7) 50 min
Sinking, R
L
=
100Ω −85 −60 mA
−50 max
I
SC
Output Short Circuit Sourcing 107 mA
Current Sinking −105 mA
I
S
Supply Current Both Amplifiers 4.6 8 mA
www.national.com3
Page 4
±
15V DC Electrical Characteristics (Continued)
Unless otherwise specified, all limits guaranteed for T
J
=
25˚C,V
+
=
+15V, V
−
=
−15V, V
CM
=
0V, and R
L
=
1kΩ.Boldface
limits apply at the temperature extremes
Typ
(Note 5)
LM6172I
Symbol Parameter Conditions Limit Units
(Note 5)
9 max
±
15V AC Electrical Characteristics
Unless otherwise specified, T
J
=
25˚C, V
+
=
+15V, V
−
=
−15V, V
CM
=
0V, and R
L
=
1kΩ
LM6172I
Symbol Parameter Conditions Typ Units
(Note 5)
SR Slew Rate A
V
=
+2, V
IN
=
13 V
PP
3000 V/µs
A
V
=
+2, V
IN
=
10 V
PP
2500 V/µs
Unity-Gain Bandwidth 100 MHz
−3 dB Frequency A
V
=
+1 160 MHz
A
V
=
+2 62 MHz
Bandwidth Matching between Channels 2 MHz
φ
m
Phase Margin 40 Deg
t
s
Settling Time (0.1%)A
V
=
−1, V
OUT
=
±
5V, 65 ns
R
L
=
500Ω
A
D
Differential Gain (Note 8) 0.28
%
φ
D
Differential Phase (Note 8) 0.6 Deg
e
n
Input-Referred f=1 kHz
12
Voltage Noise
i
n
Input-Referred f=1 kHz
1
Current Noise
Second Harmonic f=10 kHz −110 dB
Distortion (Note 10) f=5 MHz −50 dB
Third Harmonic f=10 kHz −105 dB
Distortion (Note 10) f=5 MHz −50 dB
±
5V DC Electrical Characteristics
Unless otherwise specified, all limits guaranteed for T
J
=
25˚C, V
+
=
+5V, V
−
=
−5V, V
CM
=
0V, and R
L
=
1kΩ.Boldface
limits apply at the temperature extremes
Typ
(Note 5)
LM6172I
Symbol Parameter Conditions Limit Units
(Note 5)
V
OS
Input Offset Voltage 0.1 3 mV
4 max
TC V
OS
Input Offset Voltage 4 µV/˚C
Average Drift
I
B
Input Bias Current 1.4 2.5 µA
3.5 max
I
OS
Input Offset Current 0.02 1.5 µA
2.2 max
R
IN
Input Resistance Common Mode 40 MΩ
Differential Mode 4.9
R
O
Output Resistance 14 Ω
CMRR Common Mode Rejection Ratio V
CM
=
±
2.5V 105 70 dB
www.national.com 4
Page 5
±
5V DC Electrical Characteristics (Continued)
Unless otherwise specified, all limits guaranteed for T
J
=
25˚C, V
+
=
+5V, V
−
=
−5V, V
CM
=
0V, and R
L
=
1kΩ.Boldface
limits apply at the temperature extremes
Typ
(Note 5)
LM6172I
Symbol Parameter Conditions Limit Units
(Note 5)
65 min
PSRR Power Supply Rejection Ratio V
S
=
±
15V to±5V 95 75 dB
70 min
A
V
Large Signal Voltage R
L
=
1kΩ 82 70 dB
Gain (Note 6) 65 min
R
L
=
100Ω 78 65 dB
60 min
V
O
Output Swing R
L
=
1kΩ 3.4 3.1 V
3 min
−3.3 −3.1 V
−3 max
R
L
=
100Ω 2.9 2.5 V
2.4 min
−2.7 −2.4 V
−2.3 max
Continuous Output Current Sourcing, R
L
=
100Ω 29 25 mA
(Open Loop) (Note 7) 24 min
Sinking, R
L
=
100Ω −27 −24 mA
−23 max
I
SC
Output Short Circuit Sourcing 93 mA
Current Sinking −72 mA
I
S
Supply Current Both Amplifiers 4.4 6 mA
7 max
±
5V AC Electrical Characteristics
Unless otherwise specified, T
J
=
25˚C, V
+
=
+5V, V
−
=
−5V, V
CM
=
0V, and R
L
=
1kΩ.
LM61722
Typ
(Note 5)
Symbol Parameter Conditions Units
SR Slew Rate A
V
=
+2, V
IN
=
3.5 V
PP
750 V/µs
Unity-Gain Bandwidth 70 MHz
−3 dB Frequency A
V
=
+1 130 MHz
A
V
=
+2 45 MHz
φ
m
Phase Margin 57 Deg
t
s
Settling Time (0.1%)A
V
=
−1, V
OUT
=
±
1V, 72 ns
R
L
=
500Ω
A
D
Differential Gain (Note 8) 0.4
%
φ
D
Differential Phase (Note 8) 0.7 Deg
e
n
Input-Referred f=1 kHz
11
Voltage Noise
i
n
Input-Referred f=1 kHz
1
Current Noise
Second Harmonic f=10 kHz −110 dB
Distortion (Note 10) f=5 MHz −48 dB
Third Harmonic f=10 kHz −105 dB
www.national.com5
Page 6
±
5V AC Electrical Characteristics (Continued)
Unless otherwise specified, T
J
=
25˚C, V
+
=
+5V, V
−
=
−5V, V
CM
=
0V, and R
L
=
1kΩ.
LM61722
Typ
(Note 5)
Symbol Parameter Conditions Units
Distortion (Note 10) f=5 MHz −50 dB
Note 1: Absolute Maximum Ratings indicate limits beyond which damage to the device may occur. Operating Ratings indicate conditions for which the device is intended to be functional, but specific performance is not guaranteed. For guaranteed specifications and the test conditions, see the Electrical Characteristics.
Note 2: Human body model, 1.5 kΩ in series with 100 pF. Machine Model, 200Ω in series with 100 pF.
Note 3: Continuous short circuit operation can result in exceeding the maximum allowed junction temperature of 150˚C.
Note 4: The maximum power dissipation is a function of T
J(max)
, θJA, and TA. The maximum allowable power dissipation at any ambient temperature is
P
D
=
(T
J(max)−TA
)/θJA. All numbers apply for packages soldered directly into a PC board.
Note 5: Typical Values represent the most likely parametric norm.
Note 6: All limits are guaranteed by testing or statistical analysis.
Note 7: Large signal voltage gain is the total output swing divided by the input signal required to produce that swing. For V
S
=
±
15V, V
OUT
=
±
5V. For V
S
=
±
5V,
V
OUT
=
±
1V.
Note 8: The open loop output current is the output swing with the 100Ω load resistor divided by that resistor.
Note 9: Differential gain and phase are measured with A
V
=
+2, V
IN
=
1V
PP
at 3.58 MHz and both input and output 75Ω terminated.
Note 10: Differential input voltage is applied at V
S
=
±
15V.
Note 11: Harmonics are measured with A
V
=
+2, V
IN
=
1V
PP
and R
L
=
100Ω.
Typical Performance Characteristics unless otherwise noted, T
A
=
25˚C
Supply Voltage vs
Supply Current
DS012581-14
Supply Current vs
Temperature
DS012581-15
Input Offset Voltage
vs Temperature
DS012581-16
Input Bias Current vs
Temperature
DS012581-17
Short Circuit Current vs
Temperature (Sourcing)
DS012581-18
Short Circuit Current vs
Temperature (Sinking)
DS012581-35
www.national.com 6
Page 7
Typical Performance Characteristics unless otherwise noted, T
A
=
25˚C (Continued)
Output Voltage vs
Output Current
(V
S
=
±
15V)
DS012581-36
Output Voltage vs
Output Current
(V
S
=
±
5V)
DS012581-37
CMRR vs Frequency
DS012581-19
PSRR vs Frequency
DS012581-20
PSRR vs Frequency
DS012581-33
Open-Loop Frequency
Response
DS012581-21
Open-Loop Frequency
Response
DS012581-22
Gain-Bandwidth Product
vs Supply Voltage
at Different Temperature
DS012581-23
Large Signal Voltage
Gain vs Load
DS012581-38
www.national.com7
Page 8
Typical Performance Characteristics unless otherwise noted, T
A
=
25˚C (Continued)
Large Signal Voltage
Gain vs Load
DS012581-39
Input Voltage Noise
vs Frequency
DS012581-40
Input Voltage Noise
vs Frequency
DS012581-41
Input Current Noise
vs Frequency
DS012581-42
Input Current Noise
vs Frequency
DS012581-43
Slew Rate vs
Supply Voltage
DS012581-25
Slew Rate vs
Input Voltage
DS012581-26
Large Signal Pulse Response
A
V
=
+1, V
S
=
±
15V
DS012581-2
Small Signal Pulse Response
A
V
=
+1, V
S
=
±
15V
DS012581-3
Large Signal Pulse Response
A
V
=
+1, V
S
=
±
5V
DS012581-4
Small Signal Pulse Response
A
V
=
+1, V
S
=
±
5V
DS012581-5
www.national.com 8
Page 9
Typical Performance Characteristics unless otherwise noted, T
A
=
25˚C (Continued)
Large Signal Pulse Response
A
V
=
+2, V
S
=
±
15V
DS012581-6
Small Signal Pulse Response
A
V
=
+2, V
S
=
±
15V
DS012581-7
Large Signal Pulse Response
A
V
=
+2, V
S
=
±
5V
DS012581-8
Small Signal Pulse Response
A
V
=
+2, V
S
=
±
5V
DS012581-9
Large Signal Pulse Response
A
V
=
−1, V
S
=
±
15V
DS012581-10
Small Signal Pulse Response
A
V
=
−1, V
S
=
±
15V
DS012581-11
Large Signal Pulse Response
A
V
=
−1, V
S
=
±
5V
DS012581-12
Small Signal Pulse Response
A
V
=
−1, V
S
=
±
5V
DS012581-13
Closed Loop Frequency
Response vs Supply Voltage
(A
V
=
+1)
DS012581-28
www.national.com9
Page 10
Typical Performance Characteristics unless otherwise noted, T
A
=
25˚C (Continued)
Closed Loop Frequency
Response vs Supply Voltage
(A
V
=
+2)
DS012581-29
Harmonic Distortion
vs Frequency
(V
S
=
±
15V)
DS012581-30
Harmonic Distortion
vs Frequency
(V
S
=
±
5V)
DS012581-34
Crosstalk Rejection vs
Frequency
DS012581-31
Maximum Power Dissipation
vs Ambient Temperature
DS012581-32
www.national.com 10
Page 11
1
⁄2LM6172 Simplified Schematic
Application Notes
LM6172 Performance Discussion
The LM6172 is a dual high-speed, low power, voltage feedback amplifier. It is unity-gain stable and offers outstanding
performance with only 2.3 mA of supply current per channel.
The combination of 100 MHz unity-gain bandwidth,
3000V/µs slew rate, 50 mA per channel output current and
other attractive features makes it easy to implement the
LM6172 in various applications. Quiescent power of the
LM6172 is 138 mW operating at
±
15V supply and 46 mW at
±
5V supply.
LM6172 Circuit Operation
The class AB input stage in LM6172 is fully symmetrical and
has a similar slewing characteristic to the current feedback
amplifiers. In the LM6172 Simplified Schematic, Q1 through
Q4 form the equivalent of the current feedback input buffer,
R
E
the equivalent of the feedback resistor, and stage A buffers the inverting input. The triple-buffered output stage isolates the gain stage from the load to provide low output impedance.
LM6172 Slew Rate Characteristic
The slew rate of LM6172 is determined by the current available to charge and discharge an internal high impedance
node capacitor. This current is the differential input voltage
divided by the total degeneration resistor R
E
. Therefore, the
slew rate is proportional to the input voltage level, and the
higher slew rates are achievable in the lower gain configurations.
When a very fast large signal pulse is applied to the input of
an amplifier, some overshoot or undershoot occurs. By placing an external series resistor such as 1 kΩ to the input of
LM6172, the slew rate is reduced to help lower the overshoot, which reduces settling time.
Reducing Settling Time
The LM6172 has a very fast slew rate that causes overshoot
and undershoot. To reduce settling time on LM6172,a1kΩ
resistor can be placed in series with the input signal to decrease slew rate. A feedback capacitor can also be used to
reduce overshoot and undershoot. This feedback capacitor
serves as a zero to increase the stability of the amplifier circuit. A 2 pF feedback capacitor is recommended for initial
evaluation. When the LM6172 is configured as a buffer, a
feedback resistor of 1 kΩ must be added in parallel to the
feedback capacitor.
Another possible source of overshoot and undershoot
comes from capacitive load at the output. Please see the
section “Driving Capacitive Loads” for more detail.
Driving Capacitive Loads
Amplifiers driving capacitive loads can oscillate or have ringing at the output. To eliminate oscillation or reduce ringing,
an isolation resistor can be placed as shown in
Figure 1
. The
combination of the isolation resistor and the load capacitor
forms a pole to increase stability by adding more phase margin to the overall system. The desired performance depends
on the value of the isolation resistor; the bigger the isolation
resistor, the more damped (slow) the pulse response becomes. For LM6172, a 50Ω isolation resistor is recommended for initial evaluation.
DS012581-55
www.national.com11
Page 12
Driving Capacitive Loads (Continued)
Layout Consideration
PRINTED CIRCUIT BOARDS AND HIGH SPEED OP
AMPS
There are many things to consider when designing PC
boards for high speed op amps. Without proper caution, it is
very easy to have excessive ringing, oscillation and other degraded AC performance in high speed circuits. As a rule, the
signal traces should be short and wide to provide low inductance and low impedance paths. Any unused board space
needs to be grounded to reduce stray signal pickup. Critical
components should also be grounded at a common point to
eliminate voltage drop. Sockets add capacitance to the
board and can affect frequency performance. It is better to
solder the amplifier directly into the PC board without using
any socket.
USING PROBES
Active (FET) probes are ideal for taking high frequency measurements because they have wide bandwidth, high input
impedance and low input capacitance. However, the probe
ground leads provide a long ground loop that will produce errors in measurement. Instead, the probes can be grounded
directly by removing the ground leads and probe jackets and
using scope probe jacks.
COMPONENTS SELECTION AND FEEDBACK
RESISTOR
It is important in high speed applications to keep all component leads short because wires are inductive at high frequency. For discrete components, choose carbon
composition-type resistors and mica-type capacitors. Surface mount components are preferred over discrete components for minimum inductive effect.
Large values of feedback resistors can couple with parasitic
capacitance and cause undesirable effects such as ringing
or oscillation in high speed amplifiers. For LM6172, a feedback resistor less than 1 kΩ gives optimal performance.
Compensation for Input
Capacitance
The combination of an amplifier’s input capacitance with the
gain setting resistors adds a pole that can cause peaking or
oscillation. To solve this problem, a feedback capacitor with
a value
C
F
>
(RGxCIN)/R
F
can be used to cancel that pole. For LM6172, a feedback capacitor of 2 pF is recommended.
Figure 4
illustrates the com-
pensation circuit.
Power Supply Bypassing
Bypassing the power supply is necessary to maintain low
power supply impedance across frequency. Both positive
and negative power supplies should be bypassed individually by placing 0.01 µF ceramic capacitors directly to power
supply pins and 2.2 µF tantalum capacitors close to the
power supply pins.
DS012581-45
FIGURE 1. Isolation Resistor Used
to Drive Capacitive Load
DS012581-51
FIGURE 2. The LM6172 Driving a 510 pF Load
with a 30Ω Isolation Resistor
DS012581-52
FIGURE 3. The LM6172 Driving a 220 pF Load
with a 50Ω Isolation Resistor
DS012581-46
FIGURE 4. Compensating for Input Capacitance
www.national.com 12
Page 13
Power Supply Bypassing (Continued)
Termination
In high frequency applications, reflections occur if signals
are not properly terminated.
Figure 6
shows a properly termi-
nated signal while
Figure 7
shows an improperly terminated
signal.
To minimize reflection, coaxial cable with matching characteristic impedance to the signal source should be used. The
other end of the cable should be terminated with the same
value terminator or resistor. For the commonly used cables,
RG59 has 75Ω characteristic impedance, and RG58 has
50Ω characteristic impedance.
Power Dissipation
The maximum power allowed to dissipate in a device is defined as:
P
D
=
(T
J(max)−TA
)/θ
JA
Where PDis the power dissipation in a device
T
J(max)
is the maximum junction temperature
T
A
is the ambient temperature
θ
JA
is the thermal resistance of a particular package
For example, for the LM6172 in a SO-8 package, the maximum power dissipation at 25˚C ambient temperature is
780 mW.
Thermal resistance, θ
JA
, depends on parameters such as
die size, package size and package material. The smaller
the die size and package, the higher θ
JA
becomes. The 8-pin
DIP package has a lower thermal resistance (95˚C/W) than
that of 8-pin SO (160˚C/W). Therefore, for higher dissipation
capability, use an 8-pin DIP package.
The total power dissipated in a device can be calculated as:
P
D
=
P
Q+PL
PQis the quiescent power dissipated in a device with no load
connected at the output. P
L
is the power dissipated in the device with a load connected at the output; it is not the power
dissipated by the load.
Furthermore,
P
Q
:
=
supply current x total supply voltage with no load
P
L
:
=
output current x (voltage difference between supply voltage and output voltage of the same supply)
For example, the total power dissipated by the LM6172 with
V
S
=
±
15V and both channels swinging output voltage of
10V into 1 kΩ is
P
D
:=PQ+P
L
:
=
2[(2.3 mA)(30V)] + 2[(10 mA)(15V − 10V)]
:
=
138 mW + 100 mW
:
=
238 mW
DS012581-47
FIGURE 5. Power Supply Bypassing
DS012581-53
FIGURE 6. Properly Terminated Signal
DS012581-54
FIGURE 7. Improperly Terminated Signal
www.national.com13
Page 14
Application Circuits
I-to-V Converters
DS012581-48
Differential Line Driver
DS012581-49
www.national.com 14
Page 15
Physical Dimensions inches (millimeters) unless otherwise noted
8-Lead Ceramic Dual-In-Line Package
Order Number LM6172AMJ-QML or 5962-9560401QPA
NS Package Number J08A
8-Lead (0.150" Wide) Molded Small Outline Package, JEDEC
Order Number LM6172IM or LM6172IMX
NS Package Number M08A
www.national.com15
Page 16
Physical Dimensions inches (millimeters) unless otherwise noted (Continued)
LIFE SUPPORT POLICY
NATIONAL’S PRODUCTS ARE NOT AUTHORIZED FOR USE AS CRITICAL COMPONENTS IN LIFE SUPPORT
DEVICES OR SYSTEMS WITHOUT THE EXPRESS WRITTEN APPROVAL OF THE PRESIDENT AND GENERAL
COUNSEL OF NATIONAL SEMICONDUCTOR CORPORATION. As used herein:
1. Life support devices or systems are devices or
systems which, (a) are intended for surgical implant
into the body, or (b) support or sustain life, and
whose failure to perform when properly used in
accordance with instructions for use provided in the
labeling, can be reasonably expected to result in a
significant injury to the user.
2. A critical component is any component of a life
support device or system whose failure to perform
can be reasonably expected to cause the failure of
the life support device or system, or to affect its
safety or effectiveness.
National Semiconductor
Corporation
Americas
Tel: 1-800-272-9959
Fax: 1-800-737-7018
Email: support@nsc.com
National Semiconductor
Europe
Fax: +49 (0) 1 80-530 85 86
Email: europe.support@nsc.com
Deutsch Tel: +49 (0) 1 80-530 85 85
English Tel: +49 (0) 1 80-532 78 32
Français Tel: +49 (0) 1 80-532 93 58
Italiano Tel: +49 (0) 1 80-534 16 80
National Semiconductor
Asia Pacific Customer
Response Group
Tel: 65-2544466
Fax: 65-2504466
Email: sea.support@nsc.com
National Semiconductor
Japan Ltd.
Tel: 81-3-5639-7560
Fax: 81-3-5639-7507
www.national.com
8-Lead (0.300" Wide) Molded Dual-In-Line Package
Order Number LM6172IN
NS Package Number N08E
LM6172 Dual High Speed, Low Power, Low Distortion, Voltage Feedback Amplifiers
National does not assume any responsibility for use of any circuitry described, no circuit patent licenses are implied and National reserves the right at any time without notice to change said circuitry and specifications.
Loading...