LM6171
High Speed Low Power Low Distortion Voltage Feedback
Amplifier
General Description
The LM6171 is a high speed unity-gain stable voltage feedback amplifier. It offers a high slew rate of 3600V/µs and a
unity-gain bandwidth of 100 MHz while consuming only 2.5
mA of supply current. The LM6171 has very impressive AC
and DC performance which is a great benefit for high speed
signal processing and video applications.
The
±
15V power supplies allow for large signal swings and
give greater dynamic range and signal-to-noise ratio. The
LM6171 has high output current drive, low SFDR and THD,
ideal for ADC/DAC systems. The LM6171 is specified for
±
5V operation for portable applications.
The LM6171 is built on National’s advanced VIP
™
III (Verti-
cally Integrated PNP) complementary bipolar process.
Features
(Typical Unless Otherwise Noted)
n Easy-To-Use Voltage Feedback Topology
n Very High Slew Rate: 3600V/µs
n Wide Unity-Gain-Bandwidth Product: 100 MHz
n −3 dB Frequency
@
A
V
=
+2: 62 MHz
n Low Supply Current: 2.5 mA
n High CMRR: 110 dB
n High Open Loop Gain: 90 dB
n Specified for
±
15V and±5V Operation
Applications
n Multimedia Broadcast Systems
n Line Drivers, Switchers
n Video Amplifiers
n NTSC, PAL
®
and SECAM Systems
n ADC/DAC Buffers
n HDTV Amplifiers
n Pulse Amplifiers and Peak Detectors
n Instrumentation Amplifier
n Active Filters
Typical Performance Characteristics
VIP™is a trademark of National Semiconductor Corporation.
PAL
®
is a registered trademark of and used under licence from Advanced Micro Devices, Inc.
Closed Loop Frequency Response
vs Supply Voltage (A
V
=
+1)
DS012336-5
Large Signal
Pulse Response
A
V
=
+1, V
S
=
±
15
DS012336-9
May 1998
LM6171 High Speed Low Power Low Distortion Voltage Feedback Amplifier
© 1999 National Semiconductor Corporation DS012336 www.national.com
Connection Diagram
Ordering Information
Package Temperature Range Transport
Media
NSC
Drawing
Industrial
−40˚C to +85˚C
8-Pin LM6171AIN Rails N08E
Molded DIP LM6171BIN
8-Pin LM6171AIM, LM6171BIM Rails M08A
Small Outline LM6171AIMX, LM6171BIMX Tape and Reel
8-Pin DIP/SO
DS012336-1
Top View
www.national.com 2
Absolute Maximum Ratings (Note 1)
If Military/Aerospace specified devices are required,
please contact the National Semiconductor Sales Office/
Distributors for availability and specifications.
ESD Tolerance (Note 2) 2.5 kV
Supply Voltage (V
+–V−
) 36V
Differential Input Voltage
(Note 11)
±
10V
Common-Mode
Voltage Range V
+
−1.4V to V−+ 1.4V
Output Short Circuit to Ground
(Note 3) Continuous
Storage Temperature Range −65˚C to +150˚C
Maximum Junction Temperature
(Note 4) 150˚C
Operating Ratings (Note 1)
Supply Voltage 2.75V ≤ V
+
≤ 18V
Junction Temperature Range
LM6171AI, LM6171BI −40˚C ≤ T
J
≤ +85˚C
Thermal Resistance (θ
JA
)
N Package, 8-Pin Molded DIP 108˚C/W
M Package, 8-Pin Surface Mount 172˚C/W
±
15V DC Electrical Characteristics
Unless otherwise specified, all limits guaranteed for T
J
=
25˚C, V
+
=
+15V, V
−
=
−15V, V
CM
=
0V, and R
L
=
1kΩ.Boldface
limits apply at the temperature extremes
Typ LM6171AI LM6171BI
Symbol Parameter Conditions (Note 5) Limit Limit Units
(Note 6) (Note 6)
V
OS
Input Offset Voltage 1.5 3 6 mV
58max
TC V
OS
Input Offset Voltage Average Drift 6 µV/˚C
I
B
Input Bias Current 1 3 3 µA
44max
I
OS
Input Offset Current 0.03 2 2 µA
33max
R
IN
Input Resistance Common Mode 40 MΩ
Differential Mode 4.9
R
O
Open Loop 14 Ω
Output Resistance
CMRR Common Mode V
CM
=
±
10V 110 80 75 dB
Rejection Ratio 75 70 min
PSRR Power Supply V
S
=
±
15V to±5V 95 85 80 dB
Rejection Ratio 80 75 min
V
CM
Input Common-Mode CMRR ≥ 60 dB
±
13.5 V
Voltage Range
A
V
Large Signal Voltage R
L
=
1kΩ 90 80 80 dB
Gain (Note 7) 70 70 min
R
L
=
100Ω 83 70 70 dB
60 60 min
V
O
Output Swing R
L
=
1kΩ 13.3 12.5 12.5 V
12 12 min
−13.3 −12.5 −12.5 V
−12 −12 max
R
L
=
100Ω 11.6 9 9 V
8.5 8.5 min
−10.5 −9 −9 V
−8.5 −8.5 max
Continuous Output Current Sourcing, R
L
=
100Ω 116 90 90 mA
(Open Loop) (Note 8) 85 85 min
Sinking, R
L
=
100Ω 105 90 90 mA
85 85 max
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±
15V DC Electrical Characteristics (Continued)
Unless otherwise specified, all limits guaranteed for T
J
=
25˚C, V
+
=
+15V, V
−
=
−15V, V
CM
=
0V, and R
L
=
1kΩ.Boldface
limits apply at the temperature extremes
Typ LM6171AI LM6171BI
Symbol Parameter Conditions (Note 5) Limit Limit Units
(Note 6) (Note 6)
Continuous Output Current Sourcing, R
L
=
10Ω 100 mA
(in Linear Region) Sinking, R
L
=
10Ω 80 mA
I
SC
Output Short Sourcing 135 mA
Circuit Current Sinking 135 mA
I
S
Supply Current 2.5 4 4 mA
4.5 4.5 max
±
15V AC Electrical Characteristics
Unless otherwise specified, all limits guaranteed for T
J
=
25˚C, V
+
=
+15V, V
−
=
−15V, V
CM
=
0V, and R
L
=
1kΩ.Boldface
limits apply at the temperature extremes
Typ LM6171AI LM6171BI
Symbol Parameter Conditions (Note 5) Limit Limit Units
(Note 6) (Note 6)
SR Slew Rate (Note 9) A
V
=
+2, V
IN
=
13 V
PP
3600 V/µs
A
V
=
+2, V
IN
=
10 V
PP
3000
GBW Unity Gain-Bandwidth Product 100 MHz
−3 dB Frequency A
V
=
+1 160 MHz
A
V
=
+2 62 MHz
φm Phase Margin 40 deg
t
s
Settling Time (0.1%)A
V
=
−1, V
OUT
=
±
5V 48 ns
R
L
=
500Ω
Propagation Delay V
IN
=
±
5V, R
L
=
500Ω,6 ns
A
V
=
−2
A
D
Differential Gain (Note 10) 0.03
%
φ
D
Differential Phase (Note 10) 0.5 deg
e
n
Input-Referred f=1 kHz
12
Voltage Noise
i
n
Input-Referred f=1 kHz
1
Current Noise
±
5V DC Electrical Characteristics
Unless otherwise specified, all limits guaranteed for T
J
=
25˚C, V
+
=
+5V, V
−
=
−5V, V
CM
=
0V, and R
L
=
1kΩ.Boldface
limits apply at the temperature extremes
Typ LM6171AI LM6171BI
Symbol Parameter Conditions (Note 5) Limit Limit Units
(Note 6) (Note 6)
V
OS
Input Offset Voltage 1.2 3 6 mV
58max
TC V
OS
Input Offset Voltage 4 µV/˚C
Average Drift
I
B
Input Bias Current 1 2.5 2.5 µA
3.5 3.5 max
I
OS
Input Offset Current 0.03 1.5 1.5 µA
2.2 2.2 max
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±
5V DC Electrical Characteristics (Continued)
Unless otherwise specified, all limits guaranteed for T
J
=
25˚C, V
+
=
+5V, V
−
=
−5V, V
CM
=
0V, and R
L
=
1kΩ.Boldface
limits apply at the temperature extremes
Typ LM6171AI LM6171BI
Symbol Parameter Conditions (Note 5) Limit Limit Units
(Note 6) (Note 6)
R
IN
Input Resistance Common Mode 40 MΩ
Differential Mode 4.9
R
O
Open Loop 14 Ω
Output Resistance
CMRR Common Mode V
CM
=
±
2.5V 105 80 75 dB
Rejection Ratio 75 70 min
PSRR Power Supply V
S
=
±
15V to±5V 95 85 80 dB
Rejection Ratio 80 75 min
V
CM
Input Common-Mode CMRR ≥ 60 dB
±
3.7 V
Voltage Range
A
V
Large Signal Voltage R
L
=
1kΩ 84 75 75 dB
Gain (Note 7) 65 65 min
R
L
=
100Ω 80 70 70 dB
60 60 min
V
O
Output Swing R
L
=
1kΩ 3.5 3.2 3.2 V
33min
−3.4 −3.2 −3.2 V
−3 −3 max
R
L
=
100Ω 3.2 2.8 2.8 V
2.5 2.5 min
−3.0 −2.8 −2.8 V
−2.5 −2.5 max
Continuous Output Current Sourcing, R
L
=
100Ω 32 28 28 mA
(Open Loop) (Note 8) 25 25 min
Sinking, R
L
=
100Ω 30 28 28 mA
25 25 max
I
SC
Output Short Sourcing 130 mA
Circuit Current Sinking 100 mA
I
S
Supply Current 2.3 3 3 mA
3.5 3.5 max
±
5V AC Electrical Characteristics
Unless otherwise specified, all limits guaranteed for T
J
=
25˚C, V
+
=
+5V, V
−
=
−5V, V
CM
=
0V, and R
L
=
1kΩ.Boldface
limits apply at the temperature extremes
Typ LM6171AI LM6171BI
Symbol Parameter Conditions (Note 5) Limit Limit Units
(Note 6) (Note 6)
SR Slew Rate (Note 9) A
V
=
+2, V
IN
=
3.5 V
PP
750 V/µs
GBW Unity Gain-Bandwidth 70 MHz
Product
−3 dB Frequency A
V
=
+1 130 MHz
A
V
=
+2 45
φm Phase Margin 57 deg
t
s
Settling Time (0.1%)A
V
=
−1, V
OUT
=
+1V, 60 ns
R
L
=
500Ω
Propagation Delay V
IN
=
±
1V, R
L
=
500Ω,8 ns
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±
5V AC Electrical Characteristics (Continued)
Unless otherwise specified, all limits guaranteed for T
J
=
25˚C, V
+
=
+5V, V
−
=
−5V, V
CM
=
0V, and R
L
=
1kΩ.Boldface
limits apply at the temperature extremes
Typ LM6171AI LM6171BI
Symbol Parameter Conditions (Note 5) Limit Limit Units
(Note 6) (Note 6)
A
V
=
−2
A
D
Differential Gain (Note 10) 0.04
%
φ
D
Differential Phase (Note 10) 0.7 deg
e
n
Input-Referred f=1 kHz
11
Voltage Noise
i
n
Input-Referred f=1 kHz
1
Current Noise
Note 1: Absolute Maximum Ratings indicate limits beyond which damage to the device may occur. Operating Ratings indicate conditions for which the device is intended to be functional, but specific performance is not guaranteed. For guaranteed specifications and the test conditions, see the Electrical Characteristics.
Note 2: Human body model, 1.5 kΩ in series with 100 pF.
Note 3: Continuous short circuit operation at elevated ambient temperature can result in exceeding the maximum allowed junction temperature of 150˚C.
Note 4: The maximum power dissipation is a function of T
J(max)
, θJA, and TA. The maximum allowable power dissipation at any ambient temperature is P
D
=
(T
J(max)−TA
)/θJA. All numbers apply for packages soldered directly into a PC board.
Note 5: Typical Values represent the most likely parametric norm.
Note 6: All limits are guaranteed by testing or statistical analysis.
Note 7: Large signal voltage gain is the total output swing divided by the input signal required to produce that swing. For V
S
=
±
15V, V
OUT
=
±
5V. For V
S
=
+5V,
V
OUT
=
±
1V.
Note 8: The open loop output current is the output swing with the 100Ω load resistor divided by that resistor.
Note 9: Slew rate is the average of the rising and falling slew rates.
Note 10: Differential gain and phase are measured with A
V
=
+2, V
IN
=
1V
PP
at 3.58 MHz and both input and output 75Ω terminated.
Note 11: Differential input voltage is measured at V
S
=
±
15V.
Typical Performance Characteristics Unless otherwise noted, T
A
=
25˚C
Supply Current vs
Supply Voltage
DS012336-20
Supply Current vs
Temperature
DS012336-21
Input Offset Voltage vs
Temperature
DS012336-22
Input Bias Current
vs Temperature
DS012336-23
Input Offset Voltage vs
Common Mode Voltage
DS012336-24
Short Circuit Current
vs Temperature (Sourcing)
DS012336-25
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Typical Performance Characteristics Unless otherwise noted, T
A
=
25˚C (Continued)
Short Circuit Current
vs Temperature (Sinking)
DS012336-26
Output Voltage
vs Output Current
DS012336-27
Output Voltage
vs Output Current
DS012336-28
CMRR vs Frequency
DS012336-29
PSRR vs Frequency
DS012336-30
PSRR vs Frequency
DS012336-31
Open Loop
Frequency Response
DS012336-32
Open Loop
Frequency Response
DS012336-33
Gain Bandwidth Product
vs Supply Voltage
DS012336-34
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Typical Performance Characteristics Unless otherwise noted, T
A
=
25˚C (Continued)
Gain Bandwidth
Product vs
Load Capacitance
DS012336-35
Large Signal
Voltage Gain
vs Load
DS012336-36
Large Signal
Voltage Gain
vs Load
DS012336-37
Input Voltage Noise
vs Frequency
DS012336-38
Input Voltage Noise
vs Frequency
DS012336-39
Input Current Noise
vs Frequency
DS012336-40
Input Current Noise
vs Frequency
DS012336-41
Slew Rate vs
Supply Voltage
DS012336-42
Slew Rate vs
Input Voltage
DS012336-43
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Typical Performance Characteristics Unless otherwise noted, T
A
=
25˚C (Continued)
Slew Rate vs
Load Capacitance
DS012336-44
Open Loop Output
Impedance vs Frequency
DS012336-45
Open Loop Output
Impedance vs Frequency
DS012336-46
Large Signal
Pulse Response
A
V
=
−1, V
S
=
±
15V
DS012336-47
Large Signal
Pulse Response
A
V
=
−1, V
S
=
±
5V
DS012336-48
Large Signal
Pulse Response
A
V
=
+1, V
S
=
±
15V
DS012336-49
Large Signal
Pulse Response
A
V
=
+1, V
S
=
±
5V
DS012336-50
Large Signal
Pulse Response
A
V
=
+2, V
S
=
±
15V
DS012336-51
Large Signal
Pulse Response
A
V
=
+2, V
S
=
±
5V
DS012336-52
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Typical Performance Characteristics Unless otherwise noted, T
A
=
25˚C (Continued)
Small Signal
Pulse Response
A
V
=
−1, V
S
=
±
15V
DS012336-53
Small Signal
Pulse Response
A
V
=
−1, V
S
=
±
5V
DS012336-54
Small Signal
Pulse Response
A
V
=
+1, V
S
=
±
15V
DS012336-55
Small Signal
Pulse Response
A
V
=
+1, V
S
=
±
5V
DS012336-56
Small Signal
Pulse Response
A
V
=
+2, V
S
=
±
15V
DS012336-57
Small Signal
Pulse Response
A
V
=
+2, V
S
=
±
5V
DS012336-58
Closed Loop Frequency
Response vs Supply
Voltage (A
V
=
+1)
DS012336-59
Closed Loop Frequency
Response vs Supply
Voltage (A
V
=
+2)
DS012336-60
Closed Loop Frequency
Response vs Capacitive
Load (A
V
=
+1)
DS012336-61
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Typical Performance Characteristics Unless otherwise noted, T
A
=
25˚C (Continued)
Closed Loop Frequency
Response vs Capacitive
Load (A
V
=
+1)
DS012336-62
Closed Loop Frequency
Response vs Capacitive
Load (A
V
=
+2)
DS012336-63
Closed Loop Frequency
Response vs Capacitive
Load (A
V
=
+2)
DS012336-64
Total Harmonic Distortion
vs Frequency
DS012336-65
Total Harmonic Distortion
vs Frequency
DS012336-66
Total Harmonic Distortion
vs Frequency
DS012336-67
Total Harmonic Distortion
vs Frequency
DS012336-68
Undistorted Output Swing
vs Frequency
DS012336-69
Undistorted Output Swing
vs Frequency
DS012336-70
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Typical Performance Characteristics Unless otherwise noted, T
A
=
25˚C (Continued)
LM6171 Simplified Schematic
Application Information
LM6171 Performance Discussion
The LM6171 is a high speed, unity-gain stable voltage feedback amplifier. It consumes only 2.5 mA supply current while
providing a gain-bandwidth product of 100 MHz and a slew
rate of 3600V/µs. It also has other great features such as low
differential gain and phase and high output current. The
LM6171 is a good choice in high speed circuits.
The LM6171 is a true voltage feedback amplifier. Unlike current feedback amplifiers (CFAs)with a low inverting input impedance and a high non-inverting input impedance, both inputs of voltage feedback amplifiers (VFAs) have high
impedance nodes. The low impedance inverting input in
CFAs will couple with feedback capacitor and cause oscillation. As a result, CFAs cannot be used in traditional op amp
circuits such as photodiode amplifiers, I-to-V converters and
integrators.
LM6171 Circuit Operation
The class AB input stage in LM6171 is fully symmetrical and
has a similar slewing characteristic to the current feedback
amplifiers. In the LM6171 Simplfied Schematic, Q1 through
Q4 form the equivalent of the current feedback input buffer,
R
E
the equivalent of the feedback resistor, and stage A buffers the inverting input. The triple-buffered output stage isolates the gain stage from the load to provide low output impedance.
LM6171 Slew Rate Characteristic
The slew rate of LM6171 is determined by the current available to charge and discharge an internal high impedance
node capacitor. The current is the differential input voltage
divided by the total degeneration resistor R
E
. Therefore, the
Undistorted Output Swing
vs Frequency
DS012336-71
Undistorted Output Swing
vs Frequency
DS012336-72
Total Power
Dissipation vs
Ambient Temperature
DS012336-73
DS012336-10
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Application Information (Continued)
slew rate is proportional to the input voltage level, and the
higher slew rates are achievable in the lower gain configurations.
When a very fast large signal pulse is applied to the input of
an amplifier, some overshoot or undershoot occurs. By placing an external series resistor such as 1 kΩ to the input of
LM6171, the bandwidth is reduced to help lower the overshoot.
Layout Consideration
PRINTED CIRCUIT BOARDS AND HIGH SPEED OP
AMPS
There are many things to consider when designing PC
boards for high speed op amps. Without proper caution, it is
very easy and frustrating to have excessive ringing, oscillation and other degraded AC performance in high speed circuits.As a rule, the signal traces should be short and wide to
provide low inductance and low impedance paths. Any unused board space needs to be grounded to reduce stray signal pickup. Critical components should also be grounded at
a common point to eliminate voltage drop. Sockets add capacitance to the board and can affect frequency performance. It is better to solder the amplifier directly into the PC
board without using any socket.
USING PROBES
Active (FET) probes are ideal for taking high frequency measurements because they have wide bandwidth, high input
impedance and low input capacitance. However, the probe
ground leads provide a long ground loop that will produce errors in measurement. Instead, the probes can be grounded
directly by removing the ground leads and probe jackets and
using scope probe jacks.
COMPONENTS SELECTION AND FEEDBACK
RESISTOR
It is important in high speed applications to keep all component leads short because wires are inductive at high frequency. For discrete components, choose carbon
composition-type resistors and mica-type capacitors. Surface mount components are preferred over discrete components for minimum inductive effect.
Large values of feedback resistors can couple with parasitic
capacitance and cause undesirable effects such as ringing
or oscillation in high speed amplifiers. For LM6171, a feedback resistor of 510Ω gives optimal performance.
Compensation for Input
Capacitance
The combination of an amplifier’s input capacitance with the
gain setting resistors adds a pole that can cause peaking or
oscillation. To solve this problem, a feedback capacitor with
a value
C
F
>
(RGxCIN)/R
F
can be used to cancel that pole. For LM6171, a feedback capacitor of 2 pF is recommended.
Figure 1
illustrates the com-
pensation circuit.
Power Supply Bypassing
Bypassing the power supply is necessary to maintain low
power supply impedance across frequency. Both positive
and negative power supplies should be bypassed individually by placing 0.01 µF ceramic capacitors directly to power
supply pins and 2.2 µF tantalum capacitors close to the
power supply pins.
Termination
In high frequency applications, reflections occur if signals
are not properly terminated.
Figure 3
shows a properly termi-
nated signal while
Figure 4
shows an improperly terminated
signal.
DS012336-11
FIGURE 1. Compensating for Input Capacitance
DS012336-12
FIGURE 2. Power Supply Bypassing
DS012336-14
FIGURE 3. Properly Terminated Signal
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Application Information (Continued)
To minimize reflection, coaxial cable with matching characteristic impedance to the signal source should be used. The
other end of the cable should be terminated with the same
value terminator or resistor. For the commonly used cables,
RG59 has 75Ω characteristic impedance, and RG58 has
50Ω characteristic impedance.
Driving Capacitive Loads
Amplifiers driving capacitive loads can oscillate or have ringing at the output. To eliminate oscillation or reduce ringing,
an isolation resistor can be placed as shown below in
Figure
5
. The combination of the isolation resistor and the load capacitor forms a pole to increase stablility by adding more
phase margin to the overall system. The desired performance depends on the value of the isolation resistor; the bigger the isolation resistor, the more damped the pulse response becomes. For LM6171, a 50Ω isolation resistor is
recommended for initial evaluation.
Figure 6
shows the
LM6171 driving a 200 pF load with the 50Ω isolation resistor.
Power Dissipation
The maximum power allowed to dissipate in a device is defined as:
P
D
=
(T
J(max)−TA
)/θ
JA
Where PDis the power dissipation in a device
T
J(max)
is the maximum junction temperature
T
A
is the ambient temperature
θ
JA
is the thermal resistance of a particular package
For example, for the LM6171 in a SO-8 package, the maximum power dissipation at 25˚C ambient temperature is
730 mW.
Thermal resistance, θ
JA
, depends on parameters such as
die size, package size and package material. The smaller
the die size and package, the higher θ
JA
becomes. The 8-pin
DIP package has a lower thermal resistance (108˚C/W) than
that of 8-pin SO (172˚C/W). Therefore, for higher dissipation
capability, use an 8-pin DIP package.
DS012336-15
FIGURE 4. Improperly Terminated Signal
DS012336-13
FIGURE 5. Isolation Resistor Used
to Drive Capacitive Load
DS012336-16
FIGURE 6. The LM6171 Driving a 200 pF Load
with a 50Ω Isolation Resistor
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Application Information (Continued)
The total power dissipated in a device can be calculated as:
P
D
=
P
Q+PL
PQis the quiescent power dissipated in a device with no load
connected at the output. P
L
is the power dissipated in the device with a load connected at the output; it is not the power
dissipated by the load.
Furthermore,
P
Q
=
supply current x total supply voltage with no
load
P
L
=
output current x (voltage difference between
supply voltage and output voltage of the same
supply)
For example, the total power dissipated by the LM6171 with
V
S
=
±
15V and output voltage of 10V into 1 kΩ load resistor
(one end tied to ground) is
P
D
=
P
Q+PL
=
(2.5 mA) x (30V) + (10 mA) x (15V − 10V)
=
75mW+50mW
=
125 mW
Application Circuits
Design Kit
A design kit is available for the LM6171. The design kit contains:
•
High Speed Evaluation Board
•
LM6171 in 8-pin DIP Package
•
LM6171 Datasheet
•
Pspice Macromodel Diskette With the LM6171 Macromodel
•
An Amplifier Selection Guide
Pitch Pack
Apitch pack is available for the LM6171. The pitch pack contains:
•
High Speed Evaluation Board
•
LM6171 in 8-pin DIP Package
•
LM6171 Datasheet
•
Pspice Macromodel Diskette With the LM6171 Macromodel
Contact your local National Semiconductor sales office to
obtain a pitch pack.
Fast Instrumentation Amplifier
DS012336-17
Multivibrator
DS012336-18
Pulse Width Modulator
DS012336-19
www.national.com15
Physical Dimensions inches (millimeters) unless otherwise noted
8-Pin Small Outline Package
NS Package Number M08A
8-Pin Molded DIP Package
NS Package Number N08E
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Notes
LIFE SUPPORT POLICY
NATIONAL’S PRODUCTS ARE NOT AUTHORIZED FOR USE AS CRITICAL COMPONENTS IN LIFE SUPPORT
DEVICES OR SYSTEMS WITHOUT THE EXPRESS WRITTEN APPROVAL OF THE PRESIDENT OF NATIONAL
SEMICONDUCTOR CORPORATION. As used herein:
1. Life support devices or systems are devices or
systems which, (a) are intended for surgical implant
into the body, or (b) support or sustain life, and
whose failure to perform when properly used in
accordance with instructions for use provided in the
labeling, can be reasonably expected to result in a
significant injury to the user.
2. A critical component is any component of a life
support device or system whose failure to perform
can be reasonably expected to cause the failure of
the life support device or system, or to affect its
safety or effectiveness.
National Semiconductor
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Email: support@nsc.com
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Deutsch Tel: +49 (0) 1 80-530 85 85
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Japan Ltd.
Tel: 81-3-5639-7560
Fax: 81-3-5639-7507
www.national.com
LM6171 High Speed Low Power Low Distortion Voltage Feedback Amplifier
National does not assume any responsibility for use of any circuitry described, no circuit patent licenses are implied and National reserves the right at any time without notice to change said circuitry and specifications.
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