Datasheet LM4992 Datasheet (National Semiconductor)

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LM4992
420mW Stereo Cell Phone Audio Amplifier

LM4992 420mW Stereo Cell Phone Audio Amplifier

February 2004

General Description

The LM4992 is a stereo audio power amplifier primarily
designed for demanding applications in mobile phones and
other portable communication device applications. It is ca­pable of delivering 1 watt, per channel, of continuous aver­age power to an 8Ω BTL load with less than 1% distortion
(THD+N) from a 5V

Boomer audio power amplifiers were designed specifically to
provide high quality output power with a minimal amount of
external components. The LM4992 does not require output
coupling capacitors or bootstrap capacitors, and therefore is
ideally suited for mobile phone and other low voltage appli­cations where minimal power consumption is a primary re­quirement.

The LM4992 features independent shutdown control for
each channel and a low-power consumption shutdown
mode, which is achieved by driving both shutdown pins with
logic low. Additionally, the LM4992 features an internal ther­mal shutdown protection mechanism.

The LM4992 contains advanced pop & click circuitry which
eliminates noise which would otherwise occur during turn-on
and turn-off transitions.

The LM4992 is unity-gain stable and can be configured by
external gain-setting resistors.

power supply.

DC

Key Specifications

j

Improved PSRR at 217Hz & 1KHz 64dB (1KHz)

j

Stereo Output Power at 5.0V,

1% THD, 8Ω 1.07W (typ)

j

Stereo Output Power at 3.3V,

1% THD, 8Ω 420mW (typ)

j

Shutdown Current, Vdd= 3.3V 0.2µA (typ)

Features

n Available in space-saving LLP package
n Ultra low current shutdown mode
n BTL output can drive capacitive loads
n Improved pop & click circuitry eliminates noise during

turn-on and turn-off transitions

n 2.2 - 5.5V operation
n No output coupling capacitors, snubber networks or

bootstrap capacitors required

n Unity-gain stable
n External gain configuration capability

Applications

n Mobile Phones
n PDAs
n Portable electronic devices

Connection Diagram

SDA14A

Top View

Order Number LM4992SD

See NS Package Number SDA14A

Boomer®is a registered trademark of National Semiconductor Corporation.

© 2004 National Semiconductor Corporation DS200761 www.national.com

200761E6

Typical Application

LM4992

FIGURE 1. Typical Audio Amplifier Application Circuit

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200761E7

LM4992

Absolute Maximum Ratings (Note 2)

If Military/Aerospace specified devices are required,
please contact the National Semiconductor Sales Office/
Distributors for availability and specifications.

Supply Voltage (Note 10) 6.0V

Junction Temperature 150˚C

Thermal Resistance

θ

(LLP) 103˚C/W

JA

Operating Ratings

Storage Temperature −65˚C to +150˚C

Input Voltage −0.3V to V

DD

+0.3V

Power Dissipation (Notes 3, 11) Internally Limited

ESD Susceptibility (Note 4) 2000V

Temperature Range

T

MIN

≤ TA≤ T

MAX

−40˚C ≤ TA≤ 85˚C

Supply Voltage 2.2V ≤ V

DD

≤ 5.5V

ESD Susceptibility (Note 5) 200V

Electrical Characteristics VDD=5V (Notes 1, 2)

The following specifications apply for the circuit shown in Figure 1, unless otherwise specified. Limits apply for T

LM4992

Symbol Parameter Conditions

Typical Limit

(Note 6) (Notes 7, 8)

= 0V, Io= 0A, No Load 6 14 mA (max)

V

I

DD

I

SD

V

SDIH

V

SDIL

V

OS

P

o

Quiescent Power Supply Current

Shutdown Current VSD=V

Shutdown Voltage Input High 1.5 V

Shutdown Voltage Input Low 1.3 V

Output Offset Voltage 7 30 mV (max)

Output Power THD = 1% (max);f=1kHz, per

IN

V

= 0V, Io= 0A, 8Ω Load 7 18 mA (max)

IN

GND

1.4 3 µA (max)

1.07 0.9 W (min)

channel

T

WU

THD+N Total Harmonic Distortion+Noise P

Wake-up time 100 ms

= 0.5 Wrms; f = 1kHz 0.15 %

o

Xtalk Crosstalk 80 dB

V

PSRR Power Supply Rejection Ratio

= 200mV sine p-p

ripple

Input terminated with 10Ω

60 (f =
217Hz)

55 dB (min)

64 (f = 1kHz)

= 25˚C.

A

Units

(Limits)

Electrical Characteristics VDD= 3.3V (Notes 1, 2)

The following specifications apply for the circuit shown in Figure 1, unless otherwise specified. Limits apply for T

LM4992

Symbol Parameter Conditions

Typical Limit

(Note 6) (Notes 7, 8)

= 0V, Io= 0A, No Load 4 12 mA (max)

V

I

DD

I

SD

V

SDIH

V

SDIL

V

OS

P

o

T

WU

Quiescent Power Supply Current

Shutdown Current VSD=V

Shutdown Voltage Input High 1.2 V

Shutdown Voltage Input Low 1.0 V

Output Offset Voltage 7 30 mV (max)

Output Power THD = 1% (max);f=1kHz, per

Wake-up time 75 ms

THD+N Total Harmonic Distortion+Noise P

IN

V

= 0V, Io= 0A, 8Ω Load 5 15 mA (max)

IN

GND

0.2 2.0 µA (max)

420 mW (min)

channel

= 0.25 Wrms; f = 1kHz 0.1 %

o

Xtalk Crosstalk 80 dB

V

PSRR Power Supply Rejection Ratio

= 200mV sine p-p

ripple

Input terminated with 10Ω

65 (f =
217Hz)

55 dB (min)

70 (f = 1kHz)

= 25˚C.

A

Units

(Limits)

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Electrical Characteristics VDD= 2.6V (Notes 1, 2)

The following specifications apply for the circuit shown in Figure 1, unless otherwise specified. Limits apply for T

LM4992

LM4992

Symbol Parameter Conditions

Typical Limit

(Note 6) (Notes 7, 8)

= 0V, Io= 0A, No Load 4.0 mA (max)

V

I

DD

I

SD

V

SDIH

V

SDIL

V

OS

P

o

Quiescent Power Supply Current

Shutdown Current VSD=V

Shutdown Voltage Input High 1.2 V

Shutdown Voltage Input Low 1.0 V

Output Offset Voltage 5 30 mV (max)

Output Power THD = 1% (max);f=1kHz, per

IN

V

= 0V, Io= 0A, 8Ω Load 6.0 mA (max)

IN

GND

0.02 2.0 µA (max)

240

channel

T

WU

THD+N Total Harmonic Distortion+Noise P

Wake-up time 70 ms

= 0.15 Wrms; f = 1kHz 0.1 %

o

Xtalk Crosstalk 80 dB

V

PSRR Power Supply Rejection Ratio

= 200mV sine p-p

ripple

Input terminated with 10Ω

51 (f =
217Hz)
51 (f = 1kHz)

Note 1: All voltages are measured with respect to the ground pin, unless otherwise specified.

Note 2: Absolute Maximum Ratings indicate limits beyond which damage to the device may occur. Operating Ratings indicate conditions for which the device is

functional, but do not guarantee specific performance limits. Electrical Characteristics state DC andAC electrical specifications under particular test conditions which
guarantee specific performance limits. This assumes that the device is within the Operating Ratings. Specifications are not guaranteed for parameters where no limit
is given, however, the typical value is a good indication of device performance.

Note 3: The maximum power dissipation must be derated at elevated temperatures and is dictated by T
allowable power dissipation is P

Note 4: Human body model, 100pF discharged through a 1.5kΩ resistor.

Note 5: Machine Model, 220pF–240pF discharged through all pins.

Note 6: Typicals are measured at 25˚C and represent the parametric norm.

Note 7: Limits are guaranteed to National’s AOQL (Average Outgoing Quality Level).

Note 8: Datasheet min/max specification limits are guaranteed by design, test, or statistical analysis.

Note 9: R

Note 10: If the product is in Shutdown mode and V

If the source impedance limits the current to a max of 10mA, then the device will be protected. If the device is enabled when V

6.5V, no damage will occur, although operation life will be reduced. Operation above 6.5V with no current limit will result in permanent damage.

Note 11: Maximum power dissipation in the device (P
Equation 1 shown in the Application Information section. It may also be obtained from the power dissipation graphs.

is measured from the output pin to ground. This value represents the parallel combination of the 10kΩ output resistors and the two 20kΩ resistors.

OUT

DMAX

=(T

)/θJAor the number given in Absolute Maximum Ratings, whichever is lower.

JMAX–TA

exceeds 6V (to a max of 8V VDD), then most of the excess current will flow through the ESD protection circuits.

DD

) occurs at an output power level significantly below full output power. P

DMAX

, θJA, and the ambient temperature TA. The maximum

JMAX

is greater than 5.5V and less than

DD

DMAX

A

can be calculated using

= 25˚C.

Units

(Limits)

mW (min)

dB (min)

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External Components Description

(Figure 1)

Components Functional Description

1. R

2. C

3. R

4. C

Inverting input resistance which sets the closed-loop gain in conjunction with Rf. This resistor also forms a

i

high pass filter with C

Input coupling capacitor which blocks the DC voltage at the amplifiers input terminals. Also creates a

i

highpass filter with R
for an explanation of how to determine the value of C

Feedback resistance which sets the closed-loop gain in conjunction with Ri.

f

Supply bypass capacitor which provides power supply filtering. Refer to the Power Supply Bypassing

S

at fC= 1/(2π RiCi).

i

at fc= 1/(2π RiCi). Refer to the section, Proper Selection of External Components,

i

.

i

section for information concerning proper placement and selection of the supply bypass capacitor.

5. C

Bypass pin capacitor which provides half-supply filtering. Refer to the section, Proper Selection of External

B

Components, for information concerning proper placement and selection of C

Typical Performance Characteristics

LM4992

.

B

THD+N vs Frequency

= 5V, 8Ω RL,

at V

DD

and PWR = 500mW, per channel

THD+N vs Frequency

= 2.6V, 8Ω RL,

at V

DD

and PWR = 150mW, per channel

THD+N vs Frequency
at VDD= 3.3V, 8Ω RL,

and PWR = 250mW, per channel

200761F1 200761F2

THD+N vs Power Out

at VDD= 5V, 8Ω RL,

1kHz, per channel

200761F3 200761F4

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Typical Performance Characteristics (Continued)

LM4992

THD+N vs Power Out
at V

= 3.3V, 8Ω RL,

DD

1kHz, per channel

200761F5 200761F6

Power Supply Rejection Ratio (PSRR) vs Frequency

= 5V, 8Ω R

at V

DD

L

THD+N vs Power Out
at VDD= 2.6V, 8Ω RL,

1kHz, per channel

Power Supply Rejection Ratio (PSRR) vs Frequency

= 5V, 8Ω R

at V

DD

L

Input terminated with 10Ω

200761F7

Power Supply Rejection Ratio (PSRR) vs Frequency

= 3.3V, 8Ω R

at V

DD

L

200761F9

Input Floating

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Input Floating

200761F8

Power Supply Rejection Ratio (PSRR) vs Frequency

= 3.3V, 8Ω R

at V

DD

L

200761G0

Input Floating

Typical Performance Characteristics (Continued)

LM4992

Power Supply Rejection Ratio (PSRR) vs Frequency

at V

= 2.6V, 8Ω R

DD

L

200761G1

Input terminated with 10Ω

Open Loop Frequency Response, 5V Open Loop Frequency Response, 3.3V

Power Supply Rejection Ratio (PSRR) vs Frequency

= 2.6V, 8Ω R

at V

DD

L

200761G2

Input Floating

200761G3 200761G4

Open Loop Frequency Response, 2.6V Noise Floor, 5V, 8Ω

80kHz Bandwidth, Input to GND

200761G5

200761G6

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Typical Performance Characteristics (Continued)

LM4992

Crosstalk vs Frequency

5V, 8Ω,P

OUT

=1W

Crosstalk vs Frequency

2.6V, 8Ω,P

OUT

= 200mW

Crosstalk vs Frequency

3.3V, 8Ω,P

200761G7 200761G8

OUT

= 400mW

Power Dissipation vs

Output Power, 5V, 8Ω,

per channel

200761G9

Power Dissipation vs

Output Power, 3.3V, 8Ω,

per channel

200761H1

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200761H0

Power Dissipation vs

Output Power, 2.6V, 8Ω,

per channel

200761H2

Typical Performance Characteristics (Continued)

LM4992

Shutdown Hysteresis Voltage

5V

Shutdown Hysteresis Voltage

2.6V

Shutdown Hysteresis Voltage

3.3V

200761H3 200761H4

Output Power vs

Supply Voltage, 8Ω

Frequency Response vs

Input Capacitor Size

200761H4 200761H5

Wakeup Time vs

Supply Voltage

200761H6 200761H7

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Application Information

BRIDGE CONFIGURATION EXPLANATION

LM4992

As shown in Figure 1, the LM4992 has two internal opera­tional amplifiers per channel. The first amplifier’s gain is
externally configurable , while the second amplifier is inter­nally fixed in a unity-gain, inverting configuration. The
closed-loop gain of the first amplifier is set by selecting the
ratio of R
the two internal 20kΩ resistors. Figure 1 shows that the
output of amplifier one serves as the input to amplifier two
which results in both amplifiers producing signals identical in
magnitude, but out of phase by 180˚. Consequently, the
differential gain for the IC is

By driving the load differentially through outputs Vo1 and
Vo2, an amplifier configuration commonly referred to as
“bridged mode” is established. Bridged mode operation is
different from the classical single-ended amplifier configura­tion where one side of the load is connected to ground.

A bridge amplifier design has a few distinct advantages over
the single-ended configuration, as it provides differential
drive to the load, thus doubling output swing for a specified
supply voltage. Four times the output power is possible as
compared to a single-ended amplifier under the same con­ditions. This increase in attainable output power assumes
that the amplifier is not current limited or clipped. In order to
choose an amplifier’s closed-loop gain without causing ex­cessive clipping, please refer to the Audio Power Amplifier
Design section.

A bridge configuration, such as the one used in LM4992,
also creates a second advantage over single-ended amplifi­ers. Since the differential outputs, Vo1 and Vo2, are biased
at half-supply, no net DC voltage exists across the load. This
eliminates the need for an output coupling capacitor which is
required in a single supply, single-ended amplifier configura­tion. Without an output coupling capacitor, the half-supply
bias across the load would result in both increased internal
IC power dissipation and also possible loudspeaker damage.

POWER DISSIPATION

Power dissipation is a major concern when designing a
successful amplifier, whether the amplifier is bridged or
single-ended. A direct consequence of the increased power
delivered to the load by a bridge amplifier is an increase in
internal power dissipation. The maximum internal power dis­sipation per channel is 4 times that of a single-ended ampli­fier. The maximum power dissipation for a given application
can be derived from the power dissipation graphs or from
Equation 1.

It is critical that the maximum junction temperature T
150˚C is not exceeded. T
PC board foil area. By adding copper foil, the thermal resis­tance of the application can be reduced from the free air
value of θ
mal shutdown protection circuitry being activated. Additional
copper foil can be added to any of the leads connected to the
LM4992. It is especially effective when connected to V
GND, and the output pins. Refer to the application informa­tion on the LM4992 reference design board for an example

to Riwhile the second amplifier’s gain is fixed by

f

= 2 *(Rf/Ri)

A

VD

= 4*(VDD)2/(2π2RL) (1)

P

DMAX

is a function of P

JMAX

, resulting in higher P

JA

values without ther-

DMAX

DMAX

JMAX

and the

DD

of good heat sinking. If T

still exceeds 150˚C, then

JMAX

additional changes must be made. These changes can in­clude reduced supply voltage, higher load impedance, or
reduced ambient temperature. Internal power dissipation is a
function of output power. Refer to the Typical Performance
Characteristics curves for power dissipation information for
different output powers and output loading.

EXPOSED-DAP MOUNTING CONSIDERATIONS

The LM4992’s exposed-DAP (die attach paddle) packages
(SD) provide a low thermal resistance between the die and
the PCB to which the part is mounted and soldered. This
allows rapid heat transfer from the die to the surrounding
PCB copper area heatsink, copper traces, ground plane, and
finally, surrounding air. The result is a low voltage audio
power amplifier that produces 1.07W dissipation per channel
in an 8Ω load at ≤ 1% THD+N. This power is achieved
through careful consideration of necessary thermal design.
Failing to optimize thermal design may compromise the
LM4992’s performance and activate unwanted, though nec­essary, thermal shutdown protection.

The LM4992SD must have its DAP soldered to a copper pad
on the PCB. The DAP’s PCB copper pad is then, ideally,
connected to a large plane of continuous unbroken copper.
This plane forms a thermal mass, heat sink, and radiation
area. Place the heat sink area on either outside plane in the
case of a two-sided or multi-layer PCB. (The heat sink area
can also be placed on an inner layer of a multi-layer board.
The thermal resistance, however, will be higher.) Connect
the DAP copper pad to the inner layer or backside copper
heat sink area with vias. The via diameter should be 0.012in

- 0.013in with a 1.27mm pitch. Ensure efficient thermal con­ductivity by plugging and tenting the vias with plating and
solder mask, respectively.

POWER SUPPLY BYPASSING

As with any amplifier, proper supply bypassing is critical for
low noise performance and high power supply rejection. The
capacitor location on both the bypass and power supply pins
should be as close to the device as possible. Typical appli­cations employ a 5V regulator with 10 µF tantalum or elec­trolytic capacitor and a ceramic bypass capacitor which aid
in supply stability. This does not eliminate the need for
bypassing the supply nodes of the LM4992. The selection of
a bypass capacitor, C

, is dependent upon PSRR require-

B

ments, click and pop performance (as explained in the sec­tion, Proper Selection of External Components), system
cost, and size constraints.

SHUTDOWN FUNCTION

In order to reduce power consumption while not in use, the
LM4992 contains shutdown circuitry that is used to indepen­dently turn off each channel’s bias circuitry. This shutdown
feature turns a given channel off when logic low is placed on
the corresponding shutdown pin. By switching a particular

of

shutdown pin to GND, the LM4992 supply current draw due
to that channel will be minimized in idle mode. Idle current is
measured with the shutdown pin connected to GND. The
trigger point for shutdown is shown as a typical value in the
Shutdown Hysteresis Voltage graphs in the Typical Perfor-
mance Characteristics section. It is best to switch between
ground and supply for maximum performance. While the

,

device may be disabled with shutdown voltages in between
ground and supply, the idle current may be greater than the

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Application Information (Continued)

typical value of 0.2µA. In either case, the shutdown pin
should be tied to a definite voltage to avoid unwanted state
changes.

In many applications, a microcontroller or microprocessor
output is used to control the shutdown circuitry, which pro­vides a quick, smooth transition to shutdown. Another solu­tion is to use a single-throw switch in conjunction with an
external pull-up resistor. This scheme guarantees that the
shutdown pin will not float, thus preventing unwanted state
changes.

PROPER SELECTION OF EXTERNAL COMPONENTS

Proper selection of external components in applications us­ing integrated power amplifiers is critical to optimize device
and system performance. While the LM4992 is tolerant of
external component combinations, consideration to compo­nent values must be used to maximize overall system qual­ity.

The LM4992 is unity-gain stable which gives the designer
maximum system flexibility. The LM4992 should be used in
low gain configurations to minimize THD+N values, and
maximize the signal to noise ratio. Low gain configurations
require large input signals to obtain a given output power.
Input signals equal to or greater than 1 Vrms are available
from sources such as audio codecs. Please refer to the
section, Audio Power Amplifier Design, for a more com­plete explanation of proper gain selection.

Besides gain, one of the major considerations is the closed­loop bandwidth of the amplifier. To a large extent, the band­width is dictated by the choice of external components
shown in Figure 1. The input coupling capacitor, C
first order high pass filter which limits low frequency re­sponse. This value should be chosen based on needed
frequency response for a few distinct reasons.

Selection Of Input Capacitor Size

Large input capacitors are both expensive and space hungry
for portable designs. Clearly, a certain sized capacitor is
needed to couple in low frequencies without severe attenu­ation. But in many cases the speakers used in portable
systems, whether internal or external, have little ability to
reproduce signals below 100Hz to 150Hz. Thus, using a
large input capacitor may not increase actual system perfor­mance.

In addition to system cost and size, click and pop perfor­mance is effected by the size of the input coupling capacitor,

A larger input coupling capacitor requires more charge to

C

i.

reach its quiescent DC voltage (nominally 1/2 V
charge comes from the output via the feedback and is apt to
create pops upon device enable. Thus, by minimizing the
capacitor size based on necessary low frequency response,
turn-on pops can be minimized.

Besides minimizing the input capacitor size, careful consid­eration should be paid to the bypass capacitor value. Bypass
capacitor, C

, is the most critical component to minimize

B

turn-on pops since it determines how fast the LM4992 turns
on. The slower the LM4992’s outputs ramp to their quiescent
DC voltage (nominally 1/2 V
Choosing C

equal to 1.0µF along with a small value of Ci(in

B

), the smaller the turn-on pop.

DD

the range of 0.1µF to 0.39µF), should produce a virtually
clickless and popless shutdown function. While the device
will function properly, (no oscillations or motorboating), with

, forms a

i

). This

DD

C

equal to 0.1µF, the device will be much more susceptible

B

to turn-on clicks and pops. Thus, a value of C

equal to

B

1.0µF is recommended in all but the most cost sensitive
designs.

AUDIO POWER AMPLIFIER DESIGN

A 1W/8Ω Audio Amplifier

Given:

Power Output 1 Wrms

Load Impedance 8Ω

Input Level 1 Vrms

Input Impedance 20 kΩ

Bandwidth 100 Hz–20 kHz

±

0.25 dB

A designer must first determine the minimum supply rail to
obtain the specified output power. By extrapolating from the
Output Power vs Supply Voltage graphs in the Typical Per-
formance Characteristics section, the supply rail can be
easily found.

5V is a standard voltage in most applications, it is chosen for
the supply rail. Extra supply voltage creates headroom that
allows the LM4992 to reproduce peaks in excess of 1W
without producing audible distortion. At this time, the de­signer must make sure that the power supply choice along
with the output impedance does not violate the conditions
explained in the Power Dissipation section.

Once the power dissipation equations have been addressed,
the required differential gain can be determined from Equa­tion 2.

(2)

R

f/Ri=AVD

From Equation 2, the minimum A

/2

is 2.83; use AVD=3.

VD

Since the desired input impedance was 20 kΩ, and with a

impedance of 2, a ratio of 1.5:1 of Rfto Riresults in an

A

VD

allocation of R

=20kΩ and Rf=30kΩ. The final design step

i

is to address the bandwidth requirements which must be
stated as a pair of −3 dB frequency points. Five times away
from a −3 dB point is 0.17 dB down from passband response

±

which is better than the required

= 100 Hz/5 = 20 Hz

f

L

=20kHz*5=100kHz

f

H

As stated in the External Components section, R
junction with C

≥ 1/(2π*20 kΩ*20 Hz) = 0.397 µF; use 0.39 µF

C

i

create a highpass filter.

i

0.25 dB specified.

in con-

i

The high frequency pole is determined by the product of the
desired frequency pole, f
With a A

= 3 and fH= 100 kHz, the resulting GBWP =

VD

, and the differential gain, AVD.

H

300kHz which is much smaller than the LM4992 GBWP of

1.5MHz. This figure displays that if a designer has a need to
design an amplifier with a higher differential gain, the
LM4992 can still be used without running into bandwidth
limitations.

The LM4992 is unity-gain stable and requires no external
components besides gain-setting resistors, an input coupling
capacitor, and proper supply bypassing in the typical appli­cation. However, if a closed-loop differential gain of greater
than 10 is required, a feedback capacitor (C4) may be
needed as shown in Figure 2 to bandwidth limit the amplifier.
This feedback capacitor creates a low pass filter that elimi-

LM4992

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Application Information (Continued)

nates possible high frequency oscillations. Care should be

LM4992

taken when calculating the -3dB frequency in that an incor­rect combination of R
20kHz. A typical combination of feedback resistor and ca­pacitor that will not produce audio band high frequency rolloff

= 20kΩ and C4= 25pf. These components result in a

is R

3

-3dB point of approximately 320 kHz.

PCB LAYOUT GUIDELINES

This section provides practical guidelines for mixed signal
PCB layout that involves various digital/analog power and
ground traces. Designers should note that these are only
"rule-of-thumb" recommendations and the actual results will
depend heavily on the final layout.

GENERAL MIXED SIGNAL LAYOUT
RECOMMENDATION

Power and Ground Circuits

For 2 layer mixed signal design, it is important to isolate the
digital power and ground trace paths from the analog power
and ground trace paths. Star trace routing techniques (bring­ing individual traces back to a central point rather than daisy
chaining traces together in a serial manner) can have a
major impact on low level signal performance. Star trace

and C4will cause rolloff before

3

routing refers to using individual traces to feed power and
ground to each circuit or even device. This technique will
require a greater amount of design time but will not increase
the final price of the board. The only extra parts required will
be some jumpers.

Single-Point Power / Ground Connections

The analog power traces should be connected to the digital
traces through a single point (link). A "Pi-filter" can be helpful
in minimizing High Frequency noise coupling between the
analog and digital sections. It is further recommended to put
digital and analog power traces over the corresponding digi­tal and analog ground traces to minimize noise coupling.

Placement of Digital and Analog Components

All digital components and high-speed digital signal traces
should be located as far away as possible from analog
components and circuit traces.

Avoiding Typical Design / Layout Problems

Avoid ground loops or running digital and analog traces
parallel to each other (side-by-side) on the same PCB layer.
When traces must cross over each other do it at 90 degrees.
Running digital and analog traces at 90 degrees to each
other from the top to the bottom side as much as possible will
minimize capacitive noise coupling and cross talk.

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Application Information (Continued)

SCHEMATIC DRAWING

LM4992

FIGURE 2. Higher Gain Schematic Drawing

200761I2

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Demonstration Board Layout

LM4992

Recommended LLP Board Layout:

Top Overlay

Recommended LLP Board Layout:

Top Layer

200761E8

200761E9

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Demonstration Board Layout (Continued)

LM4992

Recommended LLP Board Layout:

Bottom Layer

200761F0

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Physical Dimensions inches (millimeters) unless otherwise noted

LLP Package

Order Number LM4992SD

NS Package Number SDA14A

LM4992 420mW Stereo Cell Phone Audio Amplifier

LIFE SUPPORT POLICY

NATIONAL’S PRODUCTS ARE NOT AUTHORIZED FOR USE AS CRITICAL COMPONENTS IN LIFE SUPPORT
DEVICES OR SYSTEMS WITHOUT THE EXPRESS WRITTEN APPROVAL OF THE PRESIDENT AND GENERAL
COUNSEL OF NATIONAL SEMICONDUCTOR CORPORATION. As used herein:

1. Life support devices or systems are devices or
systems which, (a) are intended for surgical implant
into the body, or (b) support or sustain life, and
whose failure to perform when properly used in
accordance with instructions for use provided in the
labeling, can be reasonably expected to result in a
significant injury to the user.

BANNED SUBSTANCE COMPLIANCE

2. A critical component is any component of a life
support device or system whose failure to perform
can be reasonably expected to cause the failure of
the life support device or system, or to affect its
safety or effectiveness.

National Semiconductor certifies that the products and packing materials meet the provisions of the Customer Products
Stewardship Specification (CSP-9-111C2) and the Banned Substances and Materials of Interest Specification
(CSP-9-111S2) and contain no ‘‘Banned Substances’’ as defined in CSP-9-111S2.

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National does not assume any responsibility for use of any circuitry described, no circuit patent licenses are implied and National reserves the right at any time without notice to change said circuitry and specifications.

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