Datasheet LM4867MTX, LM4867MTEX, LM4867MTE, LM4867MT, LM4867LQX Datasheet (NSC)

LM4867

Output-Transient-Free Dual 2.1W Audio Amplifier Plus
No Coupling Capacitor Stereo Headphone Function

General Description

The LM4867 is a dual bridge-connected audio power ampli­fier which, when connected to a 5V supply, will deliver 2.1W
toa4Ωload (Note 1) or 2.4W to a 3Ω load (Note 2) with less
than 1.0% THD+N. The LM4867 uses advanced, latest gen­eration circuitry to eliminate all traces of clicks and pops
when the supply voltage is first applied. The amplifier has a
headphone-amplifier-select input pin. It is used to switch the
amplifiers from bridge to single-ended mode for driving
headphones. A new circuit topology eliminates headphone
output coupling capacitors. A MUX control pin allows selec­tion between the two sets of stereo input signals. The MUX
control can also be used to select between two different
customer-specified closed-loop responses.

Boomer audio power amplifiers are designed specifically to
provide high quality output power from a surface mount
package and require few external components. To simplify
audio system design, the LM4867 combines dual bridge
speaker amplifiers and stereo headphone amplifiers in one
package.

The LM4867 features an externally controlled power-saving
micropower shutdown mode, a stereo headphone amplifier
mode, and thermal shutdown protection.

Note 1: An LM4867LQ or LM4867MTE that has been properly mounted to
a circuit board will deliver 2.1W into 4Ω. The Mux control can also be used to
select two different closed-loop responses. LM4867MT will deliver 1.1W into
8Ω. See the Application Information sections for further information concern­ing the LM4867LQ and the LM4867MT.

Note 2: An LM4867LQ or LM4867MTE that has been properly mounted to a
circuit board and forced-air cooled will deliver 2.4W into 3Ω.

Key Specifications

n POat 1% THD+N
n LM4867LQ, 3Ω load 2.4W (typ)
n LM4867LQ, 4Ω load 2.1W (typ)
n LM4867MTE, 4Ω 1.9W (typ)
n LM4867MT, 8Ω 1.1W (typ)
n Single-ended mode - THD+N at 75mW into 32Ω 0.5%

(max)

n Shutdown current 0.7µA (typ)

Features

n Advanced “click and pop” suppression circuitry
n Eliminates headphone amplifier output coupling

capacitors

n Stereo headphone amplifier mode
n Input mux control and two separate inputs per channel
n Thermal shutdown protection circuitry
n LLP, TSSOP, and exposed-DAP TSSOP packaging

available

Applications

n Multimedia monitors
n Portable and desktop computers
n Portable audio systems

Typical Application

Boomer®is a registered trademark of National Semiconductor Corporation.

DS200013-31

*

Refer to the Application Information section titled PROPER SELECTION OF EXTERNAL COMPONENTS for details concerning the value of CB.

FIGURE 1. Typical Audio Amplifier Application Circuit

(Pin out shown for the 24-pin Exposed-DAP LLP package. Numbers in ( ) are for the 20-pin MTE and MT

packages.)

February 2001

LM4867 Output-Transient-Free Dual 2.1W Audio Amplifier Plus No Coupling Capacitor Stereo

Headphone Function

© 2001 National Semiconductor Corporation DS200013 www.national.com

Connection Diagram

Connection Diagram

DS200013-58

Top View

Order Number LM4867MT, LM4867MTE

See NS Package Number MTC20 for TSSOP

See NS Package Number MXA20A for Exposed-DAP TSSOP

DS200013-38

Top View

Order Number LM4867LQ

See NS Package Number LQA24A for Exposed-DAP LLP

LM4867

www.national.com 2

Absolute Maximum Ratings (Note 3)

If Military/Aerospace specified devices are required,
please contact the National Semiconductor Sales Office/
Distributors for availability and specifications.

Supply Voltage 6.0V
Storage Temperature −65˚C to +150˚C
Input Voltage −0.3V to V

DD

+0.3V
Power Dissipation (Note 4) Internally limited
ESD Susceptibility (Note 5)

All pins except Pin 3 (MT, MTE), Pin 2 (LQ) 2000V

Pin 3 (MT, MTE), Pin 2 (LQ) 8000V
ESD Susceptibility (Note 6) 200V
Junction Temperature 150˚C
Solder Information

Small Outline Package

Vapor Phase (60 sec.) 215˚C
Infrared (15 sec.) 220˚C

See AN-450 “Surface Mounting and their Effects on
Product Reliablilty” for other methods of soldering surface
mount devices.

Thermal Resistance

θ

JC

(typ)—MTC20 20˚C/W

θ

JA

(typ)—MTC20 80˚C/W

θ

JC

(typ)—MXA20A 2˚C/W

θ

JA

(typ)—MXA20A 41˚C/W (Note 7)

θ

JA

(typ)—MXA20A 51˚C/W (Note 8)

θ

JA

(typ)—MXA20A 90˚C/W (Note 9)

θ

JC

(typ)—LQA24A 3.0˚C/W

θ

JA

(typ)—LQA24A TBD˚C/W (Note 10)

θ

JA

(typ)—LQA24A TBD˚C/W (Note 11)

θ

JA

(typ)—LQA24A TBD˚C/W (Note 12)

Operating Ratings

Temperature Range

T

MIN

≤ TA≤ T

MAX

−40˚C ≤ TA≤ 85˚C

Supply Voltage 2.0V ≤ V

DD

≤ 5.5V

Electrical Characteristics for Entire IC (Notes 3, 13)

The following specifications apply for VDD= 5V unless otherwise noted. Limits apply for TA= 25˚C.

Symbol Parameter Conditions LM4867 Units

(Limits)

Typical Limit

(Note 14) (Note 15)

V

DD

Supply Voltage 2 V (min)

5.5 V (max)

I

DD

Quiescent Power Supply Current VIN= 0V, IO= 0A (Note 16) , HP-IN = 0V 7.5 15 mA (max)

V

IN

= 0V, IO= 0A (Note 16) , HP-IN = 4V 3.0 6 mA (max)

I

SD

Shutdown Current VDDapplied to the SHUTDOWN pin 0.7 2 µA (max)

Electrical Characteristics for Bridged-Mode Operation (Notes 3, 13)

The following specifications apply for VDD= 5V unless otherwise specified. Limits apply for TA= 25˚C.

Symbol Parameter Conditions LM4867 Units

(Limits)

Typical Limit

(Note 14) (Note 15)

V

OS

Output Offset Voltage VIN= 0V 5 50 mV (max)

P

O

Output Power (Note 17) THD = 1%, f = 1kHz

LM4867MTE, R

L

=3Ω(Note 18) 2.2 W

LM4867LQ, R

L

=3Ω(Note 18) 2.2 W

LM4867MTE, R

L

=4Ω(Note 19) 1.9 W

LM4867LQ, R

L

=4Ω(Note 19) 1.9 W

LM4867, R

L

=8Ω 1.1 1.0 W (min)

THD+N = 10%, f = 1kHz

LM4867MTE, R

L

=3Ω(Note 18) 3.0 W

LM4867LQ, R

L

=3Ω(Note 18) 3.0 W

LM4867MTE, R

L

=4Ω(Note 19) 2.6 W

LM4867LQ, R

L

=4Ω(Note 19) 2.6 W

LM4867, R

L

=8Ω 1.5 W

THD+N = 1%, f = 1 kHz, R

L

=32Ω 0.34 W

LM4867

www.national.com3

Electrical Characteristics for Bridged-Mode Operation (Notes 3, 13) (Continued)

The following specifications apply for VDD= 5V unless otherwise specified. Limits apply for TA= 25˚C.

Symbol Parameter Conditions LM4867 Units

(Limits)

Typical Limit

(Note 14) (Note 15)

THD+N Total Harmonic Distortion+Noise 20Hz ≤ f ≤ 20kHz, A

VD

=2

LM4867MTE, R

L

=4Ω,PO=2W

LM4867LQ, R

L

=4Ω,PO=2W

LM4867, R

L

=8Ω,PO=1W

0.3

0.3

0.3

%
%
%

PSRR Power Supply Rejection Ratio V

DD

= 5V, V

RIPPLE

= 200 mV

RMS,RL

=8Ω,

C

B

= 2.2µF

67 dB

X

TALK

Channel Separation f = 1 kHz, CB= 2.2µF 80 dB

SNR Signal To Noise Ratio V

DD

= 5V, PO= 1.1W, RL=8Ω 97 dB

Electrical Characteristics for Single-Ended Operation (Notes 3, 13)

The following specifications apply for VDD= 5V unless otherwise specified. Limits apply for TA= 25˚C.

Symbol Parameter Conditions LM4867 Units

(Limits)

Typical Limit

(Note 14) (Note 15)

V

OS

Output Offset Voltage VIN= 0V 5 50 mV (max)

P

O

Output Power THD = 0.5%, f = 1kHz, RL=32Ω 85 75 mW (min)

THD+N = 1%, f = 1kHz, R

L

=8Ω(Note

20)

180 mW

THD+N = 1%, f = 1kHz, R

L

=16Ω

THD+N = 10%, f = 1kHz, R

L

=32Ω

THD+N = 10%, f = 1kHz, R

L

=16Ω

THD+N = 10%, f = 1kHz, R

L

=32Ω

165

88
208
114

mW
mW
mW
mW

V

OUT

Output Voltage Swing THD = 0.05%, RL=5kΩ 1V

P-P

THD+N Total Harmonic Distortion+Noise AV= −1, PO= 75mW, 20 Hz ≤ f ≤ 20kHz,

R

L

=32Ω

0.2 %

PSRR Power Supply Rejection Ratio C

B

= 2.2µF, V

RIPPLE

= 200mV

RMS

,

f = 1kHz

52 dB

X

TALK

Channel Separation f = 1kHz, CB= 2.2µF 60 dB

SNR Signal To Noise Ratio V

DD

= 5V, PO= 340mW, RL=8Ω 94 dB

Note 3: Absolute Maximum Ratings indicate limits beyond which damage to the device may occur. Operating Ratings indicate conditions for which the device is
functional, but donotguaranteespecific performance limits. Electrical Characteristics state DC and AC electrical specifications under particular test conditions which
guarantee specific performance limits. This assumes that the device operates within the Operating Ratings. Specifications are not guaranteed for parameters where
no limit is given. The typical value however, is a good indication of device performance.

Note 4: The maximum power dissipation must be derated at elevated temperatures and is dictated by T

JMAX

, θJA, and the ambient temperature TA. The maximum

allowable power dissipation is P

DMAX

=(T

JMAX−TA

)/θJA. For the LM4867, T

JMAX

= 150˚C. For the θJAs for different packages, please see the Application

Information section or the Absolute Maximum Ratings section.

Note 5: Human body model, 100 pF discharged through a 1.5 kΩ resistor.
Note 6: Machine model, 220 pF–240 pF discharged through all pins.
Note 7: The given θ

JA

is for an LM4867 packaged in an MXA20A with the Exposed-DAP soldered to an exposed 2in2area of 1oz printed circuit board copper.

Note 8: The given θ

JA

is for an LM4867 packaged in an MXA20A with the Exposed-DAP soldered to an exposed 1in2area of 1oz printed circuit board copper.

Note 9: The given θ

JA

is for an LM4867 packaged in an MXA20A with the Exposed-DAP not soldered to printed circuit board copper.

Note 10: The given θ

JA

is for an LM4867 packaged in an LQA24A with the Exposed-DAP soldered to an exposed 2in2area of 1oz printed circuit board copper.

Note 11: The given θ

JA

is for an LM4867 packaged in an LQA24A with the Exposed-DAP soldered to an exposed 1in2area of 1oz printed circuit board copper.

Note 12: The given θ

JA

is for an LM4867 packaged in an LQA24A with the Exposed-DAP not soldered to printed circuit board copper.

Note 13: All voltages are measured with respect to the ground (GND) pins, unless otherwise specified.
Note 14: Typicals are measured at 25˚C and represent the parametric norm.
Note 15: Limits are guaranteed to National’s AOQL (Average Outgoing Quality Level). Datasheet min/max specification limits are guaranteed by design, test, or

statistical analysis.

Note 16: The quiescent power supply current depends on the offset voltage when a practical load is connected to the amplifier.
Note 17: Output power is measured at the device terminals.
Note 18: When driving 3Ω loads from a 5V supply,the LM4867LQ, LM4867MTE, or LM4867MTE-1 must be mounted to the circuit board and forced-air cooled (450

linear-feet per minute).

Note 19: When driving 4Ω loads from a 5V supply, the LM4867LQ, LM4867MTE or LM4867MTE-1 must be mounted to the circuit board.

LM4867

www.national.com 4

Electrical Characteristics for Single-Ended Operation (Notes 3, 13) (Continued)

Note 20: See Application Information section ’Single-Ended Output Power Performance and Measurement Considerations’ for more information.

Typical Performance Characteristics
MTE- and LQ- Specific Characteristics

Note 21: This curve shows the LM4867MTE’s thermal dissipation ability at different ambient temperatures given these conditions:

500LFPM + JEDEC board: The part is soldered to a 1S2P 20-lead exposed-DAP TSSOP test board with 500 linear feet per minute of forced-air flow across

it. Board information - copper dimensions: 74x74mm, copper coverage: 100% (buried layer) and 12% (top/bottom layers), 16 vias under the exposed-DAP.

500LFPM + 2.5in

2

: The part is soldered to a 2.5in2, 1 oz. copper plane with 500 linear feet per minute of forced-air flow across it.

2.5in

2

: The part is soldered to a 2.5in2, 1oz. copper plane.

Not Attached: The part is not soldered down and is not forced-air cooled.

LM4867MTE
THD+N vs Output Power

DS200013-33

LM4867MTE
THD+N vs Frequency

DS200013-34

LM4867LQ
THD+N vs Output Power

DS200013-53

LM4867LQ
THD+N vs Frequency

DS200013-54

LM4867MTE
THD+N vs Output Power

DS200013-36

LM4867LQ
THD+N vs Output Power

DS200013-55

LM4867LQ, LM4867MTE
Power Dissipation vs Power Output

DS200013-61

LM4867LQ, LM4867MTE(Note 21)
Power Derating Curve

DS200013-59

LM4867

www.national.com5

Typical Performance Characteristics

THD+N vs Frequency

DS200013-3

THD+N vs Frequency

DS200013-4

THD+N vs Frequency

DS200013-5

THD+N vs Output Power

DS200013-6

THD+N vs Output Power

DS200013-7

THD+N vs Output Power

DS200013-8

THD+N vs Output Power

DS200013-65

THD+N vs Frequency

DS200013-63

THD+N vs Output Power

DS200013-66

THD+N vs Frequency

DS200013-64

Output Power vs
Load Resistance

DS200013-62

Power Dissipation vs
Supply Voltage

DS200013-60

LM4867

www.national.com 6

Typical Performance Characteristics (Continued)

Output Power vs
Supply Voltage

DS200013-9

Output Power vs
Supply Voltage

DS200013-10

Output Power vs
Supply Voltage

DS200013-11

Output Power vs
Load Resistance

DS200013-12

Output Power vs
Load Resistance

DS200013-13

Power Dissipation vs
Output Power

DS200013-14

Dropout Voltage vs
Supply Voltage

DS200013-15

Power Derating Curve

DS200013-16

Power Dissipation vs
Output Power

DS200013-17

LM4867

www.national.com7

Typical Performance Characteristics (Continued)

Noise Floor

DS200013-18

Channel Separation

DS200013-19

Channel Separation

DS200013-20

Power Supply
Rejection Ratio

DS200013-21

Open Loop
Frequency Response

DS200013-22

Supply Current vs
Supply Voltage

DS200013-23

LM4867

www.national.com 8

External Components Description

( Refer to Figure 1. )

Components Functional Description

1. R

i

Inverting input resistance which sets the closed-loop gain in conjunction with Rf. This resistor also forms a
high pass filter with C

i

at fc= 1/(2πRiCi).

2. C

i

Input coupling capacitor which blocks the DC voltage at the amplifier’s input terminals. Also creates a
highpass filter with R

i

at fc= 1/(2πRiCi). Refer to the section, Proper Selection of External Components,

for an explanation of how to determine the value of C

i

.

3. R

f

Feedback resistance which sets the closed-loop gain in conjunction with Ri.

4. C

s

Supply bypass capacitor which provides power supply filtering. Refer to the Power Supply Bypassing
section for information concerning proper placement and selection of the supply bypass capacitor.

5. C

B

Bypass pin capacitor which provides half-supply filtering. Refer to the section, Proper Selection of
External Components, for information concerning proper placement and selection of C

B

.

Application Information

ELIMINATING OUTPUT COUPLING CAPACITORS

Typical single-supply audio amplifiers that can switch be­tween driving bridge-tied-load (BTL) speakers and
single-ended (SE) headphones use a coupling capacitor on
each SE output. This capacitor blocks the half-supply volt­age to which the output amplifiers are typically biased and
couples the audio signal to the headphones. The signal
return to circuit ground is through the headphone jack’s
sleeve.

The LM4867 eliminates these coupling capacitors. Amp2A is
internally configured to apply V

DD

/2 to a stereo headphone
jack’s sleeve. This voltage matches the quiescent voltage
present on the Amp1A and Amp1B outputs that drive the
headphones. The headphones operate in a manner very
similar to a bridge-tied-load (BTL). The same DC voltage is
applied to both headphone speaker terminals. This results in
no net DC current flow through the speaker.AC current flows
through a headphone speaker as an audio signal’s output
amplitude increases on the speaker’s terminal.

When operating as a headphone amplifier, the headphone
jack sleeve is not connected to circuit ground. Using the
headphone output jack as a line-level output will place the
LM4867’s one-half supply voltage on a plug’s sleeve con­nection. Driving a portable notebook computer or
audio-visual display equipment is possible. This presents no
difficulty when the external equipment uses capacitively
coupled inputs. For the very small minority of equipment that
is DC-coupled, the LM4867 monitors the current supplied by
the amplifier that drives the headphone jack’s sleeve. If this
current exceeds 500mA

PK

, the amplifier is shutdown, pro­tecting the LM4867 and the external equipment. For more
information, see the section titled ’Single-Ended Output

Power Performance and Measurement Considerations’.

OUTPUT TRANSIENT (’POPS AND CLICKS’)
ELIMINATED

The LM4867 contains advanced circuitry that eliminates out­put transients (’pop and click’). This circuitry prevents all
traces of transients when the supply voltage is first applied,
when the part resumes operation after shutdown, or when
switching between BTL speakers and SE headphones. Two
circuits combine to eliminate pop and click. One circuit
mutes the output when switching between speaker loads.
Another circuit monitors the input signal. It maintains the
muted condition until there is sufficient input signal magni­tude to mask any remaining transient that may occur.

Figure 2

shows the LM4867’s lack of transients in the differ­ential signal (Trace B) across a BTL 8Ω load. The LM4867’s
active-high SHUTDOWN pin is driven by the logic signal
shown in Trace A. Trace C is the VOUT- output signal and
trace D is the VOUT+ output signal. The shutdown signal
frequency is 1Hz with a 50% duty cycle.

Figure 3

is gener­ated with the same conditions except that the output drives a
32Ω single-ended (SE) load. Again, no trace of output tran­sients is seen.

USING THE LM4867 TO UPGRADE LM4863 AND LM4873
DESIGNS

The LM4867’s noise-free operation plus
coupling-capacitorless headphone operation and functional
compatibility with the LM4873 and the LM4863 simplifies
upgrading systems using these parts. Upgrading older de­signs that use either the LM4863 or the LM4873 is easy.
Simply remove and short the coupling capacitors located
between the LM4873’s or LM4863’s Amp1A and Amp1B
outputs and the headphone connections. Also remove the
1kΩ resistor between each headphone connection and
ground. Finally, remove any resistors connected to the
HP-IN pin (typically two 100kΩ resistors). Connect the HP-IN
pin directly to the headphone jack control pin as shown in

Figure 4

.

DS200013-56

FIGURE 2. Differential output signal (Trace B) is devoid

of transients. The SHUTDOWN pin is driven by a

shutdown signal (Trace A). The inverting output (Trace

C) and the non-inverting output (Trace D) are applied

across an 8Ω BTL load.

LM4867

www.national.com9

Application Information (Continued)

The LM4867’s pin configuration simplifies the process of
upgrading systems that use the LM4863. Except for its four
MUX function pins, the LM4867’s pin configuration matches
the LM4863’s pin configuration. If the LM4867’s MUX func­tionality is not needed when replacing an LM4863, connect
the MUX CTRL pin to either V

DD

or ground. To ensure

correct amplifier operation, unused MUX inputs must be
tied to GND. As shown in Table1, grounding the MUX CTRL

pin selects stereo input 1 (−IN A1 and −IN B1), whereas
applying V

DD

to the MUX CTRL pin selects stereo input 2

(−IN A2 and −IN B2).
The LM4867’s unique headphone sense circuit requires a

dual switch headphone jack. Replace the four-terminal head­phone jack used with the LM4863 and LM4873 with the
five-terminal headphone jack, such as the Switchcraft
35RAPC4BH3, shown in Figure 4. Connect the +OUT A
(Amp2A) pin to the five-terminal headphone jack’s sleeve
pin.

DS200013-57

FIGURE 3. Single-ended output signal (Trace B) is

devoid of transients. The SHUTDOWN pin is driven by

a shutdown signal (Trace A). The inverting output

(Trace C) and the V

BYPASS

output (Trace D) are applied

across a 32Ω BTL load.

DS200013-31

FIGURE 4. Typical Audio Amplifier Application Circuit

(Pin out shown for the 24-pin Exposed-DAP LLP package. Numbers in ( ) are for the 20-pin MTE and MT packages.)

LM4867

www.national.com 10

Application Information (Continued)

STEREO-INPUT MULTIPLEXER (STEREO MUX)

The LM4867 has two stereo inputs. The MUX CTRL Pin
controls which stereo input is active. As shown in the Truth
Tablefor Logic Inputs, applying 0V to the MUX CTRL input
activates stereo input 1, whereas applying V

DD

to the MUX

CTRL inputs activates stereo input 2. To ensure correct

amplifier operation, unused MUX inputs must be tied to
GND.

TypicalLM4867 applications use the MUX to switch between
two stereo input signals. Each stereo channel’s gain can be
tailored to produce the required output signal level by choos­ing the appropriate input and feedback resistor ratio.

Another configuration uses the MUX to select two different
gains or frequency compensated gains that amplify a single
pair of stereo input signals.

Figure 5

shows two different
feedback networks, Network 1 and Network 2. Network 1
produces increasing gain as the input signal’s frequency

decreases. This can be used to compensate a small,
full-range speaker’s low frequency response roll-off. Network
2 sets the gain for an alternate load such as headphones.
The circuit in

Figure 6

uses Network 1 when driving external
speakers, switching to Network 2 when headphones are
connected. The normally closed control switch in

Figure 6

’s
headphone jack connects to the MUX CTRL pin. When
headphones are connected, the LM4867’s internal pull-up
that applies V

DD

to the HP-IN and the external 100kΩ resis-

tor applies V

DD

to MUX CTRL pin. Simultaneously applying
these control voltages automatically selects the amplifier
(headphone or bridge) and switches the gain (MUX channel
selection).Alternatively,leaving the MUX CTRL pin indepen­dently accessible allows a user to select bass boost as
needed. This alternative user-selectable bass-boost scheme
requires connecting equal ratio resistor feedback networks
to each MUX input channel. The value of the resistor in the
RC network is chosen to give a gain that is necessary to
achieve the desired bass-boost.

Switching between the MUX channels may change the input
signal source or the feedback resistor network. During the
channel switching transition, the average voltage level
present on the internal amplifier’s input may change. This
change can slew at a rate that may produce audible voltage
transients or clicks in the amplifier’s output signal. Using the
MUX to select between two vastly dissimilar gains is a typical
transient-producing situation. As the MUX is switched, an
audible click may occur as the gain suddenly changes.

PIN OUT COMPATIBILITY WITH THE LM4863

The LM4867 pin out was designed to simplify replacing the
LM4863: except for the four Pins(-INA

2

, MUX CTRL, -IN B2,
and NC) that implement the LM4867’s extra functionality,the
LM4867MT/MTE and LM4863MT/MTE pin outs match.
(Note 22)

Note 22: If the LM4867 replaces an LM4863 and the input MUX circuitry is
not being used, the LM4867 MUX CTRL pin must be tied to V

DD

or GND and

the unused MUX inputs must be connected to GND.

EXPOSED-DAP MOUNTING CONSIDERATIONS

The LM4867’s exposed-DAP (die attach paddle) packages
(MTE and LQ) provide a low thermal resistance between the
die and the PCB to which the part is mounted and soldered.
This allows rapid heat transfer from the die to the surround­ing PCB copper area heatsink, copper traces, ground plane,
and finally, surrounding air. The result is a low voltage audio

power amplifier that produces 2.4W dissipation in a 4Ω load
at ≤ 1% THD+N and over 3W in a 3Ω load at 10% THD+N.
This high power is achieved through careful consideration of
necessary thermal design. Failing to optimize thermal design
may compromise the LM4867’s high power performance and
activate unwanted, though necessary, thermal shutdown
protection.

DS200013-70

FIGURE 5. Input MUX Example

DS200013-39

FIGURE 6. As configured, connecting headphones to this jack automatically selects the stereo headphone amplifier

and, with the additional NC switch, changes MUX channels (Network 2 in Figure 2 )

LM4867

www.national.com11

Application Information (Continued)

The MTE and LQ packages must have their DAPs soldered
to a copper pad on the PCB. The DAP’s PCB copper pad is
then, ideally, connected to a large plane of continuous un­broken copper. This plane forms a thermal mass, heat sink,
and radiation area. Place the heat sink area on either outside
plane in the case of a two-sided or multi-layer PCB. (The
heat sink area can also be placed on an inner layer of a
multi-layer board. The thermal resistance, however, will be
higher.) Connect the DAP copper pad to the inner layer or
backside copper heat sink area with 32 (4 X 8) (MTE) or 6 (3
X 2) (LQ) vias. The via diameter should be 0.012in - 0.013in
with a 1.27mm pitch. Ensure efficient thermal conductivity by
plugging and tenting the vias with plating and solder mask,
respectively.

Best thermal performance is achieved with the largest prac­tical copper heat sink area. If the heatsink and amplifier
share the same PCB layer, a nominal 2.5in

2

(min) area is
necessary for 5V operation with a 4Ω load. Heatsink areas
not placed on the same PCB layer as the LM4867 should be
5in

2

(min) for the same supply voltage and load resistance.
The last two area recommendations apply for 25˚C ambient
temperature. Increase the area to compensate for ambient
temperatures above 25˚C. In systems using cooling fans, the
LM4867MTE can take advantage of forced air cooling. With
an air flow rate of 450 linear-feet per minute and a 2.5in

2

exposed copper or 5.0in2inner layer copper plane heatsink,
the LM4867MTE can continuously drive a 3Ω load to full
power. The LM4867LQ achieves the same output power
level without forced-air cooling. In all circumstances and
under all conditions, the junction temperature must be held
below 150˚C to prevent activating the LM4867’s thermal
shutdown protection. The LM4867’s power de-rating curve in
the Typical Performance Characteristics shows the maxi­mum power dissipation versus temperature. Example PCB
layouts for the exposed-DAP TSSOP and LQ packages are
shown in the Demonstration Board Layout section. Further
detailed and specific information concerning PCB layout and
fabrication and mounting an LQ (LLP) is found in National
Semiconductor’s AN1187.

PCB LAYOUT AND SUPPLY REGULATION
CONSIDERATIONS FOR DRIVING 3Ω AND 4Ω LOADS

Power dissipated by a load is a function of the voltage swing
across the load and the load’s impedance. As load imped­ance decreases, load dissipation becomes increasingly de­pendent on the interconnect (PCB trace and wire) resistance
between the amplifier output pins and the load’s connec­tions. Residual trace resistance causes a voltage drop,
which results in power dissipated in the trace and not in the
load as desired. For example, 0.1Ω trace resistance reduces
the output power dissipated by a 4Ω load from 2.1W to 2.0W.
The problem of decreased load dissipation is exacerbated
as load impedance decreases. Therefore, to maintain the
highest load dissipation and widest output voltage swing,
PCB traces that connect the output pins to a load must be as
wide as possible.

Poor power supply regulation adversely affects maximum
output power. A poorly regulated supply’s output voltage
decreases with increasing load current. Reduced supply
voltage causes decreased headroom, output signal clipping,
and reduced output power. Even with tightly regulated sup­plies, trace resistance creates the same effects as poor
supply regulation. Therefore, making the power supply
traces as wide as possible helps maintain full output voltage
swing.

BRIDGE CONFIGURATION EXPLANATION

As shown in

Figure 4

, the LM4867 consists of two pairs of
operational amplifiers, forming a two-channel (channel A and
channel B) stereo amplifier. (Though the following discusses
channelA, it applies equally to channel B.) External resistors
R

f

and Riset the closed-loop gain of Amp1A, whereas two
internal 20kΩ resistors set Amp2A’s gain at -1. The LM4867
drives a load, such as a speaker,connected between the two
amplifier outputs, -OUTA and +OUTA.

Figure 4

shows that Amp1A’s output serves as Amp2A’s
input. This results in both amplifiers producing signals iden­tical in magnitude, but 180˚ out of phase. Taking advantage
of this phase difference, a load is placed between -OUTA
and +OUTA and driven differentially (’commonly referred to
as bridge mode’). This results in a differential gain of

A

VD

=2*(Rf/Ri) (1)

Bridge mode amplifiers are different from single-ended am­plifiers that drive loads connected between a single amplifi­er’s output and ground. For a given supply voltage, bridge
mode has a distinct advantage over the single-ended con­figuration: its differential output doubles the voltage swing
across the load. This produces four times the output power
when compared to a single-ended amplifier under the same
conditions. This increase in attainable output power as­sumes that the amplifier is not current limited or that the
output signal is not clipped. To ensure minimum output sig­nal clipping when choosing an amplifier’s closed-loop gain,
refer to the Audio Power Amplifier Design section.

A bridge amplifier design has a few distinct advantages over
the single-ended configuration, as it provides differential
drive to the load, thus doubling the output swing for a speci­fied supply voltage. Four times the output power is possible
as compared to a single-ended amplifier under the same
conditions. This increase in attainable output power as­sumes that the amplifier is not current limited or clipped. In
order to choose an amplifier’s closed-loop gain without caus­ing excessive clipping, please refer to the Audio Power
Amplifier Design section.

Another advantage of the differential bridge output is no net
DC voltage across the load. This is accomplished by biasing
channel A’s and channel B’s outputs at half-supply. This
eliminates the coupling capacitor that single supply,
single-ended amplifiers require. Eliminating an output cou­pling capacitor in a single-ended configuration forces a
single-supply amplifier’s half-supply bias voltage across the
load. This increases internal IC power dissipation and may
permanently damage loads such as speakers.

POWER DISSIPATION

Power dissipation is a major concern when designing a
successful single-ended or bridged amplifier. Equation (2)
states the maximum power dissipation point for a
single-ended amplifier operating at a given supply voltage
and driving a specified output load.

P

DMAX

=(VDD)2/(2π2RL): Single-Ended (2)

However, a direct consequence of the increased power de­livered to the load by a bridge amplifier is higher internal
power dissipation for the same conditions.

The LM4867 has two operational amplifiers per channel. The
maximum internal power dissipation per channel operating in

LM4867

www.national.com 12

Application Information (Continued)

the bridge mode is four times that of a single-ended ampli­fier. From Equation (3), assuming a 5V power supply and an
4Ω load, the maximum single channel power dissipation is

1.27W or 2.54W for stereo operation.

P

DMAX

=4*(VDD)2/(2π2RL): Bridge Mode (3)

The LM4867’s power dissipation is twice that given by Equa­tion (2) or Equation (3) when operating in the single-ended
mode or bridge mode, respectively. Twice the maximum
power dissipation point given by Equation (3) must not ex­ceed the power dissipation given by Equation (4):

P

DMAX

’=(T

JMAX−TA

)/θ

JA

(4)

The LM4867’s TJMAX = 150˚C. In the LQ package soldered
to a DAP pad that expands to a copper area of 5in

2

on a

PCB, the LM4867’s θ

JA

is 20˚C/W. In the MTE package

soldered to a DAP pad that expands to a copper area of 2in

2

on a PCB, the LM4867’s θJAis 41˚C/W.At any given ambient
temperature T

A

, use Equation (4) to find the maximum inter­nal power dissipation supported by the IC packaging. Rear­ranging Equation (4) and substituting P

DMAX

for P

DMAX

’ re­sults in Equation (5). This equation gives the maximum
ambient temperature that still allows maximum stereo power
dissipation without violating the LM4867’s maximum junction
temperature.

T

A=TJMAX

−2XP

DMAXθJA

(5)

For a typical application with a 5V power supply and an 4Ω
load, the maximum ambient temperature that allows maxi­mum stereo power dissipation without exceeding the maxi­mum junction temperature is approximately 99˚C for the LQ
package and 45˚C for the MTE package.

T

JMAX=PDMAXθJA+TA

(6)

Equation (6) gives the maximum junction temperature
T

JMAX

. If the result violates the LM4867’s 150˚C, reduce the
maximum junction temperature by reducing the power sup­ply voltage or increasing the load resistance. Further allow­ance should be made for increased ambient temperatures.

The above examples assume that a device is a surface
mount part operating around the maximum power dissipation
point. Since internal power dissipation is a function of output
power, higher ambient temperatures are allowed as output
power or duty cycle decreases.

If the result of Equation (2) is greater than that of Equation
(3), then decrease the supply voltage, increase the load
impedance, or reduce the ambient temperature. If these
measures are insufficient, a heat sink can be added to
reduce θ

JA

. The heat sink can be created using additional
copper area around the package, with connections to the
ground pin(s), supply pin and amplifier output pins. External,
solder attached SMT heatsinks such as the Thermalloy
7106D can also improve power dissipation. When adding a
heat sink, the θ

JA

is the sum of θJC, θCS, and θSA.(θJCis the

junction−to−case thermal impedance, θ

CS

is the

case−to−sink thermal impedance, and θ

SA

is the
sink−to−ambient thermal impedance.) Refer to the Typical
Performance Characteristics curves for power dissipation
information at lower output power levels.

POWER SUPPLY BYPASSING

As with any power amplifier, proper supply bypassing is
critical for low noise performance and high power supply
rejection. Applications that employ a 5V regulator typically
use a 10µF in parallel with a 0.1µF filter capacitors to stabi­lize the regulator’s output, reduce noise on the supply line,
and improve the supply’s transient response. However, their
presence does not eliminate the need for a local 1.0µF
tantalum bypass capacitance connected between the
LM4867’s supply pins and ground. Do not substitute a ce­ramic capacitor for the tantalum. Doing so may cause oscil­lation. Keep the length of leads and traces that connect
capacitors between the LM4867’s power supply pin and
ground as short as possible. Connecting a 1µF capacitor,
C

B

, between the BYPASS pin and ground improves the
internal bias voltage’s stability and improves the amplifier’s
PSRR. The PSRR improvements increase as the bypass pin
capacitor value increases. Too large, however, increases
turn−on time and can compromise the amplifier’s click and
pop performance. The selection of bypass capacitor values,
especially C

B

, depends on desired PSRR requirements,
click and pop performance (as explained in the section,
Proper Selection of External Components), system cost,
and size constraints.

MICRO−POWER SHUTDOWN

The voltage applied to the SHUTDOWN pin controls the
LM4867’s shutdown function. Activate micro−power shut­down by applying V

DD

to the SHUTDOWN pin. When active,
the LM4867’s micro−power shutdown feature turns off the
amplifier’s bias circuitry, reducing the supply current. The
logic threshold is typically V

DD

/2. The low 0.7µA typical
shutdown current is achieved by applying a voltage that is as
near as V

DD

as possible to the SHUTDOWN pin. A voltage

that is less than V

DD

may increase the shutdown current.
Table 1 shows the logic signal levels that activate and deac­tivate micro−power shutdown and headphone amplifier op­eration. To ensure that the output signal remains

transient−free, do not cycle the shutdown function
faster than 1Hz.

There are a few ways to control the micro−power shutdown.
These include using a single−pole, single, throw switch, a
microprocessor, or a microcontroller. When using a switch,
connect an external 100kΩ pull−up resistor between the
SHUTDOWN pin and V

DD

. Connect the switch between the
SHUTDOWN pin and ground. Select normal amplifier opera­tion by closing the switch. Opening the switch connects the
SHUTDOWN pin to V

DD

through the pull−up resistor, acti­vating micro−power shutdown. The switch and resistor guar­antee that the SHUTDOWN pin will not float. This prevents
unwanted state changes. In a system with a microprocessor
or a microcontroller, use a digital output to apply the control
voltage to the SHUTDOWN pin. Driving the SHUTDOWN pin
with active circuitry eliminates the pull up resistor.

LM4867

www.national.com13

Application Information (Continued)
Truth Table for Logic Inputs

SHUTDOWN

PIN

HP-IN

PIN

MUX CHANNEL

INPUT SELECT

OPERATIONAL MODE (MUX

INPUTCHANNEL #)

Logic Low = −OUTB signal Logic Low Bridged amplifiers (1)
Logic Low = −OUTB signal Logic High Bridged amplifiers (2)
Logic Low

≠

−OUTB signal Logic Low Single-ended amplifiers (1)

Logic Low

≠

−OUTB signal Logic High Single-ended amplifiers (2)

Logic High X X Micro−power shutdown

HP-IN FUNCTION

An internal pull−up circuit is connected to the HP−IN (pin 20)
headphone amplifier control pin. When this pin is left uncon­nected, V

DD

is applied to the HP−IN. This turns off Amp2B
and switches Amp2A’s input signal from an audio signal to
the V

DD

/2 voltage present on pin 14. The result is muted
bridge-connected loads. Quiescent current consumption is
reduced when the IC is in this single−ended mode.

Figure 7

shows the implementation of the LM4867’s head­phone control function. An internal comparator with a nomi­nal 400mV offset monitors the signal present at the −OUTB
output. It compares this signal against the signal applied to
the HP−IN pin. When these signals are equal, as is the case
when a BTL is connected to the amplifier, the comparator
forces the LM4867 to maintain bridged−amplifier operation.
When the HP−IN pin is externally floated, such as when
headphones are connected to the jack shown in

Figure 7

,

and internal pull−up forces V

DD

on the internal comparator’s
HP−IN inputs. This changes the comparator’s output state
and enables the headphone function: it turns off Amp2B,
switches Amp2A’s input signal from an audio signal to the
V

DD

/2 voltage present on pin 14, and mutes the
bridge-connected loads. Amp1A and Amp1B drive the head­phones.

Figure 7

also shows the suggested headphone jack electri­cal connections. The jack is designed to mate with a
three−wire plug. The plug’s tip and ring should each carry
one of the two stereo output signals, whereas the sleeve
provides the return to Amp2A. A headphone jack with one
control pin contact is sufficient to drive the HP−IN pin when
connecting headphones.

A switch can replace the headphone jack contact pin. When
a switch shorts the HP−IN pin to V

DD

, bridge−connected

speakers are muted and Amp1A and Amp2A drive a pair of

headphones. When a switch shorts the HP−IN pin to GND,
the LM4867 operates in bridge mode. If headphone drive is
not needed, short the HP−IN pin to the −OUTB pin.

Single-Ended Output Power Performance and
Measurement Considerations

The LM4867 delivers clean, low distortion SE output power
into loads that are greater than 10Ω. As an example, output
power for 16Ω and 32Ω loads are shown in the Typical
Performance Characteristic curves. For loads less than
10Ω, the LM4876 can typically supply 180mW of low distor­tion power. However, when higher dissipation is desired in
loads less than 10Ω, a dramatic increase in THD+N may
occur. This is normal operation and does not indicate that
proper functionality has ceased. When a jump from moder­ate to excessively high distortion is seen, simply reducing
the output voltage swing will restore the clean, low distortion
SE operation.

The dramatic jump in distortion for loads less than 10Ω
occurs when current limiting circuitry activates. During SE
operation, AMP2A (refer to

Figure 4

) drives the headphone
sleeve. An on-board circuit monitors this amplifier’s output
current. The sudden increase in THD+N is caused by the
current limit circuitry forcing AMP2A into a high−impedance
output mode. When this occurs, the output waveform has
discontinuities that produce large amounts of distortion. It
has been observed that as the output power is steadily
increased, the distortion may jump from 5% to greater than
35%. Indeed, 10% THD+N may not actually be achievable.

Using the Single−Ended Output for Line Level
Applications

Some samples of the LM4867 may exhibit small amplitude,
high frequency oscillation when the SE output is connected
to a line-level input. This oscillation can be eliminated by
connecting a 5%, 300Ω resistor betweenAmp2A’s output pin
and each amplifier, AMP1A and AMP1B, output.

LM4867

www.national.com 14

Application Information (Continued)

Input Capacitor Value Selection

Amplifying the lowest audio frequencies requires high value
input coupling capacitor (C

i

in

Figure 4

).A high value capaci­tor can be expensive and may compromise space efficiency
in portable designs. In many cases, however, the speakers
used in portable systems, whether internal or external, have
little ability to reproduce signals below 150Hz. Applications
using speakers with this limited frequency response reap
little improvement by using large input capacitor.

Besides effecting system cost and size, C

i

has an affect on
the LM4867’s click and pop performance. When the supply
voltage is first applied, a transient (pop) is created as the
charge on the input capacitor changes from zero to a quies­cent state. The magnitude of the pop is directly proportional
to the input capacitor’s size. Higher value capacitors need
more time to reach a quiescent DC voltage (usually V

DD

/2)
when charged with a fixed current. The amplifier’s output
charges the input capacitor through the feedback resistor,
R

f

. Thus, pops can be minimized by selecting an input
capacitor value that is no higher than necessary to meet the
desired −3dB frequency and is between 0.14C

B

and 0.20CB.

A shown in

Figure 4

, the input resistor (RI) and the input

capacitor,C

I

produce a −3dB high pass filter cutoff frequency

that is found using Equation (7).

f

−3dB

= 1/(2πRINCI) (7)

As an example when using a speaker with a low frequency
limit of 150Hz, C

i

, using Equation (4) is 0.063µF. The 1.0µF

C

i

shown in

Figure 4

allows the LM4867 to drive high effi­ciency, full range speaker whose response extends below
30Hz.

Bypass Capacitor Value Selection

Besides minimizing the input capacitor size, careful consid­eration should be paid to value of C

B

, the capacitor con-

nected to the BYPASS pin. Since C

B

determines how fast
the LM4867 settles to quiescent operation, its value is critical
when minimizing turn-on pops. The slower the LM4867’s
outputs ramp to their quiescent DC voltage (nominally 1/2
V

DD

), the smaller the turn-on pop. Choosing CBequal to

1.0µF along with a small value of C

i

(in the range of 0.1µF to

0.39µF), produces a click-less and pop-less shutdown func­tion. As discussed above, choosing C

i

no larger than neces-

sary for the desired bandwidth helps minimize clicks and
pops. C

B

’s value should be in the range of 5 times to 7 times

the value of C

i

. This ensures that output transients are
eliminated when power is first applied or the LM4867 re­sumes operation after shutdown.

OPTIMIZING CLICK AND POP REDUCTION
PERFORMANCE

The LM4867 contains circuitry that eliminates turn-on and
shutdown transients (“clicks and pops“) and transients that
could occur when switching between BTL speakers and
single-ended headphones. For this discussion, turn-on re­fers to either applying the power supply voltage or when the
shutdown mode is deactivated. While the power supply is
ramping to its final value, the LM4867’s internal amplifiers
are configured as unity gain buffers and are disconnected
from the -OUT and +OUT pins. An internal current source
changes the voltage of the BYPASS pin in a controlled,
linear manner.Ideally, the input and outputs track the voltage
applied to the BYPASS pin. The gain of the internal amplifi­ers remains unity until the voltage on the bypass pin reaches
1/2 V

DD

. As soon as the voltage on the bypass pin is stable,
the device becomes fully operational and the amplifier out­puts are reconnected to the -OUT and +OUT pins. Although
the BYPASS pin current cannot be modified, changing the
size of C

B

alters the device’s turn-on time. There is a linear

relationship between the size of C

B

and the turn-on time.

Here are some typical turn-on times for various values of C

B

:

C

B

T

ON

0.01µF 3ms

0.1µF 30ms

0.22µF 63ms

0.47µF 134ms

1.0µF 300ms

2.2µF 630ms

In order eliminate “clicks and pops“, all capacitors must be
discharged before turn-on. Rapidly switching V

DD

may not
allow the capacitors to fully discharge, which may cause
“clicks and pops“.

DS200013-24

FIGURE 7. Headphone Circuit

(Pin numbers in ( ) are for the 20-pin MTE and MT packages.)

LM4867

www.national.com15

Application Information (Continued)

NO LOAD STABILITY

The LM4867 may exhibit low level oscillation when the load
resistance is greater than 10kΩ. This oscillation only occurs
as the output signal swings near the supply voltages. Pre­vent this oscillation by connecting a 5kΩ between the output
pins and ground.

AUDIO POWER AMPLIFIER DESIGN
Audio Amplifier Design: Driving 1W into an 8Ω Load

The following are the desired operational parameters:

Power Output: 1 W

RMS

Load Impedance: 8Ω
Input Level: 1 V

RMS

Input Impedance: 20 kΩ

Bandwidth: 100 Hz−20 kHz

±

0.25 dB

The design begins by specifying the minimum supply voltage
necessary to obtain the specified output power. One way to
find the minimum supply voltage is to use the Output Power
vs Supply Voltage curve in the Typical Performance Char-
acteristics section. Another way, using Equation (8), is to
calculate the peak output voltage necessary to achieve the
desired output power for a given load impedance. To ac­count for the amplifier’s dropout voltage, two additional volt­ages, based on the Dropout Voltage vs Supply Voltagein the
Typical Performance Characteristics curves, must be
added to the result obtained by Equation (8). The result is
Equation (9).

(8)

V

DD

≥ (V

OUTPEAK

+(V

OD

TOP

+V

OD

BOT

)) (9)

The Output Power vs Supply Voltage graph for an 8Ω load
indicates a minimum supply voltage of 4.6V. This is easily
met by the commonly used 5V supply voltage. The additional
voltage creates the benefit of headroom, allowing the
LM4867 to produce peak output power in excess of 1W
without clipping or other audible distortion. The choice of
supply voltage must also not create a situation that violates
of maximum power dissipation as explained above in the
Power Dissipation section.

After satisfying the LM4867’s power dissipation require­ments, the minimum differential gain needed to achieve 1W
dissipation in an 8Ω load is found using Equation (10).

(10)

Thus, a minimum gain of 2.83 allows the LM4867’s to reach
full output swing and maintain low noise and THD+N perfor­mance. For this example, let A

VD

=3.

The amplifier’s overall gain is set using the input (R

i

) and

feedback (R

i

) resistors. With the desired input impedance
set at 20kΩ, the feedback resistor is found using Equation
(11).

R

f/Ri=AVD

/2 (11)

The value of R

f

is 30kΩ.

The last step in this design example is setting the amplifier’s

−3dB frequency bandwidth. To achieve the desired

±

0.25dB
pass band magnitude variation limit, the low frequency re­sponse must extend to at least one-fifth the lower bandwidth
limit and the high frequency response must extend to at least
five times the upper bandwidth limit. The gain variation for
both response limits is 0.17dB, well within the

±

0.25dB
desired limit. The results are an

f

L

= 100Hz/5 = 20Hz (12)

and an

f

H

= 20kHz x 5 = 100kHz (13)

As mentioned in the Selecting Proper External Compo-
nents section, R

i

and Cicreate a highpass filter that sets the
amplifier’s lower bandpass frequency limit. Find the coupling
capacitor’s value using Equation (12).

C

i

≥ 1/(2πRifL) (14)

The result is

1/(2π

*

20kΩ*20Hz) = 0.397µF (15)

Use a 0.39µF capacitor, the closest standard value.

The product of the desired high frequency cutoff (100kHz in
this example) and the differential gain A

VD

, determines the

upper passband response limit. With A

VD

= 3 and fH=
100kHz, the closed-loop gain bandwidth product (GBWP) is
300kHz. This is less than the LM4867’s 3.5MHz GBWP.With
this margin, the amplifier can be used in designs that require
more differential gain while avoiding performance,restricting
bandwidth limitations.

RECOMMENDED PRINTED CIRCUIT BOARD LAYOUT

Figures 8 through 12 show the recommended four-layer PC
board layout that is optimized for the 24-pin LQ-packaged
LM4867 and associated external components. Figures 13
through 17 show the recommended two-layer PC board
layout that is optimized for the 24-pin MTE-packaged
LM4867 and associated external components. Figures 18
through 20 show the recommended two-layer PC board
layout that is optimized for the 20-pin MT-packaged LM4867
and associated external components. These circuits are de­signed for use with an external 5V supply and 4Ω speakers.

These circuit boards are easy to use.Apply 5V and ground to
the board’s V

DD

and GND pads, respectively. Connect 4Ω
speakers between the board’s −OUTA and +OUTA and
OUTB and +OUTB pads.

LM4867

www.national.com 16

Application Information (Continued)

DS200013-40

Figure 8. Recommended LQ PC Board Layout:

Component-Side Silkscreen

DS200013-41

Figure 9. Recommended LQ PC Board Layout:

Component-Side Layout

LM4867

www.national.com17

Application Information (Continued)

DS200013-42

Figure 10. Recommended LQ PC Board Layout:

Upper Inner-Layer Layout

DS200013-43

Figure 11. Recommended LQ PC Board Layout:

Lower Inner-Layer Layout

LM4867

www.national.com 18

Application Information (Continued)

DS200013-44

Figure 12. Recommended LQ PC Board Layout:

Bottom-Side Layout

DS200013-45

Figure 13. Recommended MTE PC Board Layout:

Component-Side Silkscreen

LM4867

www.national.com19

Application Information (Continued)

DS200013-46

Figure 14. Recommended MTE PC Board Layout:

Component-Side Layout

DS200013-47

Figure 15. Recommended MTE PC Board Layout:

Upper Inner-Layer Layout

LM4867

www.national.com 20

Application Information (Continued)

DS200013-48

Figure 16. Recommended MTE PC Board Layout:

Lower Inner-Layer Layout

DS200013-49

Figure 17. Recommended MTE PC Board Layout:

Bottom-Side Layout

LM4867

www.national.com21

Application Information (Continued)

DS200013-50

Figure 18. Recommended MT PC Board Layout:

Component-Side Silkscreen

DS200013-51

Figure 19. Recommended MT PC Board Layout:

Component-Side Layout

LM4867

www.national.com 22

Application Information (Continued)

DS200013-52

Figure 20. Recommended MT PC Board Layout:

Bottom-Side Layout

LM4867

www.national.com23

Physical Dimensions inches (millimeters) unless otherwise noted

24-Lead MOLDED PKG, Leadless Leadframe Package LLP

Order Number LM4867LQ

NS Package Number LQA24A

20-Lead MOLDED PKG, TSSOP, JEDEC, 4.4mm BODY WIDTH

Order Number LM4867MT

NS Package Number MTC20

LM4867

www.national.com 24

Physical Dimensions inches (millimeters) unless otherwise noted (Continued)

20-Lead MOLDED TSSOP, EXPOSED PAD, 6.5x4.4x0.9mm

Order Number LM4867MTE

NS Package Number MXA20A

LM4867

www.national.com25

Notes

LIFE SUPPORT POLICY

NATIONAL’S PRODUCTS ARE NOT AUTHORIZED FOR USE AS CRITICAL COMPONENTS IN LIFE SUPPORT
DEVICES OR SYSTEMS WITHOUT THE EXPRESS WRITTEN APPROVAL OF THE PRESIDENT AND GENERAL
COUNSEL OF NATIONAL SEMICONDUCTOR CORPORATION. As used herein:

1. Life support devices or systems are devices or
systems which, (a) are intended for surgical implant
into the body, or (b) support or sustain life, and
whose failure to perform when properly used in
accordance with instructions for use provided in the
labeling, can be reasonably expected to result in a
significant injury to the user.

2. A critical component is any component of a life
support device or system whose failure to perform
can be reasonably expected to cause the failure of
the life support device or system, or to affect its
safety or effectiveness.

National Semiconductor
Corporation

Americas
Tel: [phone]
Fax: [phone]
Email: [e-mail]

National Semiconductor
Europe

Fax: [phone]

Email: [e-mail]
Deutsch Tel: [phone]
English Tel: [phone]
Français Tel: [phone]

National Semiconductor
Asia Pacific Customer
Response Group

Tel: [phone]
Fax: [phone]
Email: [e-mail]

National Semiconductor
Japan Ltd.

Tel: [phone]
Fax: [phone]

www.national.com

LM4867 Output-Transient-Free Dual 2.1W Audio Amplifier Plus No Coupling Capacitor Stereo

Headphone Function

National does not assume any responsibility for use of any circuitry described, no circuit patent licenses are implied and National reserves the right at any time without notice to change said circuitry and specifications.