Datasheet CLC5644IN, CLC5644IMX Datasheet (NSC)

Features

■

170MHz small signal bandwidth

■

1000 V/µs slew rate

■

2.5mA / channel supply current

■

-72/-79dBc HD2/HD3 (5MHz)

■

0.04%, 0.07° differential gain, phase

■

70mA output current

■

16ns settling to 0.1%

Applications

■

Portable equipment

■

Video switchers & routers

■

Video line driver

■

Active filters

■

IF amplifier

■

Twisted pair driver/receiver

Typical Configurations

Non-Inverting Gain Inverting Gain

Pinout

DIP & SOIC

General Description

The CLC5644 is a quad, current feedback operational amplifier
that is perfect for many cost-sensitive applications that require
high performance, especially when power dissipation is critical.
Not only does the CLC5644 offer excellent economy in board
space, but has an excellent performance vs power tradeoff which
yields a 170MHz Small Signal Bandwidth while dissipating only
25mW. Applications requiring significant density of high speed
devices such as video routers, matrix switches and high-order
active filters will benefit from the configuration of the CLC5644 and
the low channel-to-channel crosstalk of 76dB at 1MHz.

The CLC5644 provides excellent performance for video
applications. Differential gain and phase of 0.04% and 0.07°
makes this device well suited for many professional composite
video systems, but consumer applications will also be able to tak e
advantage of these features due to the device’s low cost. The
CLC5644 offers superior dynamic performance with a small
signal bandwidth of 170MHz and slew rate of 1000V/µs. These
attributes are well suited for many component video applications
such as driving RGB signals down significant lengths of cable.
These and many other applications can also take advantage of
the 0.1dB flatness to 25MHz.

Combining wide bandwidth with low cost makes the the CLC5644
an attractive option for active filters. SAW filters are often used
in IF filters in the 10’s of MHz range, but higher order filters
designed around a quad operational amplifier may offer an
economical alternative to the typical SAW approach and offer
greater freedom in the selection of filter parameters. National
Semiconductor’s Comlinear Products Group has published a
wide array of liturature on active filters and a list of these
publications can be found on the last page of this datasheet.

CLC5644
Low-Power, Low-Cost, Quad Operational Amplifier

N

June 1999

CLC5644

Low-Power, Low-Cost, Quad Operational Amplifier

© 1999 National Semiconductor Corporation http://www.national.com

Printed in the U.S.A.

Non-Inverting Frequency Response

Vo = 0.25V

pp

Av = +1

Rf = 6.98kΩ

Av = +5

Rf = 499Ω

Av = +10

Normalized Magnitude (0.5dB/div)

1M

Rf = 249Ω

10M

Frequency (Hz)

Av = +2

Rf = 1.65kΩ

100M

V

CC

6.8µF

+

V

in

R

t

R

g

V

o

A1

==+

V

in

R

v

f

R

g

+

1/4

CLC5644

-

V

EE

0.1µF

R

f

0.1µF

6.8µF

V

o

+

V

in

R

t

V

o

A

==−

V

in

R

b

R

g

v

V

CC

6.8µF

+

0.1µF

+

1/4

CLC5644

­R

f

0.1µF

R

f

R

g

V

EE

+

6.8µF

V

o

Note: Rb provides DC bias
for the non-inverting input.

Select R

to yield desired

t

Rin = Rt || Rg.

http://www.national.com 2

PARAMETERS CONDITIONS TYP MIN/MAX RATINGS UNITS NOTES
Ambient Temperature CLC5644I +25°C +25°C -40 to 85°C

FREQUENCY DOMAIN RESPONSE

-3dB bandwidth A

v

= 1 170 – – MHz

V

o

< 0.5V

pp

125 – – MHz

V

o

< 5V

pp

50 – – MHz

0.1dB bandwidth 25 – – MHz
differential gain NTSC, R

L

= 150Ω 0.04 – – dB

differential phase NTSC, R

L

= 150Ω 0.07 – – dB

TIME DOMAIN RESPONSE

rise and fall time 0.5V step 2.7 – – ns

5V step 7 – – ns
settling time to 0.1% 1V step 16 – – ns
overshoot 0.5V step 4 – – %
slew rate 1000 – – V/µs

DISTORTION AND NOISE RESPONSE

2ndharmonic distortion 2Vpp, 1MHz -72 – – dBc
3

rd

harmonic distortion 2Vpp, 1MHz -79 – – dBc

equivalent input noise

voltage (e

ni

) >1MHz 4.5 – – nV/√Hz

non-inverting current (i

bn

) >1MHz 1.5 – – pA/√Hz

inverting current (i

bi

) >1MHz 10 – – pA/√Hz

crosstalk (input inferred) 10MHz 76 – – dBc

STATIC DC PERFORMANCE

input offset voltage 2.5 7 15 mV A

average drift 25 – 90 µV/˚C

input bias current (non-inverting) 2 6 10 µAA

average drift 15 – 80 nA/˚C

input bias current (inverting) 2.5 7.5 22 µAA

average drift 24 – 150 nA/˚C
power supply rejection ratio DC 50 46 44 dB
common-mode rejection ratio DC 50 45 43 dB
supply current (per channel) R

L

= ∞ 2.5 3 3 mA A

MISCELLANEOUS PERFORMANCE

input resistance (non-inverting) 2 1 0.5 MΩ
input capacitance (non-inverting) 1 2 2 pF
common-mode input range ±2.2 ±2.0 ±1.4 V
output voltage range R

L

= 150Ω ±2.8 ±2.6 ±2.5 V
output current 70 50 30 mA
output resistance, closed loop DC 0.2 0.3 0.6 mΩ

Min/max ratings are based on product characterization and simulation. Individual parameters are tested as noted. Outgoing quality levels are
determined from tested parameters.

CLC5644 Electrical Characteristics

(Av= +2, Rf= 1.65kΩ,RL= 100Ω,Vs= ±5V, unless specified)

Absolute Maximum Ratings

supply voltage (VCC- VEE)

+

14V
output current 95mA
common-mode input voltage

VEEto

V

CC

maximum junction temperature +150°C
storage temperature range -65°C to +150°C
lead temperature (soldering 10 sec) +300°C

Notes

A) I-level:spec is 100% tested at +25°C.

Reliability Information

Transistor Count 152
MTBF (based on limited test data) 23.6Mhr

Ordering Information

Model Temperature Range Description

CLC5644IN -40°C to +85°C 14-pin PDIP
CLC5644IM -40°C to +85°C 14-pin SOIC
CLC5644IMX -40°C to +85°C 14-pin tape and reel

Pac kage Thermal Resistance

Package

θθ

JC

θθ

JA

Plastic (IN) 60°C/W 110°C/W
Surface Mount (IM) 55°C/W 125°C/W

3 http://www.national.com

CLC5644 T ypical Performance

(Av= +2, Rf= 1.65kΩ,RL= 100Ω,Vs= +5V, unless specified)

Non-Inverting Frequency Response

Vo = 0.25V

pp

Gain

Av = +1

Rf = 6.98kΩ

Phase

Av = +5

Rf = 499Ω

Av = +10

Normalized Magnitude (0.5dB/div)

1M

Rf = 249Ω

10M

Av = +2

Rf = 1.65kΩ

100M

Frequency (Hz)

Frequency Response vs. V

Vo = 1V

Vo = 2V

Magnitude (1dB/div)

1M

Vo = 4V

10M

o

Vo = 0.1V

pp

pp

pp

100M

Frequency (Hz)

2nd & 3rd Harmonic Distortion, RL = 100Ω

-50

-60

3rd = 5MHz

2nd = 5MHz

-70

3rd = 1MHz

-80

2nd = 1MHz

Distortion (dBc)

-90

-100
012

Output Amplitude (Vpp)

Large Signal Pulse Response

pp

Phase (deg)

0

-45

-90

-135

-180

-225

Inverting Frequency Response

Vo = 0.25V

pp

Gain

Av = -1

Rf = 1.1kΩ

Phase

Av = -5

Rf = 422Ω

Av = -10

Normalized Magnitude (0.5dB/div)

1M

Rf = 294Ω

10M

Av = -2

Rf = 887Ω

100M

Frequency (Hz)

2nd & 3rd Harmonic Distortion

-50

Vo = 2V

-55

-60

-65

2nd

RL = 100Ω

pp

3rd

RL = 100Ω

-70

-75

-80

Distortion (dBc)

-85

3rd

RL = 1kΩ

2nd

RL = 1kΩ

-90

-95
1M

Frequency (Hz)

2nd & 3rd Harmonic Distortion, RL = 1kΩ

-50

2nd = 5MHz

-60

-70

3rd = 5MHz

-80

-90

-100

Distortion (dBc)

-110

3rd = 1MHz

2nd = 1MHz

-120
012

Output Amplitude (Vpp)

Most Susceptible Channel Pulse Coupling

45
0

-45

-90

-135

-180

Frequency Response vs. R

Vo = 5V

Phase (deg)

Gain

Phase

-225

-270

-315

Magnitude (1dB/div)

-360

-405
1M

2nd & 3rd Harmonic Distortion, RL = 25Ω

-30

-40

-50

-60

Distortion (dBc)

-70

-80

10M

012

Small Signal Pulse Response

Output Voltage (0.1V/div)

Channel to Channel Gain Matching

Inactive Amplitude (10mV/div)

pp

RL = 25Ω

10M

Frequency (Hz)

3rd = 10MHz

2nd = 10MHz

3rd = 1MHz

2nd = 1MHz

Output Amplitude (Vpp)

Time (20ns/div)

Channel 2

L

RL = 100Ω

100M

Channel 1

RL = 1kΩ

Phase (deg)

0

-90

-180

-270

-360

-450

1000M

Phase (deg)

Output Voltage (0.1V/div)

Time (20ns/div)

Equivalent Input Noise

100

10

Noise Voltage (nV/√Hz)

1

1k

Frequency (Hz)

Inverting Current = 10pA/√Hz

Voltage = 4.5nV/√Hz

Non-Inverting

Current = 1.5pA/√Hz

100k

Inactive Channel

Active Amplitude (0.5V/div)

Active Channel

Channel 3

Magnitude (0.5dB/div)

Channel 4

0

-45

-90

-135

-180

-225

Time (20ns/div)

1M

10M

100M

Frequency (Hz)

100

Noise Current (pA/√Hz)

10

1

100M100 10k 1M 10M

Open-Loop Transimpedance Gain, Z(s)

130
120
110
100

|/1Ω]

i

90

/I

o

80
70
60

20 log[|V

50

Gain

Phase

40
30

10k

1M

200
180
160
140
120
100
80
60
40
20
0

100M1k 100k 10M

Frequency (Hz)

PSRR and CMRR

60

50

Phase (degrees)

40

30

PSRR, CMRR (dB)

20

10

100k

Frequency (Hz)

CMRR

PSRR

100M10k 1M 10M

CLC5644

Low-Power, Low-Cost, Quad Operational Amplifier

http://www.national.com 4

Customer Design Applications Support

National Semiconductor is committed to design excellence. For sales, literature and technical support, call the
National Semiconductor Customer Response Group at 1-800-272-9959 or fax [phone].

Life Support Policy

National’s products are not authorized for use as critical components in life support devices or systems without the express written approval of
the president of National Semiconductor Corporation. As used herein:

1. Life support devices or systems are devices or systems which, a) are intended for surgical implant into the body, or b) support or
sustain life, and whose failure to perform, when proper ly used in accordance with instructions for use provided in the labeling, can
be reasonably expected to result in a significant injury to the user.

2. A cr itical component is any component of a life support device or system whose failure to perform can be reasonably expected to
cause the failure of the life support device or system, or to affect its safety or effectiveness.

National Semiconductor National Semiconductor National Semiconductor National Semiconductor
Corporation Europe Hong Kong Ltd. Japan Ltd.

1111 West Bardin Road Fax: [phone] 2501 Miramar Tower Tel:[phone]
Arlington, TX 76017 E-mail:europe.suppor t.nsc.com 1-23 Kimberley Road Fax: [phone]
Tel: [phone] Deutsch Tel: [phone] Tsimshatsui, Kowloon
Fax:[phone] English Tel: [phone] Hong Kong

Francais Tel:[phone] Tel:[phone]
Italiano Tel: [phone] Fax: [phone]

National does not assume any responsibility for use of any circuitry described, no circuit patent licenses are implied and National reserves the right at any time without notice to change said
circuitry and specifications.

N

Current Feedback Amplifiers

Some of the key features of current feedback
technology are:

■

Independence of AC bandwidth and voltage gain

■

Inherently stable at unity gain

■

Adjustable frequency response with R

f

■

High slew rate

■

Fast settling

Current feedback operation can be described using a
simple equation. The voltage gain for a non-inverting
or inverting current feedback amplifier is approximated
by Equation 1.

Equation 1

where:

Avis the closed loop DC voltage gain
Rfis the feedback resistor
Z(jω) is the open loop transimpedance gain

The denominator of Equation 1 is approximately
equal to 1 at low frequencies. Near the -3dB corner
frequency, the interaction between Rfand Z(jω)
dominates the circuit performance. The value of the
feedback resistor has a large affect on the circuits
performance. Increasing Rfhas the following affects:

■

Decreases loop gain

■

Decreases bandwidth

■

Reduces gain peaking

■

Lowers pulse response overshoot

■

Affects frequency response phase linearity

Layout Considerations

A proper printed circuit layout is essential for achieving
high frequency performance. National provides
evaluation boards f or the CLC5644 (CLC730024 - DIP,
CLC730031 - SOIC) and suggests their use as a guide
for high frequency layout and as an aid for device
testing and characterization. General layout and
supply bypassing play major roles in high frequency
performance. Follow the steps below as a basis for
high frequency layout:

■

Include 6.8µF tantalum and 0.1µF ceramic
capacitors on both supplies.

■

Place the 6.8µF capacitors within 0.75 inches of
the power pins.

■

Place the 0.1µF capacitors less than 0.1 inches
from the power pins.

■

Remove the ground plane under and around the
part, especially near the input and output pins to
reduce parasitic capacitance.

■

Minimize all trace lengths to reduce series
inductances.

■

Use flush-mount printed circuit board pins for
prototyping, never use high profile DIP sockets.

Active Filter Application Notes

OA-21 Simplified Component Pre-Distortion for High

Speed Active Filters
OA-26 Designing High-Speed Active Filters
OA-27 Low-Sensitivity, Lowpass Filter Design
OA-28 Low-Sensitivity, Bandpass Filter Design

with Tuning Method
OA-29 Low-Sensitivity, Highpass Filter Design

with Parasitic Compensation

V

V

A

1

R

Zj

o

i

v

f

=

+

()

ω