Datasheet APS1006ET5, APS1006ET5-1.2, APS1006ET5-1.5, APS1006ET5-1.8 Datasheet (APSemi) [ru]

APSemi APS1006

)

1.5 MHz, 600mA Synchronous

Step-Down Converter

GENERAL DESCRIPTION FEATURES

The APS1006 is a 1.5MHz constant frequency,
slope compensated current mode PWM step­down converter. The device integrates a main
switch and a synchronous rectifier for high
efficiency without an external Schottky diode. It
is ideal for powering portable equipment that
runs from a single cell lithium-Ion (Li+) battery.
The APS1006 can supply 600mA of load current
from a 2.5V to 5.5V input voltage. The output
voltage can be regulated as low as 0.6V. The
APS1006 can also run at 100% duty cycle for
low dropout operation, extending battery life in
portable system. Pulse Skipping Mode operation
at light loads provides very low output ripple
voltage for noise sensitive applications.

The APS1006 is offered in a low profile (1mm)
5-pin, SOT package, and is available in an
adjustable version and fixed output voltage of

1.2V, 1.5V and 1.8V.

APPLICATIONS

• Cellular and Smart Phones

• Microprocessors and DSP Core Supplies

• Wireless and DSL Modems

• PDAs

• MP3 Player

• Digital Still and Video Cameras

• Portable Instruments

Typical Application

Figure 1. Basic Application Circuit with

APS1006 adjustable version, Vout = 1.8V

• High Efficiency: Up to 96%

• 1.5MHz Constant Switching Frequency

• 600mA Output Current at V

• Integrated Main switch and synchronous

rectifier. No Schottky Diode Required

• 2.5V to 5.5V Input Voltage Range

• Output Voltage as Low as 0.6V

• 100% Duty Cycle in Dropout

• Low Quiescent Current: 300µA

• Slope Compensated Current Mode Control

for Excellent Line and Load Transient
Response

• Short Circuit Protection

• Thermal Fault Protection

• <1µA Shutdown Current

• Space Saving 5-Pin Thin SOT23 package

IN

=3V

EVALUATION BOARD

Standard Demo Board Dimensions (mm)

EV1006ET5-02 60X x 60Y x 1.6Z

Efficiency vs Output Current

0

10

90

80

70

60

50

EFFICIENCY (%)

40

30

20

10

0.1 1 10 100 1000

VIN = 2.7V

VIN = 3.6V

OUTPUT CURRENT (mA

VIN = 4.2V

VOUT = 1.8V
TA = 25C

Analog Power Semiconductor 1 of 12 Ver.1.3

APSemi APS1006

Absolute Maximum Rating

Input Supply Voltage ...................... -0.3V to +6V

RUN, V

Voltages .................. -0.3V to VIN+0.3V

FB

(Note 1)

Operating Temperature Range... -40°C to +85°C
Junction Temperature

(Note2)

.....................+125°C

SW, Vout Voltages .................. -0.3V to VIN+0.3V Storage Temperature Range .... -65°C to +150°C

Peak SW Sink and Source Current.............. 1.5A Lead Temperature (Soldering, 10s).........+300°C

Package/Order Information

Adjustable Output Version: Fixed Output Versions:

Top View

TOP VIEW

Run

GND

SW

1

MARKING

2

3

TSOT23-5

5

V

OUT

4

V

IN

Part Number Top Mark Temp Range
APS1006ET5-1.5 A2XY
APS1006ET5-1.8 A3XY

-40°C to +85°C

APS1006ET5-1.2 A4XYB

Top View

TOP VIEW

Run

GND

SW

1

MARKING

2

3

5

V

FB

4

V

IN

TSOT23-5

Part Number Top Mark Temp Range

APS1006ET5 A1XY

(note4)

-40°C to +85°C

(Note 3)

Thermal Resistance

Package ӨJA ӨJC

TSOT23-5 110°C/W

Note 1: Absolute Maximum Ratings are those values beyond which the life of a device may be impaired.

T

Note 2:

T

Note 3: Thermal Resistance is specified with approximately 1 square of 1 oz copper.
Note 4: XY = Manufacturing Date Code

is calculated from the ambient temperature T

J

= TA + PD x Ө

J

250°C/W

.

JA

:

and power dissipation PD according to the following formula:

A

Analog Power Semiconductor 2 of 12 Ver.1.3

APSemi APS1006

Electrical Characteristics

(VIN =V

= 3.6V, TA = 25°C, Test Circuit Figure 1, unless otherwise noted.)

RUN

(Note 5)

Parameter Conditions MIN TYP MAX unit

Input Voltage Range 2.5 5.5 V

Input DC Supply Current
Active Mode
Shutdown Mode

Regulated Feedback
Voltage

V

=0.5V

FB

V

=0V, VIN=4.2V

FB

270

0.08

400

1.0

TA = +25°C 0.5880 0.6000 0.6120 V
TA= 0°C  TA  85°C 0.5865 0.6000 0.6135 V

= -40°C  TA  85°C 0.5850 0.6000 0.6150 V

T

A

VFB Input Bias Current VFB = 0.65V ±30 nA

Reference Voltage Line
Regulation

= 2.5V to 5.5V, V

V

IN

= VFB (R2=0) 0.11 0.40 %/V

OUT

APS1006ET5-1.2, -40°C  TA  85°C 1.164 1.200 1.236 V

Regulated Output Voltage

Output Voltage Line
Regulation

APS1006ET5-1.5, -40°C  TA  85°C 1.455 1.500 1.545 V
APS1006ET5-1.8, -40°C  T

V

= 2.5V to 5.5V, I

IN

OUT

 85°C 1.746 1.800 1.854 V

A

=10mA 0.11 0.40 %/V

µA
µA

Output Voltage Load
Regulation

Maximum Output Current V

Oscillator Frequency VFB=0.6V or V

R

R

of P-CH MOSFET I

DS(ON)

of N-CH MOSFET ISW = -300mA 0.20 0.45 

DS(ON)

Peak Inductor Current

SW Leakage V

Output over voltage lockout V

from 10 to 600mA 0.0015 %/mA

I

OUT

= 3.0V 600 mA

IN

=100% 1.2 1.5 1.8 MHz

OUT

= 300mA 0.30 0.50 

SW

V

=3V, VFB=0.5V or V

IN

Duty Cycle <35%

= 0V, VSW= 0V or 5V, VIN = 5V ±0.01 ±1 µA

RUN

OVL

= V

– VFB 60 mV

OVL

OUT

=90%

1.20 A

RUN Threshold -40°C  TA  85°C 0.3 0.45 1.5 V

RUN Leakage Current ±0.1 ±1 µA

Note 5: 100% production test at +25°C. Specifications over the temperature range are guaranteed by design and
characterization.

Analog Power Semiconductor 3 of 12 Ver.1.3

APSemi APS1006

)

)

)

)

)

)

Typical Performance Characteristics

(Test Figure 1 above unless otherwise specified)

Efficiency vs Input Voltage

100

95

90

85

Iload = 500 mA

80

75

Iload = 10 mA

70

EFFICIENCY ( %)

65

60

55

50

2 3 4 56

INPUT VOLTAGE (V

Iload = 100 mA

Efficiency vs Output Current

100

90

VIN = 2.7V

80

70

60

50

40

EFFICIENCY ( %)

30

20

10

0

0.1 1 10 100 1000

OUTPUT CURRENT (mA

Efficiency vs Output Current

100

90

VIN = 2.7V

80

70

VIN = 4.2V

60

50

40

EFFICIENCY ( %)

30

20

10

0

0.1 1 10 100 1000

OUTPUT CURRENT (mA

VIN = 4.2V

VIN = 3.6V

VOUT = 1.5V
TA = 25C

VIN = 3.6V

VOUT = 2.5V
TA = 25C

Efficiency vs Output Current

100

90

VIN = 2.7V

80

70

60

50

40

EFFICIENCY ( %)

30

20

10

0

0.1 1 10 100 1000

OUTPUT CURRENT (mA

Efficiency vs Output Current

100

90

80

70

60

50

EFFICIENCY ( %)

40

30

20

10

0.1 1 10 100 1000

VIN = 2.7V

VIN = 3.6V

OUTPUT CURRENT (mA

Efficiency vs Load Current

100

VIN = 3.6V

90

VOUT = 1.8V
TA = 25C

80

70

60

50

EFFICIENCY (%)

40

30

20

10

0.1 1 10 100 1000

VIN = 3.6V

VIN = 4.2V

VOUT = 1.2V
TA = 25C

VIN = 4.2V

VOUT = 1.8V
TA = 25C

L = 2.2 uH

L = 1.4 uH

L = 10 uH

L = 4.7 uH

LOAD CURRENT (mA

Analog Power Semiconductor 4 of 12 Ver.1.3

APSemi APS1006

)

)

)

)

)

Efficiency vs Load Current

100

90

80

70

60

50

40

EFFICIENCY (%)

30

20

10

VIN = 3.6V
VOUT 2.5V
TA = 25C

L = 10 uH

L = 4.7 uH

L = 2.2 uH

L = 1.4 uH

0

0.1 1 10 100 1000

LOAD CURRENT (mA

Frequency vs Input Voltage

1.46

FREQUENCY (MHz)

1.45

1.44

1.43

1.42

1.41

1.39

1.38

1.37

1.36

VOUT = 1.8V
ILOAD = 150mA
L = 2.2uH

1.4

2.7 3.15 3.6 4.05 4.5 4.95 5.4

INPUT VOLT AGE (V

Reference Voltage vs Temperature

0.6080

0.6072

0.6064

0.6056

0.6048

0.6040

0.6032

REFERENCE VOLTAGE (V)

0.6024

0.6016

0.6008

VIN = 3.6V

-50 -30 -10 10 30 50 70 90

TEMPERATURE (C

Outpu Voltage vs Load Current

1.84

1.82

1.8

1.78

1.76

1.74

1.72

OUTP UT VOLTAGE (V)

1.7

1.68

1.66

1.64

VOUT = 1.8V
VIN = 3.6V
L = 2.2uH

0 200 400 600 800 1000 1200

R

DS(ON)

0.5

0.4

0.3

(OHM)

DS(ON)

0.2

R

0.1

0.0
0 1 2 3 4 5 6 7

SYNCHRONOUS SW ITCH

R

0.38

VIN = 3.6V

-45 -30 -15 0 15 30 45 60 75 90

(OHM)

R

DS(ON)

0.36

0.34

0.32

0.30

0.28

0.26

0.24

0.22

0.20

0.18

LOAD CURRENT (mA

vs Input Voltage

MAIN SW ITH

INPUT VOLTAGE (V)

vs Tem perature

DS(ON)

Temperature (C

N_R

P_R

DS(ON)

DS(ON)

Analog Power Semiconductor 5 of 12 Ver.1.3

APSemi APS1006

)

)

)

Input Voltage vs Input Current

0.32

VOUT = 1.8V
ILOAD = 0
L = 2.2uH

2.7 3 3.3 3.6 3.9 4.2 4.5 4.8 5.1 5.4 5.7

INPUT VOLT AGE (V

INPUT CURRENT (mA)

0.32

0.31

0.31

0.30

0.29

0.29

0.28

0.28

0.27

0.26

Supply Current vs Temperature

320

300

Frequency vs Tem perature

1.60

VIN = 3.6V

-50 -25 0 25 50 75 100

OSC Frequency (MHz)

1.55

1.50

1.45

1.40

1.35

1.30

1.25

1.20

1.15

1.10

Load Transient Response

PWM Mode Only

Temperature (C

280

260

240

Supply Current (uA)

220

200

-50 -30 -10 10 30 50 70 90

Temperature (C

Load Transient Response

Pulse Skipping Mode to PWM Mode

Pulse Skipping

Analog Power Semiconductor 6 of 12 Ver.1.3

APSemi APS1006

Pin Description

PIN NAME FUNCTION

Regulator Enable control input. Drive RUN above 1.5V to turn on the part.

1 RUN

2 GND Ground

3 SW

4 IN

5 VFB/VOUT

Functional Block Diagram

Drive RUN below 0.3V to turn it off. In shutdown, all functions are disabled
drawing <1µA supply current. Do not leave RUN floating.

Power Switch Output. It is the Switch note connection to Inductor. This pin
connects to the drains of the internal P-CH and N-CH MOSFET switches.
Supply Input Pin. Must be closely decoupled to GND, Pin 2, with a 2.2µF or
greater ceramic capacitor.

VFB(APS1006ET5): Feedback Input Pin. Connect FB to the center point of the
external resistor divider. The feedback threshold voltage is 0.6V.
VOUT(APS1006ET5-1.2/APS1006ET5-1.5/APS1006ET5-1.8). Output Voltage
Feedback Pin. An internal resistive divider divides the output voltage down for
comparison to the internal reference voltage.

Figure 2. APS1006 Block Diagram

Analog Power Semiconductor 7 of 12 Ver.1.3

APSemi APS1006

Operation

APS1006 is a monolithic switching mode Step­Down DC-DC converter. It utilizes internal
MOSFETs to achieve high efficiency and can
generate very low output voltage by using internal
reference at 0.6V. It operates at a fixed switching
frequency, and uses the slope compensated
current mode architecture. This Step-Down DC­DC Converter supplies 600mA output current at
VIN = 3V with input voltage range from 2.5V to

5.5V.

Current Mode PWM Control

Slope compensated current mode PWM control
provides stable switching and cycle-by-cycle
current limit for excellent load and line responses
and protection of the internal main switch (P-Ch
MOSFET) and synchronous rectifier (N-CH
MOSFET). During normal operation, the internal
P-Ch MOSFET is turned on for a certain time to
ramp the inductor current at each rising edge of
the internal oscillator, and switched off when the
peak inductor current is above the error voltage.
The current comparator, I
inductor current. When the main switch is off, the
synchronous rectifier will be turned on
immediately and stay on until either the inductor
current starts to reverse, as indicated by the
current reversal comparator, I
beginning of the next clock cycle. The OVDET
comparator controls output transient overshoots
by turning the main switch off and keeping it off
until the fault is no longer present.

Pulse Skipping Mode Operation

At very light loads, the APS1006 automatically
enters Pulse Skipping Mode. In the Pulse
Skipping Mode, the inductor current may reach
zero or reverse on each pulse. The PWM control
loop will automatically skip pulses to maintain
output regulation. The bottom MOSFET is turned
off by the current reversal comparator, I
the switch voltage will ring. This is discontinuous
mode operation, and is normal behavior for the
switching regulator.

limits the peak

COMP,

, or the

ZERO

ZERO,

and

Dropout Operation

When the input voltage decreases toward the
value of the output voltage, the APS1006 allows
the main switch to remain on for more than one
switching cycle and increases the duty cycle
until it reaches 100%. The output voltage then is
the input voltage minus the voltage drop across
the main switch and the inductor. At low input
supply voltage, the R
MOSFET increases, and the efficiency of the
converter decreases. Caution must be exercised
to ensure the heat dissipated not to exceed the
maximum junction temperature of the IC.

Note 5: The duty cycle D of a step-down converter is
defined as:

fTD

OSCON

Where T
oscillator frequency (1.5Mhz).

is the main switch on time and f

ON

of the P-Channel

DS(ON)

V

OUT

V

IN

%100%100 ×≈××=

OSC

(Note 5)

is the

Maximum Load Current

The APS1006 will operate with input supply
voltage as low as 2.5V, however, the maximum
load current decreases at lower input due to large
IR drop on the main switch and synchronous
rectifier. The slope compensation signal reduces
the peak inductor current as a function of the duty
cycle to prevent sub-harmonic oscillations at duty
cycles greater than 50%. Conversely the current
limit increases as the duty cycle decreases.

Layout Guidance

When laying out the PC board, the following
suggestions should be taken to ensure proper
operation of the APS1006. These items are also
illustrated graphically in Figure 3.

1. The power traces, including the GND trace,
the SW trace and the VIN trace should be
kept short, direct and wide to allow large
current flow. Put enough multiply-layer pads
when they need to change the trace layer.

2. Connect the input capacitor C1 to the VIN pin
as closely as possible to get good power filter
effect.

Analog Power Semiconductor 8 of 12 Ver.1.3

APSemi APS1006

3. Keep the switching node, SW, away from the
sensitive FB node.

4. Do not trace signal line under inductor.

(a) Top Layer (b) Internal GND Plane

(c) Bottom Layer (d) Middle Layer

Figure 3. APS1006 Four Layers Layout Example, with the 2

nd

and 3rd Internal Plane GND

Analog Power Semiconductor 9 of 12 Ver.1.3

APSemi APS1006

APPLICATIONS
INFORMATION

Figure 4 below shows the basic application
circuit with APS1006 fixed output versions.

Figure 4. Basic Application Circuit with fixed
output versions

Setting the Output Voltage

Figure 1 above shows the basic application
circuit with APS1006 adjustable output version.
The external resistor sets the output voltage
according to the following equation:

2

R

⎛

16.0

VV

OUT

Table 1 Resistor select for output voltage setting

R1(R3) R2(R4)

V

OUT

1.2V 316k 316k

1.5V 316k 470k

1.8V 316k 634k

2.5V 316k 1000k

⎜
⎝

Inductor Selection

For most designs, the APS1006 operates with
inductors of 1µH to 4.7µH. Low inductance
values are physically smaller but require faster
switching, which results in some efficiency loss.
The inductor value can be derived from the
following equation:

()

L

=

−×

×Δ×

Where is inductor Ripple Current. Large
value inductors lower ripple current and small

value inductors result in high ripple currents.
Choose inductor ripple current approximately
35% of the maximum load current 600mA, or

IΔ

IΔ

=210mA.

L

L

⎞

+×=

⎟

1

R

⎠

VVV

OUTINOUT

fIV

OSCLIN

For output voltages above 2.0V, when light-load
efficiency is important, the minimum
recommended inductor is 2.2µH. For optimum
voltage-positioning load transients, choose an
inductor with DC series resistance in the 50m
to 150m range. For higher efficiency at heavy
loads (above 200mA), or minimal load regulation
(but some transient overshoot), the resistance
should be kept below 100m. The DC current
rating of the inductor should be at least equal to
the maximum load current plus half the ripple
current to prevent core saturation
(600mA+105mA). Table 2 lists some typical
surface mount inductors that meet target
applications for the APS1006.

Table 2. Typical Surface Mount Inductors

Part #

Sumida 2.2 71.2 1.75
CR43 3.3 86.2 1.44

Sumida 2.2 75 1.32
CDRH4D18 3.3 110 1.04

Toko
D312C

L
(µH)

1.4 56.2 2.52

4.7 108.7 1.15

1.5

4.7 162 0.84

1.5 120 1.29

2.2 140 1.14

3.3 180 0.98

4.7 240 0.79

Max
DCR
(m)

Rated
D.C.
Current
(A)

Size
WxLxH
(mm)

4.5x4.0x3.5

4.7x4.7x2.0

3.6x3.6x1.2

Input Capacitor Selection

The input capacitor reduces the surge current
drawn from the input and switching noise from
the device. The input capacitor impedance at
the switching frequency shall be less than input
source impedance to prevent high frequency
switching current passing to the input. A low
ESR input capacitor sized for maximum RMS
current must be used. Ceramic capacitors with
X5R or X7R dielectrics are highly recommended
because of their low ESR and small temperature
coefficients. A 4.7µF ceramic capacitor for most
applications is sufficient.

Output Capacitor Selection

The output capacitor is required to keep the
output voltage ripple small and to ensure
regulation loop stability. The output capacitor
must have low impedance at the switching
frequency. Ceramic capacitors with X5R or X7R
dielectrics are recommended due to their low

Analog Power Semiconductor 10 of 12 Ver.1.3

APSemi APS1006

ESR and high ripple current. The output ripple

is determined by:

V

OUT

−×

≤Δ

V

OUT

VVV

××

⎛

)(

OUTINOUT

⎜

+×

ESR

⎜

LfV

⎝

oscOSCIN

⎞

1

⎟
⎟

××

38

Cf

⎠

Package Description

Note: Package outline exclusive of mold flash and metal burr.

Analog Power Semiconductor 11 of 12 Ver.1.3

APSemi APS1006

RELATED PARTS

Part Number Description Comments

APS1006

APS1016

APS1026

APS1126

1.5 MHz, 600mA Synchronous Step-Down
Converter

1.5 MHz, 600mA Synchronous Step-Down
Converter with Low Quiescent Current

Dual Channel 1.5 MHz, 600mA
Synchronous Step-Down DC-DC Converter
with Low Quiescent Current

Dual Channel 1.5 MHz, 600mA
Synchronous Step-Down DC-DC Converter

PWM and Pulse Skipping Mode
operation.

PWM and Power Saving Mode
operation.

Dual Channel version of the
APS1016 with selectable Pulse
Skipping Mode and Power Saving
Mode operation.

Dual Channel version of the
APS1006 with Pulse Skipping Mode
operation.

IMPORTANT NOTICE

Analog Power Semiconductor (Shanghai) Co., Ltd. reserves the right to make changes without further
notice to any products or specifications herein. Analog Power Semiconductor (Shanghai) Co., Ltd. does
not assume any responsibility for use of any its products for any particular purpose, nor does Analog
Power Semiconductor (Shanghai) Co., Ltd assume any liability arising out of the application or use of any
its products or circuits. Analog Power Semiconductor (Shanghai) Co., Ltd does not convey any license
under its patent rights or other rights nor the rights of others.

Analog Power Semiconductor
IPCore Technologies (Shanghai) Co., Ltd.
11 Floor, Block B, Hi-Tech Building, 900 Yishan Road,
Shanghai, 200233, P.R. China
Tel: [phone]
Fax: [phone]

http://www.apsemi.com; http://www.ipcoreinc.com

Analog Power Semiconductor 12 of 12 Ver.1.3