Datasheet ADP3603 Datasheet (Analog Devices)

REV. 0

Information furnished by Analog Devices is believed to be accurate and
reliable. However, no responsibility is assumed by Analog Devices for its
use, nor for any infringements of patents or other rights of third parties
which may result from its use. No license is granted by implication or
otherwise under any patent or patent rights of Analog Devices.

a

Switched Capacitor Voltage Converter

with Regulated Output

ADP3603*

© Analog Devices, Inc., 1996

One Technology Way, P.O. Box 9106, Norwood, MA 02062-9106, U.S.A.
Tel: [phone] Fax: [phone]

FUNCTIONAL BLOCK DIAGRAM

8

SPD

S1

SND

S2

S

N

D

B

S3

S

ND

7

3

V

IN

CP–

CP+

1

S4

2

V

OUT

GND

OSC

CLOCK

GEN

4

SD

FEEDBACK

CONTROL

LOOP

5

V

SENSE

GENERAL DESCRIPTION

The ADP3603 switched capacitor voltage converter provides
a regulated output voltage with minimum voltage loss and re­quires a minimum number of external components. In addition,
the ADP3603 does not require the use of an inductor. The
ADP3603 provides up to 50 mA of output current with ± 3%
output accuracy.

The internal oscillator runs at 240 kHz nominal frequency
which produces an output switching frequency of 120 kHz,
allowing the use of small charge pump and filter capacitors.
The ADP3603 is primarily designed for use as a high fre­quency negative voltage regulator/inverter. The output voltages
of the ADP3603 can range from –1.2 V to –4.0 V, nominally
–3.0 V. For other output voltages, contact the factory.

The ADP3603 dissipates less than 150 mW of power and fea­tures fast shutdown mode capability (<5 ms) that also drops the
quiescent current to 1.4 mA (typ). For a higher output current
(120 mA) version, see the ADP3604.

*Patent pending.

FEATURES
Fully Regulated Output
High Output Current: 50 mA

120 mA Version (ADP3604) Is Also Available
Outstanding Precision: 63% Output Accuracy
Input Voltage Range: +4.5 V to +6.0 V
Output Voltage: –3.0 V (Regulated)
High Switching Frequency: 120 kHz (240 kHz Internal

Oscillator)
Shutdown Capability
Small Outline 8-Pin SOIC Package

APPLICATIONS
Voltage Inverters
Negative Voltage Regulators
Computer Peripherals and Add-On Cards
Portable Instruments
Battery Powered Devices
Pagers and Radio Control Receivers
Disk Drives
Mobile Phones

PIN CONFIGURATION

8-Pin SOIC

(SO-8)

1
2
3
4

8
7
6
5

TOP VIEW

(Not to Scale)

NC = NO CONNECT

ADP3603

CP+

V

SENSE

NC

V

OUT

V

IN

GND

CP–

SHUTDOWN

ADP3603

8

7

3

C2

4.7µF

†

1

4

SHUTDOWN

0

OFF

ON

C1

4.7µF

†

VIN +4.5 – +6V V

OUT

–3.0V

C3

4.7µF

†

2

5

V

SENSE

NOTE
C2: SPRAGUE, 293D105X0010B2W
C1, C3: TOKIN, 1E105ZY5UC205F

†

FOR BEST PERFORMANCE 10µF IS RECOMMENDED

Figure 1. Typical Application Circuit

PIN DESCRIPTION

Pin Function

1C

P

+, Pump Capacitor Positive Input.
2 Ground.
3C

P

–, Pump Capacitor Negative Input.
4 Shutdown, Logic Level Shutdown Pin. Application of a

logic low to this pin will place the regulator in normal
operation. The device will be put into shutdown mode
with the shutdown pin pulled to V

IN

. In Shutdown
mode the charge pump is turned off. Connect to ground
for normal operation.

5V

SENSE

, Output Voltage Sense Line. This is used to im­prove load regulation performance by eliminating IR
drop on the output traces. See application section for
more detail. For normal operation, connect Pin 5 to
V

OUT

(Pin 7).
6 NC, No Internal Electrical Connection.
7V

OUT,

Output Pin. Regulated negative output voltage.
Connect a low ESR capacitor between this pin and de­vice GND.

8V

IN,

Positive Supply Input when 4.5 V ≤ V

IN

≤ 6 V. Con­nect a low-ESR bypass capacitor between this pin and
the device ground pin.

Parameter Symbol Condition Min Typ Max Units

OPERATING SUPPLY RANGE V

S

4.5 5 6 V

SUPPLY CURRENT I

S

2.4 3 mA

–40°C < T

A

< +85°C 2.5 3.5 mA

Shutdown Mode 1.4 2 mA

–40°C < TA < +85°C 1.5 2.5 mA

OUTPUT

Output Voltage V

O

IO = 25 mA –3.1 –3 –2.91 V

V

O

IO = 10 mA to 50 mA, 4.5 V < VIN < 6 V –3.1 –3 –2.9 V

V

O

IO = 10 mA to 50 mA, 4.5 V < VIN < 6 V,
0°C < T

A

< +70°C –3.12 –3 –2.88 V

V

O

IO = 10 mA to 50 mA, 4.5 V < VIN < 6 V,
–40°C < T

A

< +85°C –3.15 –3 –2.85 V

Load Regulation ∆V

O

/ I

O

IO = 10 mA–60 mA 0.9 mV/mA
I

O

= 10 mA–120 mA 1.5 mV/mA

Output Resistance

2

R

O

8 Ω

Output Ripple Voltage

3

V

RIPPLE

C1–C3 = 10 µF, I

LOAD

= 80 mA 25 mV

C1–C3 = 10 µF, I

LOAD

= 120 mA 55 mV

SWITCHING FREQUENCY F

S

100 120 130 kHz

–40°C < TA < +85°C 96 120 140 kHz

SHUTDOWN

Logic Input High V

IH

2.4 V

Input Current I

IH

1 µA

Logic Input Low V

IL

0.4 V

Input Current I

IL

1 µA

Turn-On-Time t

ON

Figure 1, IL = 120 mA 5 ms

Turn-Off-Time t

OFF

Figure 1, IL = 120 mA 5 ms

NOTES

1

Capacitors C1 and C2 used in the test circuit are 10 µF with 0.1 Ω ESR. Capacitors with higher ESR may reduce output voltage and efficiency.

2

Open-loop output resistance.

3

See Figure 1 conditions.

All limits at temperature extremes are guaranteed via correlation using standard Statistical Quality Control (SQC) methods.
Specifications subject to change without notice

.

REV. 0

–2–

ADP3603–SPECIFICA TIONS

WARNING!

ESD SENSITIVE DEVICE

CAUTION

ESD (electrostatic discharge) sensitive device. Electrostatic charges as high as 4000 V readily
accumulate on the human body and test equipment and can discharge without detection.
Although the ADP3603 features proprietary ESD protection circuitry, permanent damage may
occur on devices subjected to high energy electrostatic discharges. Therefore, proper ESD
precautions are recommended to avoid performance degradation or loss of functionality.

(VIN = 5.0 V @ TA = +258C, CP = C

OUT

= 10 mF unless otherwise noted)

ABSOLUTE MAXIMUM RATINGS

1

(TA = +25°C unless otherwise noted)

Input Voltage (V+ to GND, GND to OUT) . . . . . . . . . +7.5 V

Output Short Circuit Protection . . . . . . . . . . . . . . . . . . . .1 sec

Power Dissipation, SO-8 . . . . . . . . . . . . . . . . . . . . . . .660 mW

θ

JA

2

. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 150°C/W

θ

JC

. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 41°C/W

Operating Temperature Range . . . . . . . . . . . . .–40°C to +85°C

Storage Temperature Range . . . . . . . . . . . . .–65°C to +150°C

Lead Temperature Range (Soldering 10 sec) . . . . . . . . +300°C

Vapor Phase (60 sec) . . . . . . . . . . . . . . . . . . . . . . . . +215°C

Infrared (15 sec) . . . . . . . . . . . . . . . . . . . . . . . . . . . . +220°C

NOTES

1

This is a stress rating only and functional operation of the device at these or any
other conditions above those indicated in the operation section of this specification
is not implied. Exposure to absolute maximum rating conditions for extended
periods may affect device reliability.

2

θJA is specified for worst case conditions with device soldered on a circuit board.

ORDERING GUIDE

Model Temperature Range Package Option*

ADP3603AR –40°C to +85°C SO-8

*SO = Small Outline Package.

ADP3603

REV. 0

–3–

SUPPLY VOLTAGE – Volts

OSCILLATOR FREQUENCY – kHz

130

4.0 4.5 8.0

5.0 5.5 6.5 7.0 7.56.0

120

110

Figure 2. Oscillator Frequency vs.
Supply Voltage

TEMPERATURE – 8C

OSCILLATOR FREQUENCY – kHz

126

112

–40 85

07025

124

122

120

118

116

114

Figure 5. Oscillator Frequency vs.
Temperature

SUPPLY VOLTAGE – Volts

SUPPLY CURRENT – mA

3.5

0

4.0 4.5 8.0

5.0 5.5 6.5 7.0 7.56.0

3.0

2.5

2.0

1.5

1.0

0.5

NORMAL MODE

SHUTDOWN MODE

Figure 8. Supply Current vs. Supply
Voltage

TEMPERATURE – 8C

SUPPLY CURRENT – mA

3.0

1.5

0
–40 85

07025

2.5

2.0

1.0

0.5

NORMAL MODE @ VIN = 5V

SHUTDOWN MODE @ VIN = 5V

Figure 3. Supply Current vs.
Temperature

LOAD CURRENT – mA

INPUT CURRENT – mA

80

40

0

10 20 70

30 50 6040

70

60

50

30

20

10

VIN = 5V

Figure 6. Average Input Current vs.
Load Current

100

90

10
0%

5ms

1V

0V

–3V

Figure 9. Start-Up Under Full Load

TEMPERATURE – 8C

OUTPUT VOLTAGE – Volts

–2.95

–3.02

–40 85

07025

–2.96

–2.97

–2.98

–2.99

–3.00

–3.01

IL = 75mA

IL = 50mA

IL = 25mA

IL = 10mA

Figure 4. Output Voltage vs.
Temperature

LOAD CURRENT – mA

EFFICIENCY – %

70

0

10 20 70

30 40 50 60

60

50

40

30

20

10

VIN = 4.5V

VIN = 5V
VIN = 6V

Figure 7. Efficiency vs. Load
Current and Input Voltage

100

90

10
0%

5ms

1V

0V

–3V

Figure 10. Enable/Disable Time
Under Full Load

ADP3603

REV. 0

–4–

and S2 are turned OFF as well as S3 and S4 to prevent any
overlap. S3 and S4

are turned ON during the second phase (see
Figure 14) and charge stored in the pump capacitor is trans­ferred to the output capacitor.

V

IN

S2

C

P

S1

V

OUT

S3

S4

C

OUT

Figure 14. ADP3603 Switch Configuration Charging the
Output Capacitor

During the second phase, the positive terminal of the pump
capacitor is connected to ground and the negative terminal is
connected to the output, resulting in a voltage inversion at the
output terminal. Output regulation is done by adjusting the ON
resistance of the S3 through the feedback control loop.

The ADP3603 alternately charges C

P

to the input voltage when

C

P

is switched in parallel with the input supply, and then trans-

fers charge to C

OUT

when CP is switched in parallel with C

OUT

.

Switching occurs at 120 kHz rate. During the time that C

P

is
charging, the peak current is approximately 2 times the output
current. During the time that C

P

is delivering charge to C

OUT

,
the supply current drops down to about 2 mA. An input supply
bypass capacitor will supply part of the peak input current
drawn by the ADP3603, and average out the current drawn
from the supply. A minimum input supply bypass capacitor of
1 µF, preferably a low ESR capacitor such as tantalum or multi-
layer ceramic chip capacitor, is recommended. A large capacitor
may be desirable in some cases, for example when the input
supply is connected to the ADP3603 through long leads, or
when the pulse current drawn by the device might effect other
circuitry through supply coupling.

The output capacitor, C

OUT

, is alternately charged to the C

P

voltage when CP is switched in parallel with C

OUT

. The ESR of

the C

OUT

introduces steps in the V

OUT

waveform whenever the

charge pump charges C

OUT

. This tends to increase V

OUT

ripple.

Ceramic or tantalum capacitors are recommended for C

OUT

if
minimum ripple is desired. The ADP3603 can operate with a
range of capacitors from 1 µF to 100 µF and larger without any
stability problems. However, all tested parameters are obtained
using 10 µF multilayer ceramic capacitors.

In most applications, IR drops due to printed circuit board
traces do not present a problem. In this case, V

SENSE

is tied to

the output at a convenient pcb location not far from the V

OUT

.
However, if a reduction in IR drops or improvement in load
regulation is desired, the sense line can be used to monitor the
output voltage at the load. To avoid excessive noise pickup, the
V

SENSE

line should be as short as possible and away from any

noisy line.

Capacitor Selection

While the exact values of the CIN and C

OUT

are not critical,
good quality, low ESR capacitors such as solid tantalum and
multilayer ceramic capacitors are recommended to minimize
voltage losses at high currents. For a given load current, factors
affecting the output voltage performance are in Figure 15:

• Pump (C2) and the output (C3) capacitance

• ESR of the C2 and C3.

APPLICATION INFORMATION

The ADP3603 uses a charge pump to generate a negative out­put voltage from a positive input supply. To understand the
operation of the ADP3603, a review of a basic switch capacitor
building block is helpful.

f

R

L

V1 V2

C1

C2

AB

Figure 11. Basic Switch Capacitor Circuit

In Figure 11, when the switch is in the A position, capacitor
C1 will be charged to voltage V1. The total charge on C1 will
be q1 = C1V1.

The switch then moves to the B position, discharging C1 to
voltage V2. After this discharge time, the charge on C1 is q2 =
C1V2. The amount of charge transferred from the source, V1,
to the output, V2, is:

∆q = q1 – q2 = C1

(V1 – V2)

If the switch is cycled f times per second, the charge transfer
per unit time (i.e., current) is:

I = f ∆q = f C1 (V1 – V2)

To obtain an equivalent resistance for the switched-capacitor
network we can rewrite this equation in terms of voltage and
impedance equivalence:

I = (V1 – V2)/(1/fC1) = (V1 – V2)/R

EQUIV

where R

EQUIV

is defined as:

R

EQUIV

= 1/f C1

Figure 11 equivalent circuit can now be drawn as shown in
Figure 12.

R

L

V1 V2

C2

R

EQUIV

R

EQUIV

=

1

fC1

Figure 12. Basic Switch Capacitor Equivalent Circuit

THEORY OF OPERATION

A switched capacitor principle is used in the ADP3603 to
generate a negative voltage from a positive input voltage. An
on-board oscillator generates two phase clocks to control a
switching network which transfers charge between the storage
capacitors. The basic principle behind the voltage inversion
scheme is illustrated in Figures 13 and 14.

V

IN

S2

C

P

S1

V

OUT

S3

S4

C

OUT

Figure 13. ADP3603 Switch Configuration Charging the
Pump Capacitor

During phase one, S1 and S2 are ON charging the pump
capacitor to the input voltage. Before the next phase begins, S1

ADP3603

REV. 0

–5–

TEMPERATURE – 8C

ESR – Ω

10

1.0

0.01
–50 100050

0.1

ALUMINUM

CERAMIC

ORGANIC SEMIC

TANTALUM

ALUMINUM

CERAMIC

ORGANIC SEMIC

TANTALUM

Figure 16. ESR vs. Temperature

Table I. Alternative Capacitor Technologies

High

Type Life Frequency Temp Size Cost

Aluminum Fair Fair Fair Small Low
Electrolytic
Capacitor

Multilayer Long Good Poor Fair High
Ceramic
Capacitor

Solid Above Avg Avg Avg Avg
Tantalum Avg
Capacitor

OS-CON Above Good Good Good Avg
Capacitor Avg

Table II shows a partial list of manufacturers providing low­ESR capacitors.

Table II. Recommended Capacitor Manufacturers

Manufacturer Capacitor Capacitor Type

Sprague 672D, 673D, Aluminum Electrolytic

674D, 678D
Sprague 675D, 173D, 199D Tantalum
Nichicon PF & PL Aluminum Electrolytic
Mallory TDC & TDL Tantalum
TOKIN MLCC Multilayer Ceramic
muRata GRM Multilayer Ceramic

EXTERNAL OUTPUT FILTERING

In applications requiring very low power supply ripple and
noise, the circuit in Figure 17 provides low noise and ripple of
less than 2% of the output voltage over the full load current and
temperature.

Since output current is supplied solely by the output capacitor
C3 during one-half of the charge-pump cycle, peak-to-peak out­put ripple voltage is calculated by using the following formula:

V

RIPPLE

=

I

OUT

2 F

PUMP

()

C2

()

+I

OUT

ESR

C2

()

In Figure 15, output ripple voltage vs. capacitance and various
ESR are shown.

CAPACITANCE – µF

OUTPUT RIPPLE – mV

60

0

09010 20 30 40 50 60 70 80

50

40

30

20

10

ESR

C

50mA

V

OUT

ADP3603

150mΩ

100mΩ

50mΩ

Figure 15. Output Ripple Voltage (mV) vs. Capacitance
and ESR

Note that as the capacitor value increases beyond the point
where the dominant contribution to the output ripple is due to
the ESR, no significant reduction in V

OUT

ripple is achieved by

added capacitance.
A low ESR capacitor has much greater impact on performance

for C2 than C3 since current through C2 is twice the C3 cur­rent. There is a voltage drop across C

P

’s ESR during the charge
as well as during discharges. Therefore, the voltage drop due to
C2 is about 4 times C2’s ESR times the load current. The volt­age drop generated by C2’s ESR combined with the voltage
drop due to the output source resistance, determines the maxi­mum available V

OUT

, while C3’s ESR affects the output voltage

ripple.
When selecting the capacitors, keep in mind that not all manu-

facturers guarantee capacitor ESR in the range required by the
circuit. In general, the capacitor’s ESR is inversely proportional
to its physical size, so larger capacitance values and higher volt­age ratings tend to reduce ESR.

ESR is also a function of the operating frequency. When select­ing a capacitor, make sure its value is rated at the circuit’s
operating frequency. The other factor affecting the capacitor’s
performance is temperature. If the circuit has to operate at
temperatures significantly different than 25°C, the capacitance
and ESR values must be carefully selected to adequately com­pensate for the change. Various capacitor technologies offer
improved performance over temperature, for example, certain
tantalum capacitors provide good low-temperature ESR but at a
higher cost.

Figure 16 demonstrates the effect temperature has on various
capacitors. ADP3603’s high internal oscillator frequency per­mits the usage of smaller capacitance for both the pump and the
output capacitors.

ADP3603

REV. 0

–6–

Table IV. Recommended Components for Circuit in Figure 18

Component Manufacturer/Type

C3 Sprague, 293D475X0035D2W
C1, C2, C4, C5 TOKIN, 1E475ZY5UC205F
L1 Coiltronics, CTX32CT-1R0
L2 Coiltronics, CTX32CT-100

SHUTDOWN MODE

ADP3603’s output can be turned off by utilizing the shutdown
pin, Pin 4. Pulling the shutdown pin high to a TTL/CMOS
logic compatible level will stop the internal oscillator and turn
OFF the output pass transistor. A digital low level will turn the
output ON. If the shutdown feature of the device is not used,
Pin 4 should be tied to the ground pin of the device.

MAXIMUM OUTPUT VOLTAGE

Maximum unregulated output voltage can be obtained by con­necting the sense pin to ground instead of the V

OUT

pin as

shown in Figure 19.
Under this condition, the magnitude of the unregulated output

voltage depends on the load current. V

OUT

is inversely propor-

tional to the load current as shown on the graph in Figure 19.

LOAD CURRENT – mA

–5.0

–4.0

10 40

V

OUT

– Volts

20 25 30

–3.0

ADP3603

8 7

3

1

4

VIN = 5.0V

2

5

Figure 19. Maximum Unregulated Output Voltage

Under light loads, 30 mA < I

LOAD

, a regulated output voltage

between –3.0 V to –V

IN

V is possible by inserting a resistor be-

tween the sense pin and the V

OUT

pin as shown in Figure 20.

The output voltage is approximated using the following formula:

V

OUT

= –(3 +R/5)

where V

OUT

is in volts and R is in kΩs.

LOAD CURRENT – mA

–5.0

–4.0

10 40

V

OUT

– Volts

20 25 30

–3.0

ADP3603

8 7

3

1

4

VIN = 5.0V

2

5

V

OUT

R

R = 10kV

R = 5kV

Figure 20. Maximum Regulated Output Voltage

The output current is supplied solely by the output capacitor C3
during one-half of the charge-pump cycle. This introduces a
peak-to-peak ripple of:

V

RIPPLE

=

I

L

2×120 kHz ×C3

+ IL× ESR

C3

For a nominal F pump of 120 kHz (one-half the nominal
240 kHz oscillator frequency) and C3 = 10 µF with an ESR of

0.15 Ω, ripple voltage is approximately 30 mV with a 50 mA
load current.

Multilayer Ceramic Capacitors (MLCC) offer great perfor­mance and small size. Using multiple capacitors connected in
parallel yields lower ESR and a potential saving in cost. Lighter
loads require proportionally smaller capacitors. To reduce high
frequency noise, bypass the output with a 0.1 µF ceramic
capacitor.

ADP3603

8

7

3

C2

4.7µF

1

4

VIN +4.5 – +6V

V

OUT

–3.0V

C3

4.7µF

2

5

SENSE
INPUT

L1

10µH

C4

4.7µF

C1

4.7µF

Figure 17. Circuit with Improved Output Ripple & Noise
Voltage

Table III. Re commended Components for Circuit in Figure 17

Component Manufacturer/Type

C2 Sprague, 293D475X0035D2W
C1, C3, C4 TOKIN, 1E475ZY5U-C205-F
L1 Coiltronics, CTX32CT

EXTERNAL INPUT FILTERING

If the ADP3603 is supplied from a high-impedance source,
connect an additional bypass capacitor from V+ to ground.
Low-ESR capacitors of up to 100 µF give best results. Place
external capacitors close to the supply pins of the device with
the ground connection made as close to the device ground as
possible. The same ground point should be used for the output
bypass capacitor.

Smaller bypass capacitors can be used in conjunction with a
π-LC filter.

ADP3603

8

7

3

C3

4.7µF

1

4

VIN +4.5 – +6V

V

OUT

–3.0V

C4

4.7µF

2

5

SENSE
INPUT

L2

10µH

C5

4.7µF

C2

4.7µF

L1

1µH

C1

4.7µF

Figure 18. Circuit with Reduced Input and Output Ripple
& Noise Voltage

ADP3603

REV. 0

–7–

POWER DISSIPATION

The power dissipation of the ADP3603 circuit must be limited
such that the junction temperature of the device does not ex­ceed the maximum junction temperature rating.

Power is dissipated in two components, power loss due to volt­age drops in the switches, and power loss due to MOSFET
drive current losses. Total power dissipation is calculated:

P ≈ (V

IN

– |V

OUT

|)(I

OUT

) + (VIN)(IS)

where both V

IN

and V

OUT

are referred to ground pin of the

ADP3603.
For example: Assuming the worst case conditions, V

IN

= 5.5 V,

V

OUT

= –2.85 V, and I

OUT

= 50 mA, calculated power dissipa-

tion is:

P ≈ (5.5 V–|–2.85 V|)(0.05 A) + (5.5 V)(0.003 A) = 149 mW

This is far below the power dissipation capability of the ADP3603
package which is 660 mW.

LAYOUT AND GROUNDING TIPS

The ADP3603 switches turn on and off very fast. Good PC
board layout practices will ensure the proper operation of the
device. Important layout considerations include:

Use adequate ground and power traces or planes.
Keep components as close as possible to the device.
Use short trace lengths from the input and output capacitors to

the input and output pins respectively.
Use single point ground for the device ground pins and the in-

put and output capacitors.
Improper layouts will result in poor load regulation, especially

with heavy loads.

APPLICATIONS
ADP3603 Evaluation Board Layout

The ADP3603 evaluation board is a general purpose circuit
board. Its flexible design allows the user to optimize the circuit
performance by external components selection and circuit con­figuration. The circuit board can be configured as a basic charge
pump voltage inverter with one pump capacitor and two bypass
capacitors or as a more complex circuit with input and output
LC filters.

PC layout is designed for surface mount components and can be
easily configured for through-hole components as well.

ADP3603

8

7

3

C3

4.7µF

1

4

VIN +4.5 – +6V

V

OUT

–3.0V

C4

4.7µF

2

5

SENSE
INPUT

L2

10µH

C5

4.7µF

C2

4.7µF

L1

1µH

C1

4.7µF

Figure 21. ADP3603 Evaluation Board Circuit Diagram

Table V. Recommended Components for Circuit in Figure 21

Component Manufacturer/Type

C3 Sprague, 293D475X0035D2W
C1, C2, C4, C5 TOKIN, 1E475ZY5UC205F
L1 Coiltronics, CTX32CT-1R0
L2 Coiltronics, CTX32CT-100

FILTERED INPUT

INPUT

OUTPUT

FILTERED OUTPUT

SHDN

OUTPUT GND

Figure 22. 8-Pin SOIC Layout, Wiring Connection

C2

C1

C4

C5

L1

C3

L2

Figure 23. 8-Pin SOIC Layout, Component Placement
Diagram (1

×

Scale)

Figure 24. 8 Pin-SOIC Layout, Component Side
(1

×

Layout)

ADP3603

REV. 0

–8–

C2169–12–9/96

PRINTED IN U.S.A.

OUTLINE DIMENSIONS

Dimensions shown in inches and (mm).

8-Pin SOIC

(SO-8)

0.1968 (5.00)

0.1890 (4.80)

8

5

41

0.2440 (6.20)

0.2284 (5.80)

PIN 1

0.1574 (4.00)

0.1497 (3.80)

0.0688 (1.75)

0.0532 (1.35)

SEATING

PLANE

0.0098 (0.25)

0.0040 (0.10)

0.0192 (0.49)

0.0138 (0.35)

0.0500
(1.27)

BSC

0.0098 (0.25)

0.0075 (0.19)

0.0500 (1.27)

0.0160 (0.41)

8°
0°

0.0196 (0.50)

0.0099 (0.25)

x 45°