Datasheet ADL5500 Datasheet (ANALOG DEVICES)

100 MHz to 6 GHz

FEATURES

True rms response
Excellent temperature stability
±0.1 dB accuracy vs. temperature over top 8 dB of input range
Up to 30 dB input dynamic range at 3.9 GHz
50 Ω input impedance
1250 mV rms, +15 dBm, maximum input
Single-supply operation: 2.7 V to 5.5 V
Low power: 3 mW at 3 V supply
RoHS compliant

APPLICATIONS

Measurement of CDMA2000, W-CDMA, and QPSK-/QAM-

based OFDM, and other complex modulation waveforms

RF transmitter or receiver power measurement

GENERAL DESCRIPTION

The ADL5500 is a mean-responding power detector for use
in high frequency receiver and transmitter signal chains from
100 MHz to 6 GHz. It is easy to apply, requiring only a single
supply between 2.7 V and 5.5 V and a power supply decoupling
capacitor. The input is internally ac-coupled and has a nominal
input impedance of 50 Ω. The output is a linear-responding dc
voltage with a conversion gain of 6.4 V/V rms at 900 MHz. The
on-chip, 1 kΩ series resistance at the output combined with an
external shunt capacitor creates a low-pass filter response that
reduces the residual ripple in the dc output voltage.

TruPwr™ Detector

ADL5500

5

1

OUTPUT (V)

0.1

0.03
–25 15

–20–15–10–50 510

INPUT (dBm)

Figure 1. Output vs. Input Level, Supply 3 V, Frequency 1.9 GHz

The ADL5500 offers excellent temperature stability with near
0 dB measurement error across temperature. The high accuracy
range, centered around +3 dBm at 900 MHz, offers ±0.1 dB
error from −40°C to +85°C over an 8.5 dB range. The ADL5500
reduces calibration requirements with low drift across a 30 dB
range over temperature and process variations.

The ADL5500 operates from −40°C to +85°C and is available in
a 4-ball, 1.0 mm × 1.0 mm wafer-level chip scale package. It is
fabricated on a proprietary high f

silicon bipolar process.

T

05546-001

The ADL5500 is intended for true power measurement of
simple and complex waveforms. The device is particularly
useful for measuring high crest factor (high peak-to-rms ratio)
signals, such as CDMA2000, W-CDMA, and QPSK/QAM­based OFDM waveforms.

FUNCTIONAL BLOCK DIAGRAM

ADL5500

i

2

RFIN

Rev. A

Information furnished by Analog Devices is believed to be accurate and reliable. However, no
responsibility is assumed by Anal og Devices for its use, nor for any infringements of patents or ot her
rights of third parties that may result from its use. Specifications subject to change without notice. No
license is granted by implication or otherwise under any patent or patent rights of Analog Devices.
Trademarks and registered trademarks are the property of their respective owners.

x

TRANS­CONDUCTANCE
CELLS

i

2

x

1kΩ

VPOS

VRMS

COMM

05546-002

INTERNAL FILTER
CAPACITOR

ERROR
AMP

BUFFER

Figure 2.

One Technology Way, P.O. Box 9106, Norwood, MA 02062-9106, U.S.A.
Tel: [phone] www.analog.com
Fax: [phone] ©2006 Analog Devices, Inc. All rights reserved.

ADL5500

TABLE OF CONTENTS

Features .............................................................................................. 1

Input Coupling Using a Series Resistor................................... 16

Applications....................................................................................... 1

General Description......................................................................... 1

Functional Block Diagram .............................................................. 1

Revision History ............................................................................... 2

Specifications..................................................................................... 3

Absolute Maximum Ratings............................................................ 7

ESD Caution.................................................................................. 7

Pin Configuration and Function Descriptions............................. 8

Typical Performance Characteristics ............................................. 9

Circuit Description......................................................................... 14

Filtering........................................................................................ 14

Applications..................................................................................... 15

Basic Connections...................................................................... 15

Output Swing .............................................................................. 15

Linearity....................................................................................... 15

Multiple RF Inputs ..................................................................... 16

Selecting the Output Low-Pass Filter Network...................... 16

Power Consumption and Power-On/-Off Response............. 16

Output Drive Capability and Buffering................................... 17

VRMS Output Offset ................................................................. 17

Device Calibration and Error Calculation.............................. 18

Calibration for Improved Accuracy......................................... 18

Drift over a Reduced Temperature Range .............................. 19

Operation Above 4.0 GHz......................................................... 19

Device Handling......................................................................... 19

Evaluation Board ........................................................................ 20

Outline Dimensions ....................................................................... 22

Ordering Guide .......................................................................... 22

REVISION HISTORY

2/06—Rev 0 to Rev. A

Changes to Features.......................................................................... 1

Changes to Table 2............................................................................ 7

Changes to Figure 5.......................................................................... 9

Changes to Figure 28 and Figure 31............................................. 13

Changes to Figure 35 Caption....................................................... 15

Changes to Power Consumption and Power-On/-Off

Response Section ............................................................................ 16

Changes to Figure 48...................................................................... 20

Changes to Ordering Guide.......................................................... 22

7/05—Revision 0: Initial Version

Rev. A | Page 2 of 24

ADL5500

SPECIFICATIONS

TA = 25°C, VS = 3.0 V, C

Table 1.

Parameter Condition Min Typ Max Unit

FREQUENCY RANGE Input RFIN 100 6000 MHz
RMS CONVERSION (f = 100 MHz) Input RFIN to output VRMS

Input Impedance 94||3 Ω||pF
Input Return Loss 10 dB
Dynamic Range

±0.1 dB Error
±0.25 dB Error

1

2

3

V
±1 dB Error

3

V
±2 dB Error

3

V
Maximum Input Level

Minimum Input Level
Conversion Gain VOUT = (Gain × VIN) + Intercept 6.1 V/V rms

V
Output Intercept

4

V
Output Voltage—High Power In PIN = +5 dBm, 400 mV rms 2.43 V
Output Voltage—Low Power In PIN = −21 dBm, 20 mV rms 0.14 V
Temperature Sensitivity PIN = −5 dBm

RMS CONVERSION (f = 450 MHz) Input RFIN to output VRMS

Input Impedance 75||1.4 Ω||pF
Input Return Loss 12.5 dB
Dynamic Range

±0.1 dB Error
±0.25 dB Error

1

2

3

V
±1 dB Error

3

V
±2 dB Error

3

V
Maximum Input Level

Minimum Input Level
Conversion Gain VOUT = (Gain × VIN) + Intercept 6.9 V/V rms

Output Intercept

4

Output Voltage—High Power In PIN = +5 dBm, 400 mV rms 2.8 V
Output Voltage—Low Power In PIN = −21 dBm, 20 mV rms 0.16 V
Temperature Sensitivity PIN = −5 dBm

= 10 nF, light condition ≤ 600 LUX, unless otherwise noted.

FLT

CW input, −40°C < TA < +85°C
Delta from 25°C, VS = 5 V 5 dB
VS = 3 V 17.5 dB

= 5 V 20 dB

S

VS = 3 V 25 dB

= 5 V 29 dB

S

VS = 3 V 28.5 dB

= 5 V 33 dB

S

±0.25 dB error
±1 dB error

= 5 V 4.6 7.2 V/V rms

S

3

3

0.03 V
= 5 V −20 +100 mV

S

25°C ≤ T

−40°C ≤ T

≤ 85°C

A

≤ +25°C

A

CW input, −40°C < TA < +85°C
Delta from 25°C, VS = 5 V 8 dB
VS = 3 V 19 dB

= 5 V 24 dB

S

VS = 3 V 24.5 dB

= 5 V 29 dB

S

VS = 3 V 27.5 dB

= 5 V 33 dB

S

±0.25 dB error
±1 dB error

3

3

0.03 V

25°C ≤ T

−40°C ≤ T

≤ 85°C

A

≤ +25°C

A

6 dBm

−18.5 dBm

0.0032 dB/°C

−0.0042 dB/°C

5 dBm

−19.5 dBm

0.0020 dB/°C

−0.0023 dB/°C

Rev. A | Page 3 of 24

ADL5500

Parameter Condition Min Typ Max Unit

RMS CONVERSION (f = 900 MHz) Input RFIN to output VRMS

Input Impedance 62||1.1 Ω||pF
Input Return Loss 13 dB
Dynamic Range

±0.1 dB Error
±0.25 dB Error
V
±1 dB Error
V

±2 dB Error
V
Maximum Input Level

Minimum Input Level
Conversion Gain VOUT = (Gain × VIN) + Intercept 6.4 V/V rms

Output Intercept
Output Voltage—High Power In PIN = +5 dBm, 400 mV rms 2.61 V
Output Voltage—Low Power In PIN = −21 dBm, 20 mV rms 0.15 V
Temperature Sensitivity PIN = −5 dBm

RMS CONVERSION (f = 1900 MHz) Input RFIN to output VRMS

Input Impedance 43||0.9 Ω||pF
Input Return Loss 11.5 dB
Dynamic Range

±0.1 dB Error

±0.25 dB Error

V

±1 dB Error

V

±2 dB Error
V
Maximum Input Level

Minimum Input Level
Conversion Gain VOUT = (Gain × VIN) + Intercept 5.0 V/V rms

Output Intercept
Output Voltage—High Power In PIN = +5 dBm, 400 mV rms 2.02 V
Output Voltage—Low Power In PIN = −21 dBm, 20 mV rms 0.11 V
Temperature Sensitivity PIN = −5 dBm

1

2

3

3

3

4

1

2

3

3

3

4

CW input, −40°C < TA < +85°C
Delta from 25°C, VS = 5 V 8.5 dB
VS = 3 V 19.5 dB

= 5 V 23 dB

S

VS = 3 V 24.5 dB

= 5 V 29 dB

S

VS = 3 V 28 dB

= 5 V 32 dB

S

±0.25 dB error
±1 dB error

3

3

6 dBm

−19 dBm

0.04 V

25°C ≤ T

−40°C ≤ T

≤ +85°C

A

≤ +25°C

A

0.0018 dB/°C

−0.0023 dB/°C

CW input, −40°C < TA < +85°C
Delta from 25°C, VS = 5 V 7 dB
VS = 3 V 20 dB

= 5 V 23 dB

S

VS = 3 V 26 dB

= 5 V 30 dB

S

VS = 3 V 31.5 dB

= 5 V 33 dB

S

±0.25 dB error
±1 dB error

3

3

8 dBm

−19.5 dBm

0.02 V

25°C ≤ T

−40°C ≤ T

≤ 85°C

A

≤ +25°C

A

0.0017 dB/°C

−0.0031 dB/°C

Rev. A | Page 4 of 24

ADL5500

Parameter Condition Min Typ Max Unit

RMS CONVERSION (f = 2350 MHz) Input RFIN to output VRMS

Input Impedance 37||0.9 Ω||pF
Input Return Loss 9 dB
Dynamic Range

±0.1 dB Error
±0.25 dB Error
V
±1 dB Error
V

±2 dB Error
V
Maximum Input Level

Minimum Input Level
Conversion Gain VOUT = (Gain × VIN) + Intercept 4.5 V/V rms

Output Intercept
Output Voltage—High Power In PIN = +5 dBm, 400 mV rms 1.82 V
Output Voltage—Low Power In PIN = −21 dBm, 20 mV rms 0.11 V
Temperature Sensitivity PIN = −5 dBm

RMS CONVERSION (f = 2700 MHz) Input RFIN to output VRMS

Input Impedance 34||0.8 Ω||pF
Input Return Loss 8.5 dB
Dynamic Range

±0.1 dB Error

±0.25 dB Error

V

±1 dB Error

V

±2 dB Error
V
Maximum Input Level

Minimum Input Level
Conversion Gain VOUT = (Gain × VIN) + Intercept 4.2 V/V rms

Output Intercept
Output Voltage—High Power In PIN =+5 dBm, 400 mV rms 1.67 V
Output Voltage—Low Power In PIN = –21 dBm, 20 mV rms 0.1 V
Temperature Sensitivity PIN = –5 dBm

1

2

3

3

3

4

1

2

3

3

3

4

CW input, −40°C < TA < +85°C
Delta from 25°C, VS = 5 V 5 dB
VS = 3 V 5 dB

= 5 V 10 dB

S

VS = 3 V 28.5 dB

= 5 V 32 dB

S

VS = 3 V 32 dB

= 5 V 36 dB

S

±0.25 dB error
±1 dB error

3

3

8 dBm

−19.5 dBm

0.02 V

25°C ≤ T

−40°C ≤ T

≤ 85°C

A

≤ +25°C

A

0.0027 dB/°C

−0.0046 dB/°C

CW input, −40°C < TA < +85°C
Delta from 25°C, VS = 5 V 5 dB
VS = 3 V 5 dB

= 5 V 8.5 dB

S

VS = 3 V 28.5 dB

= 5 V 32 dB

S

VS = 3 V 33 dB

= 5 V 36 dB

S

±0.25 dB error
±1 dB error

3

3

9 dBm

−19.5 dBm

0.02 V

25°C ≤ T

−40°C ≤ T

≤ 85°C

A

≤ +25°C

A

0.0030 dB/°C

−0.0049 dB/°C

Rev. A | Page 5 of 24

ADL5500

Parameter Condition Min Typ Max Unit

RMS CONVERSION (f = 3900 MHz) Input RFIN to output VRMS

Input Impedance 30||0.6 Ω||pF
Input Return Loss 9 dB
Dynamic Range

±0.1 dB Error
±0.25 dB Error
V
±1 dB Error
V

±2 dB Error
V
Maximum Input Level

Minimum Input Level
Conversion Gain VOUT = (Gain × VIN) + Intercept 3.2 V/V rms

Output Intercept
Output Voltage—High Power In PIN = +5 dBm, 400 mV rms 1.28 V
Output Voltage—Low Power In PIN = –21 dBm, 20 mV rms 0.08 V
Temperature Sensitivity PIN = –5 dBm

OUTPUT OFFSET No signal at RFIN 40 150 mV
POWER SUPPLIES

Operating Range −40°C < TA < +85°C 2.7 5.5 V
Quiescent Current No signal at RFIN

1

The available output swing, and hence the dynamic range, is altered by the supply voltage; see Figure 8.

2

Error referred to delta from 25°C response; see Figure 16 through Figure 21.

3

Error referred to best-fit line at 25°C

4

Calculated using linear regression.

5

Supply current is input level dependant; see Figure 6.

1

2

3

3

3

4

CW input, −40°C < TA < +85°C
Delta from 25°C, VS = 5 V 2 dB
VS = 3 V 5.5 dB

= 5 V 8 dB

S

VS = 3 V 28.5 dB

= 5 V 32 dB

S

VS = 3 V 34 dB

= 5 V 36.5 dB

S

±0.25 dB error
±1 dB error

3

3

12 dBm

−17 dBm

0.02 V

25°C ≤ T

−40°C ≤ T

≤ 85°C

A

≤ +25°C

A

5

0.0035 dB/°C

−0.0066 dB/°C

1.0 mA

Rev. A | Page 6 of 24

ADL5500

ABSOLUTE MAXIMUM RATINGS

Table 2.

Parameter Rating

Supply Voltage V
VRMS 0 V, V
RFIN 1.25 V rms
Equivalent Power, re 50 Ω 15 dBm
Internal Power Dissipation 150 mW
θJA (WLCSP) 260°C/W
Maximum Junction Temperature 125°C
Operating Temperature Range −40°C to +85°C
Storage Temperature Range −65°C to +150°C

S

5.5 V

S

ESD CAUTION

ESD (electrostatic discharge) sensitive device. Electrostatic charges as high as 4000 V readily accumulate on
the human body and test equipment and can discharge without detection. Although this product features
proprietary ESD protection circuitry, permanent damage may occur on devices subjected to high energy
electrostatic discharges. Therefore, proper ESD precautions are recommended to avoid performance
degradation or loss of functionality.

Stresses above those listed under Absolute Maximum Ratings
may cause permanent damage to the device. This is a stress
rating only; functional operation of the device at these or any
other conditions above those indicated in the operational
section of this specification is not implied. Exposure to absolute
maximum rating conditions for extended periods may affect
device reliability.

Rev. A | Page 7 of 24

ADL5500

PIN CONFIGURATION AND FUNCTION DESCRIPTIONS

BUMP 1
INDICATOR

VRMS

VPOS

1

4

COMM

RFIN

2

3

05546-003

TOP VIEW

(BUMP SIDE DOWN)

Not to Scale

Figure 3. 4-Ball WLCSP Pin Configuration

Table 3. Pin Function Descriptions

Ball No. Mnemonic Description

1 VRMS

Output Pin. Rail-to-rail voltage output with limited current drive capability. The output has an internal 1 kΩ

series resistance. High resistive loads are recommended to preserve output swing.
2 COMM Device Ground Pin.
3 RFIN Signal Input Pin. Internally ac-coupled after internal termination resistance. Nominal 50 Ω input impedance.
4 VPOS Supply Voltage Pin. Operational range 2.7 V to 5.5 V.

Rev. A | Page 8 of 24

ADL5500

TYPICAL PERFORMANCE CHARACTERISTICS

TA = 25°C, VS = 5.0 V, C

10

1

OUTPUT (V)

0.1

0.03
–25 15

–20 –15 –10 –5 0 5 10

Figure 4. Output vs. Input Level, Frequencies 100 MHz, 450 MHz, 900 MHz,

1900 MHz, 2350 MHz, 2700 MHz, and 3900 MHz, Supply 5.0 V

5.0

4.5

4.0

3.5

3.0

2.5

2.0

OUTPUT (V)

1.5

1.0

0.5

0

0.20.40.60.81.01.2

01

Figure 5. Output vs. Input Level (Linear Scale), Frequencies 100 MHz, 450 MHz,

900 MHz,1900 MHz, 2350 MHz, 2700 MHz, and 3900 MHz, Supply 5.0 V

11
10

9
8
7
6
5
4
3

SUPPLY CURRENT (mA)

2
1
0

0 0.9

0.1 0.2 0.3 0.4 0.5 0.6 0.80.7

Figure 6. Supply Current vs. Input Level, Supplies 3.0 V and 5.0 V,

Temperatures −40°C, +25°C, and +85°C

= 10 nF, light condition ≤ 600 LUX, Colors: black = +25°C, blue = −40°C, red = +85°C, unless otherwise noted.

FLT

3

100MHz
450MHz
900MHz
1900MHz

2

2350MHz
2700MHz
3900MHz

1

0

ERROR (dB)

–1

–2

–3

–25

–20 –15 –10 –5 0 5 10

INPUT (dBm)

INPUT (dBm)

100MHz
450MHz
900MHz
1900MHz
2350MHz
2700MHz
3900MHz

05546-004

Figure 7. Linearity Error vs. Input Level, Frequencies 100 MHz, 450 MHz,
900 MHz, 1900 MHz, 2350 MHz, 2700 MHz, and 3900 MHz, Supply 5.0 V

10

5.5V

5.0V

2.7V

3.0V

INPUT (V rms)

1

OUTPUT (V)

100MHz
450MHz
900MHz
1900MHz
2350MHz
2700MHz
3900MHz

.4

05546-005

0.1

0.03
–25 15

–20 –15 –10 –5 0 5 10

INPUT (dBm)

Figure 8. Output vs. Input Level,

Supply 2.7 V, 3.0 V, 5.0 V, and 5.5 V, Frequency 900 MHz

25

3.0V

INPUT (V rms)

5.0V

05546-006

20

15

RETURN LOSS (dB)

10

5

06

12345

FREQUENCY (GHz)

Figure 9. Return Loss vs. Frequency

05546-007

15

05546-008

05546-009

Rev. A | Page 9 of 24

ADL5500

3

3

2

1

0

ERROR (dB)

–1

–2

–3

–20 –15 –10 –5 0 5 10

–25 15

INPUT (dBm)

Figure 10. Temperature Drift Distributions for 55 Devices at −40°C, +25°C,

and +85°C vs. +25°C Linear Reference, Frequency 450 MHz, Supply 5.0 V

3

2

1

0

ERROR (dB)

–1

2

1

0

ERROR (dB)

–1

–2

05546-010

–3

–20 –15 –10 –5 0 5 10

–25 15

INPUT (dBm)

05546-013

Figure 13. Temperature Drift Distributions for 55 Devices at −40°C, +25°C,

and +85°C vs. +25°C Linear Reference, Frequency 2350 MHz, Supply 5.0 V

3

2

1

0

ERROR (dB)

–1

–2

–3

–20 –15 –10 –5 0 5 10

–25 15

INPUT (dBm)

Figure 11. Temperature Drift Distributions for 55 Devices at −40°C, +25°C,

and +85°C vs. +25°C Linear Reference, Frequency 900 MHz, Supply 5.0 V

3

2

1

0

ERROR (dB)

–1

–2

–3

–20 –15 –10 –5 0 5 10

–25 15

INPUT (dBm)

Figure 12. Temperature Drift Distributions for 55 Devices at −40°C, +25°C,

and +85°C vs. +25°C Linear Reference, Frequency 1900 MHz, Supply 5.0 V

–2

05546-011

–3

–20 –15 –10 –5 0 5 10

–25 15

INPUT (dBm)

05546-014

Figure 14. Temperature Drift Distributions for 55 Devices at −40°C, +25°C,

and +85°C vs. +25°C Linear Reference, Frequency 2700 MHz, Supply 5.0 V

3

2

1

0

ERROR (dB)

–1

–2

05546-012

–3

–20 –15 –10 –5 0 5 10

–25 15

INPUT (dBm)

05546-015

Figure 15. Temperature Drift Distributions for 55 Devices at −40°C, +25°C,

and +85°C vs. +25°C Linear Reference, Frequency 3900 MHz, Supply 5.0 V

Rev. A | Page 10 of 24

ADL5500

3

3

2

1

0

ERROR (dB)

–1

–2

–3

–20 –15 –10 –5 0 5 10

–25 15

INPUT (dBm)

Figure 16. Output Delta from +25°C Output Voltage for 55 Devices

at −40°C and +85°C, Frequency 450 MHz, Supply 5.0 V

3

2

1

0

ERROR (dB)

–1

2

1

0

ERROR (dB)

–1

–2

05546-016

–3

–20 –15 –10 –5 0 5 10

–25 15

INPUT (dBm)

05546-019

Figure 19. Output Delta from +25°C Output Voltage for 55 Devices

at −40°C and +85°C, Frequency 2350 MHz, Supply 5.0 V

3

2

1

0

ERROR (dB)

–1

–2

–3

–20 –15 –10 –5 0 5 10

–25 15

INPUT (dBm)

Figure 17. Output Delta from +25°C Output Voltage for 55 Devices

at −40°C and +85°C, Frequency 900 MHz, Supply 5.0 V

3

2

1

0

ERROR (dB)

–1

–2

–3

–20 –15 –10 –5 0 5 10

–25 15

INPUT (dBm)

Figure 18. Output Delta from +25°C Output Voltage for 55 Devices

at −40°C and +85°C, Frequency 1900 MHz, Supply 5.0 V

–2

05546-017

–3

–20 –15 –10 –5 0 5 10

–25 15

INPUT (dBm)

05546-020

Figure 20. Output Delta from +25°C Output Voltage for 55 Devices

at −40°C and +85°C, Frequency 2700 MHz, Supply 5.0 V

3

2

1

0

ERROR (dB)

–1

–2

05546-018

–3

–20 –15 –10 –5 0 5 10

–25

INPUT (dBm)

05546-021

15

Figure 21. Output Delta from +25°C Output Voltage for 55 Devices

at −40°C and +85°C, Frequency 3900 MHz, Supply 5.0 V

Rev. A | Page 11 of 24

ADL5500

10

CW
QPSK, 4.8dB CF
8PSK, 4.8dB CF
16QAM, 6.3dB CF
64QAM, 7.4dB CF

1

OUTPUT (V)

0.1

0.03
–20 –15 –10 –5 0 5 10

–25 15

INPUT (dBm)

Figure 22. Output vs. Input Level with Different Waveforms, 10 MHz Signal

BW for All Modulated Signals, Supply 5.0 V, Frequency 1900 MHz

05546-022

3.0

2.5

2.0

1.5

1.0

0.5
0

–0.5

ERROR (dB)

–1.0
–1.5
–2.0
–2.5
–3.0

–20 –15 –10 –5 0 5

–25 10

INPUT (dBm)

CW
QPSK, 4.8dB CF
8PSK, 4.8dB CF
16QAM, 6.3dB CF
64QAM, 7.4dB CF

Figure 25. Error from CW Linear Reference vs. Input with Different Waveforms,

10 MHz Signal BW for All Modulated Signals, Supply 5.0 V, Frequency 1900 MHz

05546-025

3.0

2.5

2.0

1.5

1.0

0.5

–0.5

ERROR (dB)

–1.0
–1.5
–2.0
–2.5
–3.0

0

–20 –15 –10 –5 0 5

–25

INPUT (dBm)

CW
BPSK, 11dB CF
QPSK, 11dB CF
16QAM, 12dB CF
64QAM, 11dB CF

Figure 23. Error from CW Linear Reference vs. Input Level for Various

802.16 OFDM Waveforms at 2.35 GHz, 10 MHz Signal BW and
256 Subcarriers for All Modulated Signals, S upply 5 .0 V

3.0
CW

12.2kbps, DPCCH (–5.46dB, 15ksps) +
DPDCH (0dB, 60ksps), 3.4dB CF
64kbps, DPCCH (–9.54dB, 15ksps) +

2.0
DPDCH (0dB, 240ksps), 3.4dB CF

144kbps, DPCCH (–11.48dB, 15ksps) +
DPDCH (0dB, 480ksps), 3.3dB CF
384kbps, DPCCH (–11.48dB, 15ksps) +

1.0
DPDCH (0dB, 960ksps), 3.3dB CF

768kbps, DPCCH (–11.48dB, 15ksps) +
DPDCH1 + 2 (0dB, 960ksps), 5.8dB CF

0

3.0

2.5

2.0

1.5

1.0

0.5
0

–0.5

ERROR (dB)

–1.0
–1.5
–2.0
–2.5

05546-023

10

–3.0

–20 –15 –10 –5 0 5

–25 10

INPUT (dBm)

CW
BPSK, 11dB CF
QPSK, 11dB CF
16QAM, 12dB CF
64QAM, 11dB CF

05546-026

Figure 26. Error from CW Linear Reference vs. Input Level for Various

802.16 OFDM Waveforms at 3.5 GHz, 10 MHz Signal BW and
256 Subcarriers for All Modulated Signals, Supply 5.0 V

3.0

2.0

1.0

0

ERROR (dB)

–1.0

–2.0

–3.0

–25

–20 –15 –10 –5 0 5

INPUT (dBm)

Figure 24. Error from CW Linear Reference vs. Input with Various

WCDMA Up Link Waveforms at 1900 MHz

05546-024

10

Rev. A | Page 12 of 24

ERROR (dB)

–1.0

–2.0

–3.0

–20 –15 –10 –5 0 5

–25 10

CW
PICH, 4.7dB CF
PICH + FCH (9.6kbps), 4.8dB CF
PICH + FCH (9.6kbps) +
DCCH, 6.3dB CF
PICH + FCH (9.6kbps) +
SCH (153.6kbps), 6.7dB CF
PICH + FCH (9.6kbps) +
DCCH + SCH (153.6kbps), 7.6dB CF

INPUT (dBm)

Figure 27. Error from CW Linear Reference vs. Input with Various

CDMA2000 Reverse Link Waveforms at 900 MHz

05546-027

ADL5500

TEK P6204

FET PROBE

HPE3631A

POWER SUPPLY

ADL5500

1

VRMS

C4 C1

COMM

2

VPOS

RFIN

4

3

C2
100pF

0.1μF

TEK P6204

FET PROBE

C4 C2

1

2

VRMS

COMM

HP8110A

PULSE

GENERATOR

ADL5500

VPOS

RFIN

50Ω

AD811

732Ω

4

100pFC10.1μF

3

TEK TDS784C

SCOPE

HP8648B

SIGNAL

GENERATOR

Figure 28. Hardware Configuration for Output

Response to Modulated Pulse Input

900MHz
PULSED RFIN

400mV rms
RF INPUT

250mV rms

160mV rms

VRMS

70mV rms

400μs PER
HORIZONTAL
DIVISION

500mV PER
VERTICAL
DIVISION

Figure 29. Output Response to Modulated Pulse Input for Various RF Input

Levels, Supply 3 V, Modulation Frequency 900 MHz, No Filter Capacitor

900MHz
PULSED RFIN

05546-028

TEK TDS784C

SCOPE

HP8648B

SIGNAL

GENERATOR

05546-031

Figure 31. Hardware Configuration for Output Response to

Power Supply Gating Measurements

VPOS

400mV rms
RF INPUT

250mV rms

160mV rms

VRMS
500mV PER

70mV rms

200μs PER
HORIZONTAL

05546-029

DIVISION

VERTICAL
DIVISION

05546-032

Figure 32. Output Response to Gating on Power Supply for Various RF Input
Levels, Supply 3 V, Modulation Frequency 900 MHz, 0.01 μF Filter Capacitor

400mV rms
RF INPUT

250mV rms

VRMS

160mV rms

500mV PER
VERTICAL
DIVISION

70mV rms

400μs PER
HORIZONTAL
DIVISION

Figure 30. Output Response to Modulated Pulse Input for Various RF Input

Levels, Supply 3 V, Modulation Frequency 900 MHz, 0.01 μF Filter Capacitor

05546-030

Rev. A | Page 13 of 24

ADL5500

CIRCUIT DESCRIPTION

The ADL5500 is an rms-responding (mean power) detector that
provides an approach to the exact measurement of RF power
that is independent of waveform. It achieves this function by
using a proprietary technique in which the outputs of two
identical squaring cells are balanced by the action of a high-gain
error amplifier.

The signal to be measured is applied to the input of the first
squaring cell through the input matching network. The input is
matched to offer a broadband 50 Ω input impedance from
100 MHz to 6 GHz. The input matching network has a high-pass
corner frequency of approximately 90 MHz.

The ADL5500 responds to the voltage, V
squaring this voltage to generate a current proportional to V

, at its input by

IN

2

.

IN

This current is applied to an internal load resistor in parallel
with a capacitor, followed by a low-pass filter, which extracts the
mean of V

2

. Although essentially voltage responding, the

IN

associated input impedance calibrates this port in terms of
equivalent power. Therefore, 1 mW corresponds to a voltage
input of 224 mV rms referenced to 50 Ω. Because both the
squaring cell input impedance and the input matching network
are frequency dependent, the conversion gain is a function of
signal frequency.

The voltage across the low-pass filter, whose frequency can be
arbitrarily low, is applied to one input of an error-sensing
amplifier. A second identical voltage-squaring cell is used to
close a negative feedback loop around this error amplifier. This
second cell is driven by a fraction of the quasi-dc output voltage
of the ADL5500. When the voltage at the input of the second
squaring cell is equal to the rms value of V

, the loop is in a

IN

stable state, and the output then represents the rms value of the
input.

By completing the feedback path through a second squaring
cell, identical to the one receiving the signal to be measured,
several benefits arise. First, scaling effects in these cells cancel;
therefore, the overall calibration can be accurate, even though
the open-loop response of the squaring cells taken separately
need not be. Note that in implementing rms-dc conversion, no
reference voltage enters into the closed-loop scaling. Second,
the tracking in the responses of the dual cells remains very close
over temperature, leading to excellent stability of calibration.

The squaring cells have very wide bandwidth with an intrinsic
response from dc to microwave. However, the dynamic range of
such a system is small due in part to the much larger dynamic
range at the output of the squaring cells. There are practical
limitations to the accuracy of sensing very small error signals at
the bottom end of the dynamic range, arising from small random
offsets that limit the attainable accuracy at small inputs.

On the other hand, the squaring cells in the ADL5500 have a
Class-AB aspect; the peak input is not limited by its quiescent
bias condition but is determined mainly by the eventual loss of
square-law conformance. Consequently, the top end of their
response range occurs at a large input level (approximately
700 mV rms) while preserving a reasonably accurate square-law
response. The maximum usable range is, in practice, limited by
the output swing. The rail-to-rail output stage can swing from a
few millivolts above ground to within 100 mV below the supply.
An example of the output induced limit, given a conversion gain
of 6.4 V/V rms at 900 MHz and assuming a maximum output of

2.9 V with a 3 V supply, has a maximum input of 2.9 V rms/6.4
or 450 mV rms.

FILTERING

An important aspect of rms-dc conversion is the need for
averaging (the function is root-mean-square). The on-chip
averaging in the square domain has a corner frequency of
approximately 150 kHz and is sufficient for common
modulation signals, such as CDMA, WCDMA, and QPSK­/QAM-based OFDM (for example, WLAN and WiMAX). It
ensures the accuracy of rms measurement for these signals;
however, it leaves significant ripple on the output. To reduce
this ripple, an external shunt capacitor can be used at the output
to form a low-pass filter with the on-chip 1 kΩ resistance (see
the

Selecting the Output Low-Pass Filter Network section).

Rev. A | Page 14 of 24

ADL5500

V

APPLICATIONS

BASIC CONNECTIONS

Figure 33 shows the basic connections for the ADL5500. The
device is powered by a single supply of between 2.7 V and 5.5 V
with a quiescent current of 1.0 mA. The VPOS pin is decoupled
using 100 pF and 0.1 μF capacitors.

The ADL5500 RF input does not require external termination
components because it is internally matched for an overall
broadband input impedance of 50 Ω.

+VS2.7V TO 5.5V

100pF 0.1μF

RFIN

RMS

ADL5500

VRMS

1

CFLT

COMM

2

Figure 33. Basic Connections for ADL5500

VPOS

RFIN

4

3

OUTPUT SWING

At 900 MHz, the output voltage is nominally 6.4 times the input
rms voltage (a conversion gain of 6.4 V/V rms). The output
voltage swings from near ground to 4.9 V on a 5.0 V supply.

Figure 34 shows the output swing of the ADL5500 to a CW
input for various supply voltages. It is clear from
operating the device at lower supply voltages reduces dynamic
range as the output headroom decreases.

10

1

OUTPUT (V)

Figure 34 that

5.5V

5.0V

2.7V

3.0V

05546-033

LINEARITY

Because the ADL5500 is a linear-responding device, plots of
output voltage vs. input voltage result in a straight line. It is
more useful to plot the error on a logarithmic scale, as shown in
Figure 35. The deviation of the plot for the ideal straight-line
characteristic is caused by output clipping at the high end and
by signal offsets at the low end. However, it should be noted that
offsets at the low end can be either positive or negative; therefore,
this plot could also trend upwards at the low end.
through

Figure 15 show error distributions for a large

population of devices.

3

100MHz
450MHz
900MHz
1900MHz

2

2350MHz
2700MHz
3900MHz

1

0

ERROR (dB)

–1

–2

–3

Figure 35. Representative Unit, Error in dB vs. Input Level, V

–20 –15 –10 –5 0 5 10

–25 15

INPUT (dBm)

It is also apparent in Figure 35 that the error plot tends to shift
to the right with increasing frequency. The squaring cell has an
input impedance that decreases with frequency. The matching
network compensates for the change and maintains the input
impedance at a nominal 50 Ω. The result is a decrease in the
actual voltage across the squaring cell as the frequency
increases, reducing the conversion gain. Similarly, conversion
gain is less at frequencies near 100 MHz because of the small
on-chip coupling capacitor.

Figure 10

= 5.0 V

S

05546-007

0.1

0.03

Figure 34. Output Swing for Supply Voltages of 2.7 V, 3.0 V, 5.0 V, and 5.5 V

–20 –15 –10 –5 0 5 10

–25 15

INPUT (dBm)

05546-008

Rev. A | Page 15 of 24

ADL5500

L

L

INPUT COUPLING USING A SERIES RESISTOR

Figure 36 shows a technique for coupling the input signal into
the ADL5500 that can be applicable where the input signal is
much larger than the input range of the ADL5500. A series
resistor combines with the input impedance of the ADL5500 to
attenuate the input signal. Because this series resistor forms a
divider with the frequency dependent input impedance, the
apparent gain changes greatly with frequency. However, this
method has the advantage of very little power being tapped off
in RF power transmission applications. If the resistor is large
compared to the transmission line’s impedance, the VSWR of
the system is relatively unaffected.

R

RFIN

SERIES

Figure 36. Attenuating the Input Signal

RFIN

ADL5500

05546-036

MULTIPLE RF INPUTS

Figure 37 shows a technique for combining multiple RF input
signals to the ADL5500. Some applications can share a single
detector for multiple bands. Three 16.5 Ω resistors in a T-network
combine the three 50 Ω terminations (including the ADL5500).
The broadband resistive combiner ensures each port of the
T-network sees a 50 Ω termination. Because there is only 6 dB
of isolation from one port of the combiner to the other ports,
only one band should be active at a time.

BAND 1

DIRECTIONA

COUPLER

DIRECTIONA

COUPLER

Figure 37. Combining Multiple RF Input Signals

50Ω

BAND 2

50Ω

16.5Ω

16.5Ω

16.5Ω
RFIN

ADL5500

05546-051

SELECTING THE OUTPUT LOW-PASS FILTER NETWORK

The ADL5500’s internal filter capacitor provides averaging in
the square domain but leaves some residual ac on the output.
Signals with high peak-to-average ratios, such as W-CDMA
or CDMA2000, can produce ac-residual levels on the ADL5500
dc output. To reduce the effects of these low frequency
components in the waveforms, some additional filtering is
required.

The output of the ADL5500 can be filtered by placing a
capacitor between VRMS (Pin 1) and ground. The combination
of the on-chip 1 kΩ output series resistance and the external
shunt capacitor forms a low-pass filter to reduce the residual ac.

Tabl e 4 shows the effect of several capacitor values for various
communications standards with high peak-to-average ratios
along with the residual ripple at the output, in peak-to-peak and
rms volts. Note that large load capacitances increase the turn-on
and pulse response times (see

Figure 29 and Figure 30).

Table 4. Waveform and Output Filter Effects on Residual AC

Output Residual AC
Waveform C

FILT

V dc mV p-p mV rms

64QAM 0.01 μF 0.5 7.0 1.4

(7.4 dB CF) 1.0 7.4 1.5

2.0 7.6 1.6

0.1 μF 0.5 6.7 1.4

1.0 7.2 1.5

2.0 7.4 1.5
W-CDMA RL 0.01 μF 0.5 10 1.7

(3.4 dB CF) 1.0 16 2.4

2.0 45 5.6

0.1 μF 0.5 7 1.5

1.0 9 1.6

2.0 14 2.3
CDMA2000 UL 0.01 μF 0.5 46 6

(6.7 dB CF) 1.0 85 13

2.0 191 27

0.1 μF 0.5 17 3

1.0 31 5

2.0 68 9

POWER CONSUMPTION AND POWER-ON/-OFF RESPONSE

The quiescent current consumption of the ADL5500 varies with
the size of the input signal from approximately 1 mA for no
signal up to 6 mA at an input level of 0.7 V rms (10 dBm, re
50 Ω). If the input is driven beyond this point, the supply
current increases sharply (as shown in
variation in quiescent current with power supply voltage.

The ADL5500 can be disabled by simply removing the power to
the device.

Figure 32 shows a plot of the output response to the
supply being turned on (that is, VPOS is pulsed) with an output
shunt capacitor of 0.01 μF. Again, the turn-on time is influenced
strongly by the size of the output shunt capacitor.

To improve the falling edge of the supply gating response and
the pulse response, a resistor can be placed in parallel with the
output shunt capacitor. The added resistance helps discharge
the capacitor. Although this method reduces the power-off
time, the added load resistor also attenuates the output (see the
Output Drive Capability and Buffering section).

Figure 6). There is little

Rev. A | Page 16 of 24

ADL5500

OUTPUT DRIVE CAPABILITY AND BUFFERING

The ADL5500 is capable of sourcing an output current of
approximately 3 mA. The output current is sourced through the
on-chip 1 kΩ series resistor; therefore, any load resistor forms a
voltage divider with this on-chip resistance. It is recommended
that the ADL5500 drive high resistive loads to preserve output
swing (preferably >100 kΩ). If an application requires driving
a low resistance load, a simple buffering circuit can be used,
as shown in
or decrease the nominal conversion gain (see
Figure 39). In Figure 39, the AD8031 buffers a resistive divider
to give half of the slope. In
doubles the slope. Using other resistor values, the slope can be
changed to an arbitrary value. The AD8031 rail-to-rail op amp,
used in these examples, can swing from 50 mV to 4.95 V on a
single 5 V supply and operates at supply voltages down to 2.7 V.
If high output current is required (>10 mA), the AD8051, which
also has rail-to- rail capability, can be used down to a supply
voltage of 3 V. It can deliver up to 45 mA of output current.

Figure 40. Similar circuits can be used to increase

Figure 38 and

Figure 38, the op amp’s gain of two

0.1μF

100pF

5V

VRMS OUTPUT OFFSET

The ADL5500 has a ±1 dB error detection range of about 30 dB,
as shown in
best fit line defined in the linear region of the output response.
Below an input power of −20 dBm, the response is no longer
linear and begins to lose accuracy. In addition, depending on
the supply voltage, saturation of the output limits the detection
accuracy above 10 dBm. Calibration points should be chosen in
the linear region, avoiding the nonlinear ranges at the high and
low extremes.

OUTPUT (V)

Figure 10 to Figure 15. The error is referred to the

10

1

0.1

AD8031

5kΩ

5kΩ

0.01μF

12.8V/V rms

05546-037

5V

0.01μF

3.2V/V rms

5V

0.01μF

6.4V/V rms

VPOS

VRMS

ADL5500

COMM

Figure 38. Output Buffering Options, Slope of 12.8 V/V rms at 900 MHz

0.1μF

Figure 39. Output Buffering Options, Slope of 3.2 V/V rms at 900 MHz

0.1μF

100pF

VPOS

VRMS

ADL5500

COMM

100pF

VPOS

VRMS

ADL5500

4kΩ

5kΩ

AD8031

AD8031

05546-038

0.01
–35–30–25–20–15–10 –5 0 5

–40

INPUT (dBm)

Figure 41. Output vs. Input Level Distribution of 55 Devices,

Frequency 900 MHz, Supply 3.0 V

10

Figure 41 shows the distribution of the output response vs.
the input power for multiple devices. The ADL5500 loses
accuracy at low input powers as the output response begins to
fan out. As the input power is reduced, the spread of the output
response increases along with the error. Although some devices
follow the ideal linear response at very low input powers, not
all devices continue the ideal linear regression to a near 0 V
y-intercept. Some devices exhibit output responses that rapidly
decrease and some flatten out. With no RF signal applied,
the ADL5500 has a typical output offset of 40 mV (with a
maximum of 150 mV).

05546-040

COMM

Figure 40. Output Buffering Options, Slope of 6.4 V/V rms at 900 MHz

05546-039

Rev. A | Page 17 of 24

ADL5500

DEVICE CALIBRATION AND ERROR CALCULATION

Because slope and intercept vary from device to device, board­level calibration must be performed to achieve high accuracy. In
general, calibration is performed by applying two input power
levels to the ADL5500 and measuring the corresponding output
voltages. The calibration points are generally chosen to be
within the linear operating range of the device. The best fit line
is characterized by calculating the slope and intercept using the
following equations:

− V

)/(V

− V

Slope = (V

Intercept = V

RMS2

RMS1

RMS1

IN2

− (Slope × V

where:

is the rms input voltage to RFIN.

V

IN

is the voltage output at VRMS.

V

RMS

Once slope and intercept have been calculated, an equation can
be written that allows calculation of an (unknown) input power
based on the measured output voltage.

= (V

V

IN

− Intercept)/Slope (3)

RMS

For an ideal (known) input power, the law conformance error of
the measured data can be calculated as

ERROR (dB) =
20 × log [(V

RMS, MEASURED

− Intercept)/(Slope × V

Figure 42 includes a plot of the error at 25°C, the temperature at
which the ADL5500 is calibrated. Note that the error is not zero.
This is because the ADL5500 does not perfectly follow the ideal
linear equation, even within its operating region. The error at
the calibration points is, however, equal to zero by definition.

3

2

1

0

) (1)

IN1

) (2)

IN1

)] (4)

IN, IDEAL

+85°C

+25°C

Figure 42 also includes error plots for the output voltage at

−40°C and +85°C. These error plots are calculated using the
slope and intercept at +25°C. This is consistent with calibration
in a mass-production environment where calibration at
temperature is not practical.

CALIBRATION FOR IMPROVED ACCURACY

Another way of presenting the error function of the ADL5500 is
shown in
temperatures is calculated with respect to the transfer function
at ambient. This is a key difference in comparison to the
previous plots. Up to now, the errors have been calculated with
respect to the ideal linear transfer function at ambient. When
this alternative technique is used, the error at ambient becomes
equal to 0 by definition (see

This plot is a useful tool for estimating temperature drift at a
particular power level with respect to the (nonideal) response at
ambient. The linearity and dynamic range tend to be improved
artificially with this type of plot because the ADL5500 does not
perfectly follow the ideal linear equation (especially outside of
its linear operating range). Achieving this level of accuracy in
an end application requires calibration at multiple points in the
device’s operating range.

In some applications, very high accuracy is required at just one
power level or over a reduced input range. For example, in a
wireless transmitter, the accuracy of the high power amplifier
(HPA) is most critical at or close to full power. The ADL5500
offers a tight error distribution in the high input power range,
as shown in
around +3 dBm at 900 MHz, offers 8.5 dB of ±0.1 dB detection
error over temperature. Multiple point calibration at ambient
temperature in the reduced range offers precise power
measurement with near 0 dB error from −40°C to +85°C.

Figure 43. In this case, the dB error at hot and cold

Figure 43).

Figure 43. The high accuracy range, centered

3

2

1

+85°C

+25°C

ERROR (dB)

–1

–2

–3

–25 15

–20–15–10–50 510

Figu re 42. Error from Linear Reference vs. Input at −4 0°C, +2 5°C, a nd +85° C

vs. +25°C Linear Reference, Frequency 900 MHz, Supply 5.0 V

–40°C

INPUT (dBm)

ERROR (dB)

05546-052

Rev. A | Page 18 of 24

0

–1

–2

–3

–25

–20 –15 –10 –5 0 5 10

Figure 43. Error from +25°C Output Voltage at −40°C, +25°C, and +85°C

After Ambient Normalization, Frequency 900 MHz, Supply 5.0 V

–40°C

15

INPUT (dBm)

05546-053

ADL5500

The high accuracy range center varies over frequency. At
900 MHz, the region is centered at approximately 3 dBm. At
higher frequencies, the high accuracy range is centered at
higher input powers (see

Figure 16 to Figure 21).

DRIFT OVER A REDUCED TEMPERATURE RANGE

Figure 44 shows the error over temperature for a 1.9 GHz input
signal. Error due to drift over temperature consistently remains
within ±0.25 dB and only begins to exceed this limit when the
ambient temperature goes above +50°C and below −10°C. For
all frequencies using a reduced temperature range, higher
measurement accuracy is achievable.

1.00

0.75

0.50

0.25

ERROR (dB)

–0.25

–0.50

+85°C
+70°C
+50°C
+30°C
+25°C
+15°C
0°C
–10°C
–25°C
–40°C

0

3

2

1

0

ERROR (dB)

–1

–2

–3

–20 –15 –10 –5 0 5 10

–25 15

INPUT (dBm)

Figure 45. Temperature Drift Distributions for Six Devices at −40°C, +25°C,

and +85°C After Ambient Normalization, Frequency 5.0 GHz, Supply 5.0 V

3

2

1

05546-042

–0.75

–1.00

–15 –10 –5 0 5 10

–20

INPUT (dBm)

15

Figure 44. Typical Drift at 1.9 GHz for Various Temperatures

OPERATION ABOVE 4.0 GHz

The ADL5500 works at frequencies above 4.0 GHz, but exhibits
slightly higher output voltage temperature drift.
Figure 46 show the error distributions of six devices at 5.0 GHz
and 6.0 GHz over temperature. Although the temperature drift
is larger than at lower frequencies, the error distributions at
each temperature remain tight throughout the central linear
region. Due to the repeatability of the drift from part-to-part,
compensation can be applied to reduce the effects of
temperature drift.

Figure 45 and

0

05546-041

ERROR (dB)

–1

–2

–3

–20–15–10–50 510

–25

INPUT (dBm)

05546-043

15

Figure 46. Temperature Drift Distributions for Six Devices at −40°C, +25°C,

and +85°C After Ambient Normalization, Frequency 6.0 GHz, Supply 5.0 V

DEVICE HANDLING

The wafer-level chip scale package consists of solder bumps
connected to the active side of the die. The part is lead-free with

95.5% tin, 4.0% silver, and 0.5% copper solder bump composition.
The WLCSP can be mounted on printed circuit boards using
standard surface-mount assembly techniques; however, caution
should be taken to avoid damaging the die. See the
Application Note for additional information. WLCSP devices
are bumped die; therefore, the exposed die can be sensitive to
light, which can influence specified limits. Lighting in excess of
600 LUX can degrade performance.

AN-617

Rev. A | Page 19 of 24

ADL5500

V

EVALUATION BOARD

Figure 48 shows the schematic of the ADL5500 evaluation
board. The layout and silkscreen of the evaluation board layers
are shown in
single supply in the 2.7 V to 5.5 V range. The power supply is
decoupled by 100 pF and 0.01 μF capacitors.
various configuration options of the evaluation board.

Problems caused by impedance mismatch can arise using the
evaluation board to examine the ADL5500 performance. One
way to reduce these problems is to put a coaxial 3 dB attenuator
on the RFIN SMA connector. Mismatches at the source, cable,
and cable interconnection, as well as those occurring on the
evaluation board, can cause these problems.

A simple (and common) example of such a problem is triple
travel due to mismatch at both the source and the evaluation
board. Here the signal from the source reaches the evaluation
board and mismatch causes a reflection. When that reflection
reaches the source mismatch, it causes a new reflection, which
travels back to the evaluation board, adding to the original
signal incident at the board. The resultant voltage varies with
both cable length and frequency dependence on the relative
phase of the initial and reflected signals. Placing the 3 dB pad at
the input of the board improves the match at the board and thus
reduces the sensitivity to mismatches at the source. When such
precautions are taken, measurements are less sensitive to cable
length and other fixture issues. In an actual application when
the distance between ADL5500 and source is short and well­defined, this 3 dB attenuator is not needed.

Figure 49 to Figure 52. The board is powered by a

Table 5 details the

Land Pattern and Soldering Information

Figure 47 shows the land pattern used on the ADL5500
evaluation board. Pad diameters of 0.28 mm are used with a
solder paste mask opening of 0.38 mm. For the RF input trace, a
trace width of 0.30 mm is used, which corresponds to a 50 Ω
characteristic impedance for the dielectric material being used
(FR4). All traces going to the pads are tapered down to 0.15 mm.
For the RFIN line, the length of the tapered section is 0.20 mm.

0.30 mm

(50 Ω)

GROUND
PLANE

0.20 mm

0.50 mm

(PASTE MASK OPENING)

0.38 mm

0.28 mm

VPOS

VRMS

0.15 mm

RFIN

0.50 mm

COMM

0.15 mm

Figure 47. Land Pattern Used on the ADL5500 Evaluation Board

05546-054

TO EDGE

CONNECTOR

RMS

10nF

R6

(OPEN)

C4

R8
(OPEN)

R3
0Ω

1

2

ADL5500

VRMS

COMM

VPOS

RFIN

4

3

Figure 48. Evaluation Board Schematic

RFIN

C1
100pF

C2

0.1μF
VPOS

05546-044

Table 5. Evaluation Board Configuration Options

Component Description Default Condition

VPOS, GND Ground and Supply Vector Pins. Not Applicable
C1, C2 Power Supply Decoupling. The nominal supply decoupling of 0.01 μF and 100 pF.

C1 = 0.01 μF (Size 0402)
C2 = 100 pF (Size 0402)

R3, R8, C4

Output Filtering. The combination of the internal 1 kΩ output resistance and C4 produce
a low-pass filter to reduce output ripple. The output can also be scaled down using the
resistor divider pads, R3 and R8. In addition, resistors and capacitors can be placed in C4 and

R3 = 0 Ω (Size 0402)
R8 = Open (Size 0402)
C4 = 10 nF (Size 0402)

R8 to load test VRMS.

R6

Alternate Interface. R6 allows VOUT to be accessible from the edge connector, which is only

R6 = Open (Size 0402)

used for characterization.

Rev. A | Page 20 of 24

ADL5500

05546-045

Figure 49. Layout of Component Side (WLCSP)

Figure 51. Silkscreen of Component Side (WLCSP)

05546-047

05546-048

Figure 50. Layout of Circuit Side (WLCSP)

05546-046

Figure 52. Silkscreen of Circuit Side (WLCSP)

Rev. A | Page 21 of 24

ADL5500

OUTLINE DIMENSIONS

0.675

(CB-4)

0.596

0.516
SEATING

PLANE

0.50 BSC
BALL PITCH

0.030 NOM
COPLANARITY

0.345

0.295

0.245

12

BOTTOM VIE W

(BALL SIDE UP)

A

B

111105-0

Ordering
Quantity

A1 BALL
CORNER

1.010

0.960 SQ

0.910

TOP VIEW

(BALL SIDE DOW N)

0.381

0.356

0.331

0.270

0.240

0.210

Figure 53. 4-Ball Wafer-Level Chip Scale Package [WLCSP]

Dimensions shown in millimeters

ORDERING GUIDE

Model Temperature Range Package Description Package Option Branding

ADL5500ACBZ-P71–40°C to +85°C 4-Ball WLCSP, 7” Pocket Tape and Reel CB-4 Q06 3,000
ADL5500ACBZ-P21–40°C to +85°C 4-Ball WLCSP, 7” Pocket Tape and Reel CB-4 Q06 250
ADL5500-EVALZ

1

Z = Pb-free part.

1

Evaluation Board

Rev. A | Page 22 of 24

ADL5500

NOTES

Rev. A | Page 23 of 24

ADL5500

NOTES

©2006 Analog Devices, Inc. All rights reserved. Trademarks and
registered trademarks are the property of their respective owners.
D05546–0–2/06(A)

Rev. A | Page 24 of 24