Datasheet AD8212 Datasheet (ANALOG DEVICES)

High Voltage

V

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FEATURES

Adjustable gain
High common-mode voltage range

7 V to 65 V typical
7 V to >500 V with external pass transistor

Current output

Integrated 5 V series regulator
8-lead MSOP package

Operating temperature range of −40°C to +125°C

APPLICATIONS

Current shunt measurement
Motor controls

DC-to-DC converters

Power supplies
Battery monitoring

Remote sensing

Current Shunt Monitor

AD8212

FUNCTIONAL BLOCK DIAGRAM

V+

1

AD8212

BIAS

CIRCUIT

COM BIAS ALPHA

I

OUT

Figure 1.

SENSE

8

OUTPUT

CURRENT

COMPENSATI ON

6325

05942-001

GENERAL DESCRIPTION

The AD8212 is a high common-mode voltage, current shunt
monitor. It accurately amplifies a small differential input voltage
in the presence of large common-mode voltages up to 65 V
(>500 V with an external PNP transistor).

The AD8212 is ideal for current monitoring across a shunt
r

esistor in applications controlling loads, such as motors and
solenoids. The current output of the device is proportional to
the input differential voltage. The user can select an external
resistor to set the desired gain. The typical common-mode
voltage range of the AD8212 is 7 V to 65 V.

Another feature of the AD8212 is high voltage operation,

ich is achieved by using an external high voltage breakdown

wh
PNP transistor. In this configuration, the common-mode range
of the AD8212 is equal to the breakdown of the external PNP
transistor. Therefore, operation at several hundred volts is easily
achieved (see

Figure 23).

The AD8212 features a patented output base current compensa­t

ion circuit for high voltage operation mode. This ensures that
no base current is lost through the external transistor and
excellent output accuracy is maintained regardless of common­mode voltage or temperature.

Rev. A

Information furnished by Analog Devices is believed to be accurate and reliable. However, no
responsibility is assumed by Anal og Devices for its use, nor for any infringements of patents or ot her
rights of third parties that may result from its use. Specifications subject to change without notice. No
license is granted by implication or otherwise under any patent or patent rights of Analog Devices.
Trademarks and registered trademarks are the property of their respective owners.

One Technology Way, P.O. Box 9106, Norwood, MA 02062-9106, U.S.A.
Tel: [phone] www.analog.com
Fax: [phone] ©2007 Analog Devices, Inc. All rights reserved.

AD8212

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TABLE OF CONTENTS

Features.............................................................................................. 1

Applications....................................................................................... 1

Functional Block Diagram .............................................................. 1

General Description ......................................................................... 1

Revision History ............................................................................... 2

Specifications..................................................................................... 3

Absolute Maximum Ratings............................................................ 4

ESD Caution.................................................................................. 4

Pin Configuration and Function Descriptions............................. 5

Typical Performance Characteristics ............................................. 6

Theory of Operation ........................................................................ 9

REVISION HISTORY

11/07—Rev. 0 to Rev. A

Increased Operating Temperature Range........................Universal

5/07—Revision 0: Initial Version

Normal Operation (7 V to 65 V Supply (V+) Range)..............9

High Voltage Operation Using an External PNP Transistor 10

Output Current Compensation Circuit................................... 10

Applications Information.............................................................. 11

General High-Side Current Sensing........................................ 11

Motor Control............................................................................. 11

500 V Current Monitor ............................................................. 11

Bidirectional Current Sensing.................................................. 12

Outline Dimensions....................................................................... 13

Ordering Guide .......................................................................... 13

Rev. A | Page 2 of 16

AD8212

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SPECIFICATIONS

VS = 15 V, T

Table 1.

Parameter Conditions/Comments Min Typ Max Unit

SUPPLY VOLTAGE (V+) No external pass transistor 7 65 V
With external PNP transistor
SUPPLY CURRENT2 (I
V+ = 7 V to 65 V 220 720 μA
High voltage operation, using external PNP 200 1500 μA
VOLTAGE OFFSET

Offset Voltage (RTI) TA ±2 mV
Over Temperature (RTI) T
Offset Drift T

INPUT

Input Impedance

Differential 2 kΩ
Common Mode (VCM) V+ = 7 V to 65 V 5 MΩ

Voltage Range

Differential Maximum voltage between V+ and V

V

SENSE

OUTPUT

Transconductance 1000 μA/V
Current Range (I
Gain Error for T
Impedance 20 MΩ
Voltage Range 0 V+ − 5 V

REGULATOR

Nominal Value 7 V ≤ V+ ≤ 65 V 4.80 5 5.20 V
PSRR 7 V ≤ V+ ≤ 65 V 80 dB
Bias Current (I

T

DYNAMIC RESPONSE

Small Signal −3 dB Bandwidth Gain = 10 1000 kHz
Gain = 20 500 kHz
Gain = 50 100 kHz

Settling Time Within 0.1% of the true output, gain = 20 2 μs
ALPHA PIN INPUT CURRENT 25 μA
NOISE

0.1 Hz to 10 Hz, RTI 1.1 μV p-p

Spectral Density, 1 kHz, RTI 40
TEMPERATURE RANGE

For Specified Performance (T

1

Range dependent on the VCE breakdown of the transistor.

2

The AD8212 supply current in normal voltage operation (V+ = 7 V to 65 V) is the bias current (I

differential voltage and can range from 0 μA to 500 μA. I
to the High Voltage Operation Using an External PNP Transistor section.

3

The current of the amplifier into V

for more information.

= −40°C to +125°C, TA = 25°C, unless otherwise noted.

OPR

= I

+ I

OUT

, 7 V ≤ V+ ≤ 65 V 185 200 μA

, high voltage operation 200 1000 μA

in this mode of operation is typically 185 μA and 200 μA maximum. For high voltage operation mode, refer

BIAS

(Pin 8) Current

OUT

7 V ≤ V+ ≤ 65 V, with respect to 500 μA full scale ±1 %

OPR

) T

BIAS

SUPPLY

OPR

OPR

3

V+ = 7 V to 65 V, T

) 7 V ≤ V+ ≤ 65 V, 0 mV to 500 mV differential input 500 μA

OPR

OPR

) −40 +125 °C

OPR

(Pin 8) increases when operating in high voltage mode. See the High Voltage Operation Using an External PNP Transistor section

SENSE

1

)

BIAS

7 >500 V

±3 mV
±10 μV/°C

SENSE

100 200 nA

OPR

500 mV

nV/√Hz

) added to output current (I

BIAS

). Output current varies upon input

OUT

Rev. A | Page 3 of 16

AD8212

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ABSOLUTE MAXIMUM RATINGS

T

= −40°C to +125°C, unless otherwise noted.

OPR

Table 2.

Parameter Rating

Supply Voltage 65 V
Continuous Input Voltage 68 V
Reverse Supply Voltage 0.3 V
Operating Temperature Range −40°C to +125°C
Storage Temperature Range −40°C to +150°C
Output Short-Circuit Duration Indefinite

Stresses above those listed under Absolute Maximum Ratings
may cause permanent damage to the device. This is a stress
rating only; functional operation of the device at these or any
other conditions above those indicated in the operational
section of this specification is not implied. Exposure to absolute
maximum rating conditions for extended periods may affect
device reliability.

ESD CAUTION

Rev. A | Page 4 of 16

AD8212

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PIN CONFIGURATION AND FUNCTION DESCRIPTIONS

V+ 1

AD8212

2

COM

3

BIAS

TOP VIEW

(Not to Scale)

NC 4

NC = NO CONNECT

Figure 2. Pin Configuration

8

7

6

5

V

SENSE

NC

ALPHA

I

OUT

1

2

3

05942-002

Figure 3. Metallization Diagram

Table 3. Pin Function Descriptions

Pin No. Mnemonic X Coordinate Y Coordinate Description

1 V+ −393 +219 Supply Voltage (Inverting Amplifier Input).
2 COM −392 +67 Regulator Low Side.
3 BIAS −392 −145
4 NC – –
5 I

+386 −82 Output Current.

OUT

6 ALPHA +386 +23
7 NC +386 +118
8 V

+386 +210 Noninverting Amplifier Input.

SENSE

Bias Circuit Low Side.
No Connect.

Current Compensation Circuit Input.
No Connect.

8

6

5

05942-025

Rev. A | Page 5 of 16

AD8212

V

(

V

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TYPICAL PERFORMANCE CHARACTERISTICS

195

1200

190

T = +125°C

185

180

175

170

QUIESCENT CURRENT (µA)

165

160

5.2

5.1

5.0

4.9

REGULATOR VOLTAGE (V)

4.8

T = +25°C

5 101520 2530 35404550556065

SUPPLY VOLTAGE (V)

Figure 4. Supply Current vs. Supply (Pin V+) (I

T = +25°C

T = +125°C

5 101520 2530 35404550556065

SUPPLY VOLTAGE (V)

T = –40°C

OUT

T = –40°C

Figure 5. Regulator Voltage vs. Supply (Pin V+)

= 0 mA)

1000

800

)
µ

OS

600

INPUT

400

200

05942-005

0
–40 –20 0 20 40 60 80 100 120

TEMPERATURE ( °C)

05942-008

Figure 7. Input Offset Voltage vs. Temperature

1.0

0.9

0.8

0.7

0.6

0.5

0.4

0.3

OFFSET VO LTAGE RTI (mV )

0.2

0.1

05942-006

+125°C

+25°C

–40°C

0

7 1217222732374247525762

VOLTAGE SUPPLY (V)

05942-009

Figure 8 .Input Offset Voltage vs. Supply (Pin V+)

50

45

40

35

30

25

GAIN (dB)

20

15

10

5

0

1k 10k 100k 1M 10M

G = +50

G = +20

G = +10

FREQUENCY (Hz)

Figure 6. Gain vs. Frequency

5942-021

10

9

8

7

6

5

4

3

2

OUTPUT CURRENT DRIFT (nA/ °C)

1

0

0 50 100 150 200 250 300 350 400 450 500

DIFFERENTIAL INPUT VOLTAGE (mV)

Figure 9. Output Current Drift vs. Differential Input Voltage

Rev. A | Page 6 of 16

05942-010

AD8212

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100

V

IN

20mV/DIV

10

V+ = 15V

= 50k

R

1

OUTPUT ERRO R (%)

0.1

G = +10

G = +20

G = +50

V

OUT

500mV/DIV

0V

OUT

0.01
0 10203040 60 80 10050 70 90 500

DIFFERENTIAL INPUT VOLTAGE (mV)

Figure 10. Total Output Error Due to

Input Offset vs. Differential

Input Voltage

V

IN

20mV/DIV

V+ = 15V

= 5k

R

OUT

V

OUT

50mV/DIV

0V

5µs/DIV

Figure 11. Step Response (Gain = 5)

5µs/DIV

05942-023

05942-014

Figure 13. Step Response (Gain = 50)

V

IN

100mV/DIV

V+ = 15V

R

= 5k

OUT

V

OUT

200mV/DIV

05942-012

5µs/DIV

05942-015

Figure 14. Step Response (Gain = 5)

V

IN

20mV/DIV

V

OUT

200mV/DIV

0V

V+ = 15V

R

OUT

5µs/DIV

Figure 12. Step Response (Gain = 20)

= 20k

05942-013

V

IN

100mV/DIV

V

OUT

1V/DIV

0V

Figure 15. Step Response (Gain = 20)

Rev. A | Page 7 of 16

5µs/DIV

V+ = 15V

R

OUT

= 20k

05942-016

AD8212

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V

100mV/DIV

0V

IN

V

OUT

2V/DIV

V+ = 15V

R

OUT

= 50k

5.2

5.1

5.0

4.9

REGULATOR VOLTAGE (V)

T = –40°C

T = +25°C

T = +125°C

5µs/DIV

Figure 16. Step Response (Gain = 50)

05942-017

4.8
100 200 300 400 500 600 700 800 900 1000 1100 1200

BIAS CURRENT (µA)

Figure 19. Regulator Voltage High Voltage Mode (I

= 0 mA) vs.

OUT

5942-024

Bias Current

5.2

V

IN

100mV/DIV

5.1

V+ = 300V

V+ = 15V

R

= 20k

OUT

V

OUT

2V/DIV

0V

2µs/DIV

05942-018

Figure 17. Step Response Falling

V

IN

100mV/DIV

V+ = 15V

R

= 20k

OUT

V

OUT

2µs/DIV

2V/DIV

05942-019

0V

Figure 18. Step Response Rising

5.0

V+ = 200V

4.9

REGULATOR VOLTAGE (V)

4.8
–40 –25 –10 5 20 35 50 65 8 0 95 110 125

TEMPERATURE ( °C)

Figure 20. Regulator Voltage vs. Temperature

(

High Voltage Operation)

550

500

450

400

350

300

250

200

V+ MAXIMUM RANGE

150

V+ MINIMUM RANG E

V+ OPERATING RANGE (V)

100

50

0

10 20 30 50 70 100 150 200 250 300 350 400 450 500

R

Figure 21. Supply Range (V+) vs. Bias Resistor Value

(

High Voltage Operation)

BIAS

(k)

V+ = 100V

05942-007

05942-020

Rev. A | Page 8 of 16

AD8212

V

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THEORY OF OPERATION

NORMAL OPERATION (7 V TO 65 V SUPPLY (V+) RANGE)

In typical applications, the AD8212 measures a small
differential input voltage generated by a load current
flowing through a shunt resistor.

The operational amplifier (A1) is connected across the shunt

sistor (R

re
battery/supply side, and the noninverting input connected
to the load side of the system. Amplifier A1 is powered via
an internal series regulator (depicted as a Zener diode in
Figure 22). This regulator maintains a constant 5 V between
th

e battery/supply terminal of the AD8212 and COM (Pin 2),
which represents the lowest common point of the internal
circuitry.

A load current flowing through the external shunt resistor
p

roduces a voltage at the input terminals of the AD8212.
Amplifier A1 responds by causing Transistor Q1 to conduct the
necessary current through Resistor R1 to equalize the potential
at both the inverting and noninverting inputs of Amplifier A1.

The current through the emitter of Transistor Q1 (I
proportional to the input voltage (V
load current (I
output current (I
external resistor, the value of which is dependent on the input
to output gain equation desired in the application.

The transfer function for the AD8212 is

I

OUT

V

SENSE

V

OUT

V

OUT

where:

= 1000 µA/V.

g

m

In normal voltage operation mode, the bias circuit is connected
t

o GND, as shown in

185 μA throughout the 7 V to 65 V (V+) range.

) with its inverting input connected to the

SHUNT

), and, therefore, the

SENSE

) through the shunt resistor (R

LOAD

) is converted to a voltage by using an

OUT

= (gm × V

= I

LOAD

= I

OUT

= (V

× R

SENSE

SENSE

× R

× R

OUT

)

SHUNT

OUT

)/1000

Figure 22. In this mode, I

OUT

SHUNT

is typically

BIAS

) is

). The

I

BATTERY

1

R1 R2

Q1

OUT

R

Figure 22. Typical Connection (7 V to 65 V Supply (Pin V+) Range)

OUT

I

OUT

R

AD8212

BIAS

CIRCUIT

SHUNT

A1

LOAD

8

OUTPUT

CURRENT

COMPENSATION

6325

LOAD

05942-003

When using the AD8212 as described, the battery/supply
voltage in the system must be between 7 V to 65 V. The 7 V
minimum supply range is necessary to turn on the internal
regulator (shown as a Zener diode in

ltage then remains a constant 5 V, regardless of the supply

vo

Figure 22). This regulated

(V+) voltage. The 65 V maximum limit in this mode of
operation is due to the breakdown voltage limitation of the
AD8212 process.

Typically, a 1% resistor can be used to convert the output

urrent to a voltage. Ta b le 4 provides suggested R

c

Table 4. Suggested R

Gain (V/V) R

Values

OUT

OUT

(kΩ)

values.

OUT

1 1
10 10
20
50

20

49.9

100 100

Rev. A | Page 9 of 16

AD8212

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HIGH VOLTAGE OPERATION USING AN EXTERNAL PNP TRANSISTOR

The AD8212 offers features that simplify measuring current in
the presence of common-mode voltages greater than 65 V. This
is achieved by connecting an external PNP transistor at the
output of the AD8212, as shown in Figure 23. The V
down voltage of this PNP becomes the operating common-mode
range of the AD8212. PNP transistors with breakdown voltages
exceeding 300 V are inexpensive and readily available in small
packages.

BATTERY

1

R1 R2

Q1

Q2

VOUT

R

OUT

Figure 23. High Voltage Operation Using External PNP

R

AD8212

BIAS

CIRCUIT

R

SHUNT

A1

BIAS

8

OUTPUT

CURRENT

COMPENSATI ON

6325

The AD8212 features an integrated 5 V series regulator. This
regulator ensures that at all times COM (Pin 2), which is the
most negative of all the terminals, is always 5 V less than the
supply voltage (V+). Assuming a battery voltage (V+) of 100 V,
it follows that the voltage at COM (Pin 2) is

(V+) – 5 V = 95

V

The base emitter junction of Transistor Q2, in addition to the
V

of one internal transistor, makes the collector of Transistor Q1

be

approximately equal to

95 V + 2(V

) = 95 V + 1.2 V = 96.2 V

be(Q2)

This voltage appears across external Transistor Q2. The voltage

ross Transistor Q1 is

ac

100 V – 96.2 V = 3.8 V

In this manner, Transistor Q2 withstands 95.6 V and the

nternal Transistor Q1 is only subjected to voltages well below

i
its breakdown capability.

break-

CE

LOAD

05942-004

In this mode of operation, the supply current (I

BIAS

) of the
AD8212 circuit increases based on the supply range and the
R

resistor chosen. For example

BIAS

if

V+ = 500 V and R

= (V+ − 5 V)/R

I

BIAS

= 500 kΩ

BIAS

BIAS

then,

I

= (500 – 5)/500 kΩ = 990 μA

BIAS

In high voltage operation, it is recommended that I

remain

BIAS

within 200 μA to 1 mA. This ensures that the bias circuit is
turned on, allowing the device to function as expected. At the
same time, the current through the bias circuit/regulator is
limited to 1 mA. Refer to Figure 19 and Figure 21 for I

BIAS

and
V+ information when using the AD8212 in a high voltage
configuration.

When operating the AD8212, as depicted in Figure 23,

ransistor Q2 can be a FET or a bipolar PNP transistor. The

T
latter is much less expensive, however the magnitude of I
conducted to the output resistor (R

) is reduced by the

OUT

OUT

amount of current lost through the base of the PNP. This leads
to an error in the output voltage reading.

The AD8212 includes an integrated patented circuit, which

mpensates for the output current that is lost through the base

co
of the external PNP transistor. This ensures that the correct
transconductance of the amplifier is maintained. The user can
opt for an inexpensive bipolar PNP, instead of a FET, while
maintaining a comparable level of accuracy.

OUTPUT CURRENT COMPENSATION CIRCUIT

The base of the external PNP, Q2, is connected to ALPHA
(Pin 6) of the AD8212. The current flowing in this path is
mirrored inside the current compensation circuit. This
current then flows in Resistor R2, which is the same value
as Resistor R1. The voltage created by this current across
Resistor R2, displaces the noninverting input of Amplifier A1
by the corresponding voltage. Amplifier A1 responds by driving
the base of Transistor Q1 so as to force a similar voltage
displacement across Resistor R1, thereby increasing I

Because the current generated by the output compensation

cuit is equal to the base current of Transistor Q2, and the

cir
resulting displacements across Resistor R1 and Resistor R2 result
in equal currents, the increment of current added to the output
current is equivalent to the base current of Transistor Q2.
Therefore, the integrated output current compensation circuit
has corrected I

such that no error results from the base

OUT

current lost at Transistor Q2.

This feature of the AD8212 greatly improves I

OUT

allows the user to choose an inexpensive bipolar PNP (with low
beta) with which to monitor current in the presence of high
voltages (typically several hundred volts).

.

OUT

accuracy and

Rev. A | Page 10 of 16

AD8212

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APPLICATIONS INFORMATION

GENERAL HIGH-SIDE CURRENT SENSING

The AD8212 output is intended to drive high impedance nodes.
Therefore, if interfacing with a converter, it is recommended
that the output voltage across R
of the AD8212 is not affected.

I

LOAD

BATTERY

R

SHUNT

AD8212

V+

1

V

8

SENSE

COM

2

BIAS

3

NC

4

NOTES

1. NC = NO CONNECT.

NC

ALPHA

I

OUT

7

6

5

Figure 24. Normal Voltage Range Operation

Careful calculations must be made when choosing a gain
resistor so as not to exceed the input voltage range of the
converter. The output of the AD8212 can be as high as
(V+) − 5 V. However, the true output maximum voltage is
dependent upon the differential input voltage, and the resulting
output current across R

, which can be as high as 500 μA

OUT

(based on a 500 mV maximum input differential limit).

be buffered, so that the gain

OUT

LOAD

AD8661

I

R

OUT

OUT

ADC

05942-026

500 V CURRENT MONITOR

As noted in the High Voltage Operation Using an External PNP
Tr an si st o r section, the AD8212 common-mode voltage range is

tended by using an external PNP transistor. This mode of

ex
operation is achievable with many amplifiers featuring a current
output. However, typically an external Zener regulator must be
added, along with a FET device, to withstand the common-mode
voltage and maintain output current accuracy.

The AD8212 features an integrated regulator (which acts as a
Z

ener regulator). It offers output current compensation that
allows the user to maintain excellent output current accuracy
by using any PNP transistor. Reliability is increased due to
lower component count. Most importantly, the output current
accuracy is high, allowing the user to choose an inexpensive
PNP transistor to withstand the increased common-mode
voltage.

I

LOAD

500V

3

4

500k

R

SHUNT

AD8212

V+1

COM2

BIAS

NC

V

SENSE

NC

ALPHA

I

OUT

LOAD

8

7

6

5

VOUT

R

OUT

MOTOR CONTROL

The AD8212 is a practical solution for high-side current sensing
in motor control applications. In cases where the shunt resistor
is referenced to battery and the current flowing is unidirectional,
as shown in Figure 25, the AD8212 monitors the current with
no

additional supply pin necessary.

BATTERY

AD8212

V+

1

V

8

SENSE

COM

2

BIAS

3

NC

4

NOTES

1. NC = NO CONNECT.

NC

ALPHA

I

OUT

7

6

5

R

OUT

Figure 25. High-Side Current Sensing for Motor Control

I

MOTOR

V

OUT

MOTOR

05942-028

NOTES

1. TRANSIST OR V
VOLTAG E MUST BE 500V.

2. NC = NO CONNECT.

BREAKDOWN

CE

05942-027

Figure 26. High Voltage Operation Using External PNP

Rev. A | Page 11 of 16

AD8212

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BIDIRECTIONAL CURRENT SENSING

The AD8212 is a unidirectional current sensing device.
Therefore, in power management applications where both the
charge and load currents must be monitored, two devices can
be used and connected as shown in

Figure 27. In this case,

I

LOAD

I

CHARGE

R

SHUNT

V

1 increases as I

OUT

increases when I

flows through the shunt resistor. V

LOAD

flows through the input shunt resistor.

CHARGE

OUT

2

V

SENSE

1 1

BATTERY

I

OUT

R

1

OUT

AD8212

BIAS

CIRCUIT

COM BIAS ALPHA I

8 8

OUTPUT

CURRENT

COMPENSATION

6325

V

1

OUT

V

SENSE

OUTPUT

CURRENT

COMPENSATIO N

6 3 2

AD8212

BIAS

CIRCUIT

V+V+

LOAD

CHARGE

COMBIASALPHA

OUT

5

V

2

R

OUT

OUT

2

5942-011

Figure 27. Bidirectional Current Sensing

Rev. A | Page 12 of 16

AD8212

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OUTLINE DIMENSIONS

3.20

3.00

2.80

8

5

3.20

3.00

1

2.80

PIN 1

0.65 BSC

0.95

0.85

0.75

0.15

0.38

0.00

0.22

COPLANARITY

0.10

COMPLIANT TO JEDEC STANDARDS MO-187-AA

Figure 28. 8-Lead Mini Small Outline Package [MSOP]

ORDERING GUIDE

Model Temperature Range Package Description Package Option Branding

AD8212YRMZ
AD8212YRMZ-RL
AD8212YRMZ-R7

1

Z = RoHS Compliant Part.

1

1

1

−40°C to +125°C 8-Lead MSOP RM-8 Y04

−40°C to +125°C 8-Lead MSOP, 13” Tape and Reel RM-8 Y04

−40°C to +125°C 8-Lead MSOP, 7” Tape and Reel RM-8 Y04

5.15

4.90

4.65

4

1.10 MAX

0.23

SEATING
PLANE

0.08

(RM-8)

Dim

ensions shown in millimeters

8°
0°

0.80

0.60

0.40

Rev. A | Page 13 of 16

AD8212

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NOTES

Rev. A | Page 14 of 16

AD8212

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NOTES

Rev. A | Page 15 of 16

AD8212

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NOTES

©2007 Analog Devices, Inc. All rights reserved. Trademarks and
registered trademarks are the property of their respective owners.
D05942-0-11/07(A)

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