Single 16-bit DAC, 4 LSB INL
Power-on reset to midscale or zero-scale
Guaranteed monotonic by design
3 power-down functions
Low power serial interface with Schmitt-triggered inputs
Small 8-lead SOT-23 package, low power
Fast settling time of 4 μs typically
2.7 V to 5.5 V power supply
Low glitch on power-up
interrupt facility
SYNC
APPLICATIONS
Process control
Data acquisition systems
Portable battery-powered instruments
Digital gain and offset adjustment
Programmable voltage and current sources
Programmable attenuators
GENERAL DESCRIPTION
The AD5061, a member of ADI’s nanoDAC family, is a low
power, single 16-bit buffered voltage-out DAC that operates
from a single 2.7 V to 5.5 V supply. The part offers a relative
accuracy specification of ±4 LSB and operation is guaranteed
monotonic with a ±1 LSB DNL specification. The part uses a
versatile 3-wire serial interface that operates at clock rates
up to 30 MHz, and is compatible with standard SPI®, QSPI™,
MICROWIRE™, and DSP interface standards. The reference for
the AD5061 is supplied from an external V
buffer is also provided on-chip. The part incorporates a poweron reset circuit that ensures the DAC output powers up to midscale or zero scale and remains there until a valid write takes
place to the device. The part contains a power-down feature
that reduces the current consumption of the device to typically
330 nA at 5 V and provides software-selectable output loads
while in power-down mode. The part is put into power-down
mode over the serial interface. Total unadjusted error for the
part is <3 mV. This part exhibits very low glitch on power-up.
pin. A reference
REF
AD5061
FUNCTIONAL BLOCK DIAGRAM
V
REF
POWER-ON
RESET
DAC
REGISTER
INPUT
CONTROL
LOGIC
SCLK DIN
SYNCDACGND
BUF
REF(+)
DAC
POWER-DOWN
CONTROL LO GIC
Figure 1.
Table 1. Related Devices
Part No. Description
AD5062
2.7 V to 5.5 V, 16-bit nanoDAC D/A,
1 LSB INL, SOT-23
AD5063
2.7 V to 5.5 V, 16-bit nanoDAC D/A,
1 LSB INL, MSOP
AD5040/AD5060
2.7 V to 5.5 V, 14-bit/16-bit nanoDAC D/A,
1 LSB INL, SOT-23
PRODUCT HIGHLIGHTS
1. Available in a small 8-lead SOT-23 package.
2. 16-bit resolution, 4 LSB INL.
3. Low glitch on power-up.
4. High speed serial interface with clock speeds up to 30 MHz.
5. Three power-down modes available to the user.
6. Reset to known output voltage (midscale or zero scale).
V
DD
OUTPUT
BUFFER
AD5061
RESISTOR
NETWORK
V
OUT
GND
04762-001
Rev. B
Information furnished by Analog Devices is believed to be accurate and reliable. However, no
responsibility is assumed by Anal og Devices for its use, nor for any infringements of patents or ot her
rights of third parties that may result from its use. Specifications subject to change without notice. No
license is granted by implication or otherwise under any patent or patent rights of Analog Devices.
Trademarks and registered trademarks are the property of their respective owners.
Changes to Data Sheet Title and Product Highlights Section.... 1
Changes to Ordering Guide.......................................................... 20
1/06—Rev. 0 to Rev. A
Changes to General Description .................................................... 1
Changes to Table 2............................................................................ 3
Changes to Figure 19 Caption....................................................... 10
Added Figure 28 to Figure 36........................................................12
Changes to Serial Interface Section.............................................. 15
Changes to Power-Down Modes Section.................................... 16
Changes to Ordering Guide.......................................................... 20
7/05—Revision 0: Initial Version
Rev. B | Page 2 of 20
Page 3
AD5061
SPECIFICATIONS
VDD = 5.5 V, V
Table 2.
B Grade1
Parameter Min Typ Max Unit Test Conditions/Comments
STATIC PERFORMANCE
Resolution 16 Bits
Relative Accuracy (INL)2 ±0.5 ±4 LSB −40°C to +85°C, B grade
±0.5 ±4 −40°C to +125°C, Y grade
Total Unadjusted Error (TUE) ±0.5 ±3.0 mV −40°C to +85°C, B grade
±0.5 ±3.0 −40°C to +125°C, Y grade
Differential Nonlinearity (DNL) ±0.5 ±1 LSB Guaranteed monotonic, −40°C to +85°C, B grade
±0.5 ±1
Gain Error ±0.01 ±0.05 % of FSR TA = −40°C to +85°C, B grade
±0.01 ±0.05 TA = −40°C to +125°C , Y grade
Gain Error Temperature Coefficient 1 ppm of FSR/°C
Offset Error ±0.02 ±3.0 mV TA = −40°C to + 85°C, B grade
±0.02 ±3.0 TA = −40°C to + 125°C, Y grade
Offset Error Temperature Coefficient 0.5 µV/°C
Full-Scale Error ±0.05 ±3.0 mV
±0.05 ±3.0
OUTPUT CHARACTERISTICS3
Output Voltage Range 0 V
Output Voltage Settling Time 4 µs
Output Noise Spectral Density 64
Output Voltage Noise 6 µV p-p DAC code = midscale , 0.1 Hz to 10 Hz bandwidth
Digital-to-Analog Glitch Impulse 2 nV-s 1 LSB change around major carry, RL = 5 KΩ
Digital Feedthrough 0.003 nV-s DAC code = full-scale
DC Output Impedance (Normal) 0.015 Ω Output impedance tolerance ±10%
DC Output Impedance (Power-Down)
DC Power Supply Rejection Ratio −92 dB VDD ±10%, DAC code = full-scale
Wideband Spurious-Free Dynamic Range −67 dB Output frequency = 10 kHz
REFERENCE INPUT/OUTPUT
V
Input Range4 2 V
REF
Input Current (Power-Down) ±0.1 µA Zero-scale loaded
Input Current (Normal) ±0.5 µA
DC Input Impedance 1 MΩ
= 4.096 V, RL = unloaded, CL= unloaded, T
REF
MIN
to T
, unless otherwise specified.
MAX
V
REF
nV/√Hz
− 50 mV
DD
Guaranteed monotonic, −40°C to +125°C,
Y grade
All 1s loaded to DAC register,
TA = −40°C to +85°C, B grade
All 1s loaded to DAC register,
= −40°C to +125°C , Y grade
T
A
¼ scale to ¾ scale code transition to ±1LSB,
= 5 KΩ
R
L
DAC code = midscale, 1 kHz
¼ scale to ¾ scale code transition to ±1 LSB,
R
= 5 kΩ, CL = 200 pF
L
DAC code = full-scale, output shorted to GND,
= 25°C
T
A
DAC code = zero-scale, output shorted to V
= 25°C
T
A
Time to exit power-down mode to normal
mode of AD5061, 24
th
clock edge to 90% of
DD
DAC final value, output unloaded
,
Rev. B | Page 3 of 20
Page 4
AD5061
B Grade1
Parameter Min Typ Max Unit Test Conditions/Comments
LOGIC INPUTS
Input Current5 ±1 ±5 μA
Input Low Voltage (VIL) 0.8 V VDD = 4.5 V to 5.5 V
0.8 VDD = 2.7 V to 3.6 V
Input High Voltage (VIH) 2.0 V VDD = 2.7 V to 5.5 V
1.8 VDD = 2.7 V to 3.6 V
Pin Capacitance 4 pF
POWER REQUIREMENTS
VDD 2.7 5.5 V All digital inputs at 0 V or VDD
IDD (Normal Mode) DAC active and excluding load current
VDD = 2.7 V to 5.5 V 1.0 1.2 mA
0.89
IDD (All Power-Down Modes)
VDD = 2.5 V to 5.5 V 1 μA
0.265
1
Temperature range for B grade: −40°C to +85°C, typical at 25°C; temperature range for Y grade: −40°C to +125°C.
2
Linearity calculated using a reduced code range (160 to 65535).
3
Guaranteed by design and characterization, not production tested.
4
The typical output supply headroom performance for various reference voltages at −40°C can be seen in Figure 27.
5
Total current flowing into all pins.
= VDD and VIL = GND, VDD = 5.5 V,
V
IN
V
= 4.096 V, code = midscale
REF
= VDD and VIL = GND, VDD = 3.0 V,
V
IN
= 4.096 V, code = midscale
V
REF
= VDD and VIL = GND, VDD = 5.5 V,
V
IH
= 4.096 V, code = midscale
V
REF
= VDD and VIL = GND, VDD = 3.0 V,
V
IH
V
= 4.096 V, code = midscale
REF
Rev. B | Page 4 of 20
Page 5
AD5061
TIMING CHARACTERISTICS
VDD = 2.7 V to 5.5 V, all specifications T
Table 3.
Parameter Limit1 Unit Test Conditions/Comments
2
t
33 ns min SCLK cycle time
1
t2
t
3
t
4
t5
t
6
t
7
t8
t9
1
All input signals are specified with tr = tf = 1 ns/V (10% to 90% of VDD) and timed from a voltage level of (VIL + VIH)/2.
2
Maximum SCLK frequency is 30 MHz.
5 ns min
3 ns min
10 ns min
3 ns min
2 ns min
0 ns min
12 ns min
9 ns min
SCLK
SYNC
DIN
t
8
MIN
to T
unless otherwise specified.
MAX
,
SCLK high time
SCLK low time
SYNC to SCLK falling edge set-up time
Data set-up time
Data hold time
SCLK falling edge to SYNC rising edge
Minimum SYNC high time
SYNC rising edge to next SCLK fall ignore
t
4
t
t
2
1
t
3
t
6
t
5
t
9
t
7
D0D1D2D22D23
D23D22
04762-002
Figure 2. Timing Diagram
Rev. B | Page 5 of 20
Page 6
AD5061
ABSOLUTE MAXIMUM RATINGS
Table 4.
Parameter Rating
VDD to GND −0.3 V to +7.0 V
Digital Input Voltage to GND −0.3 V to VDD + 0.3 V
V
to GND −0.3 V to VDD + 0.3 V
OUT
V
to GND −0.3 V to VDD + 0.3 V
REF
Operating Temperature Range
Industrial (B Grade) −40°C to + 85°C
Extended Automotive Temperature
Range (Y Grade) −40°C to +125°C
Storage Temperature Range −65°C to +150°C
Maximum Junction Temperature 150°C
SOT-23 Package
Power Dissipation (TJ max − TA)/θJA
θJA Thermal Impedance 206°C/W
θJC Thermal Impedance 44°C/W
Reflow Soldering (Pb-Free)
Peak Temperature 260°C
Time-at-Peak Temperature 10 sec to 40 sec
ESD 1.5 kV
Stresses above those listed under Absolute Maximum Ratings
may cause permanent damage to the device. This is a stress
rating only; functional operation of the device at these or any
other conditions above those indicated in the operational
section of this specification is not implied. Exposure to absolute
maximum rating conditions for extended periods may affect
device reliability.
This device is a high performance integrated circuit with an
ESD rating of <2 kV, and is ESD-sensitive. Proper precautions
should be taken for handling and assembly.
ESD CAUTION
ESD (electrostatic discharge) sensitive device. Electrostatic charges as high as 4000 V readily accumulate on
the human body and test equipment and can discharge without detection. Although this product features
proprietary ESD protection circuitry, permanent damage may occur on devices subjected to high energy
electrostatic discharges. Therefore, proper ESD precautions are recommended to avoid performance
degradation or loss of functionality.
Rev. B | Page 6 of 20
Page 7
AD5061
V
PIN CONFIGURATION AND FUNCTION DESCRIPTIONS
18
Table 5. Pin Function Descriptions
Pin No. Mnemonic Description
1 DIN
Serial Data Input. This device has a 24-bit shift register. Data is clocked into the register on the falling edge of the
serial clock input.
2
3 V
4 V
5 AGND
6 DACGND
7
Power Supply Input. These parts can be operated from 2.7 V to 5.5 V and VDD should be decoupled to GND.
V
DD
Reference Voltage Input.
REF
Analog Output Voltage from DAC.
OUT
Ground Reference Point for Analog Circuitry.
Ground Input to the DAC.
SYNC Level-Triggered Control Input (Active Low). This is the frame synchronization signal for the input data. When SYNC
goes low, it enables the input shift register and data is transferred in on the falling edges of the following clocks.
The DAC is updated following the 24th clock cycle unless SYNC is taken high before this edge, in which case the
rising edge of SYNC
8 SCLK
Serial Clock Input. Data is clocked into the input shift register on the falling edge of the serial clock input. Data can
be transferred at rates up to 30 MHz.
DIN
V
V
REF
OUT
AD5061
27
TOP VIEW
DD
(Not to Scale)
36
45
Figure 3. Pin Configuration
acts as an interrupt and the write sequence is ignored by the DAC.
SCLK
SYNC
DACGND
AGND
04762-003
Rev. B | Page 7 of 20
Page 8
AD5061
TYPICAL PERFORMANCE CHARACTERISTICS
1.6
TA = 25°C
1.4
= 5V, V
V
DD
1.2
1.0
0.8
0.6
0.4
0.2
0
–0.2
–0.4
INL ERRO R (LSB)
–0.6
–0.8
–1.0
–1.2
–1.4
–1.6
160
= 4.096V
REF
DAC CODE
Figure 4. Typical INL Plot
601605016040160301602016010160
04762-004
1.2
VDD = 5.5V, V
1.0
= 2.7V, V
V
DD
0.8
0.6
MAX DNL ERROR @ V
0.4
0.2
0
–0.2
–0.4
DNL ERROR (LSB)
–0.6
–0.8
MIN DNL ERROR @ VDD = 5.5V
–1.0
–1.2
–40 –20020406080100120
= 4.096V
REF
= 2.0V
REF
= 2.7V
DD
MAX DNL E RROR @ VDD = 5.5V
MIN DNL ERROR @ VDD = 2.7V
TEMPERATURE (°C)
Figure 7. DNL vs. Temperature
04762-007
140
TUE ERROR (mV)
DNL ERROR (LSB)
0.16
0.14
0.12
0.10
0.08
0.06
0.04
0.02
–0.02
–0.04
–0.06
–0.08
–0.10
–0.12
–0.14
–0.16
1.6
1.4
1.2
1.0
0.8
0.6
0.4
0.2
–0.2
–0.4
–0.6
–0.8
–1.0
–1.2
–1.4
–1.6
TA = 25°C
V
0
160
TA = 25°C
V
0
160
DD
DD
= 5V, V
REF
= 4.096V
Figure 5. Typical TUE Plot
= 5V, V
REF
= 4.096V
Figure 6. Typical DNL Plot
DAC CODE
DAC CODE
1.2
VDD = 5.5V, V
1.0
= 2.7V, V
V
DD
0.8
0.6
0.4
0.2
MIN TUE ERROR @ VDD = 5.5V
0
–0.2
TUE ERROR (mV)
–0.4
–0.6
–0.8
–1.0
601605016040160301602016010160
04762-005
–1.2
–40 –20020406080100120
= 4.096V
REF
= 2.0V
REF
MAX TUE ERROR @ V
MIN TUE ERROR @ VDD = 2.7V
TEMPERATURE (°C)
= 2.7V
DD
MAX TUE ERROR @ VDD = 5.5V
04762-008
140
Figure 8. TUE vs. Temperature
1.6
VDD = 5.5V, V
1.4
= 2.7V, V
V
DD
1.2
1.0
0.8
0.6
0.4
0.2
0
–0.2
–0.4
INL ERRO R (LSB)
–0.6
–0.8
–1.0
–1.2
601605016040160301602016010160
04762-006
–1.4
–1.6
MIN INL ERROR @ VDD = 5.5V
–40 –20020406080100120
= 4.096V
REF
= 2.0V
REF
MAX INL ERROR @ V
MAX INL ERROR @ VDD = 5.5V
MIN INL ERROR @ VDD = 2.7V
TEMPERATURE (°C)
DD
= 2.7V
04762-090
140
Figure 9. INL vs. Temperature
Rev. B | Page 8 of 20
Page 9
AD5061
1.6
TA = 25°C
1.4
1.2
1.0
0.8
0.6
0.4
0.2
0
–0.2
–0.4
DNL ERROR (LSB)
–0.6
–0.8
–1.0
–1.2
–1.4
–1.6
2.0
MAX DNL E RROR @ VDD = 5.5V
MIN DNL E RROR @ VDD = 5.5V
REFERENCE VO LTAGE (V)
04762-010
5.55.04.54.03.53.02.5
Figure 10. DNL vs. Reference Input Voltage
1.5
VDD = 5.5V, V
1.4
V
1.3
CODE = FULL -SCALE
1.2
1.1
1.0
0.9
0.8
0.7
0.6
0.5
SUPPLY CURRENT (mA)
0.4
0.3
0.2
0.1
0
–40
= 2.7V, V
DD
= 2.0V
REF
TEMPERATURE (°C)
VDD = 5.5V
= 2.7V
V
DD
= 4.096V
REF
Figure 13. Supply Current vs. Temperature
04762-013
140120100806040200–20
1.2
TA = 25°C
1.0
0.8
0.6
0.4
0.2
0
–0.2
TUE ERROR (mV)
–0.4
–0.6
–0.8
–1.0
–1.2
2.0
MAX TUE ERROR @ VDD = 5.5V
MIN TUE ERROR @ VDD = 5.5V
REFERENCE VO LTAGE (V)
04762-011
5.55.04.54.03.53.02.5
Figure 11. TUE vs. Reference Input Voltage
1.6
TA = 25°C
1.4
1.2
1.0
0.8
0.6
0.4
0.2
0
–0.2
–0.4
INL ERRO R (LSB)
–0.6
–0.8
–1.0
–1.2
–1.4
–1.6
2.0
MAX INL ERROR @ VDD = 5.5V
MIN INL E RROR @ VDD = 5.5V
REFERENCE VO LTAGE (V)
04762-009
5.55.04.54.03.53.02.5
Figure 12. INL vs. Reference Input Voltage
3.00
TA = 25°C
2.75
2.50
2.25
2.00
1.75
1.50
1.25
1.00
SUPPLY CURRENT (mA)
0.75
0.50
0.25
0
0
VDD = 5.5V, V
VDD = 3.0V, V
DAC CODE
Figure 14. Supply Current vs. Digital Input Code
2.0
V
= 2.5V
REF
1.8
= 25°C
T
A
CODE = MIDSCALE
1.6
1.4
1.2
1.0
0.8
0.6
SUPPLY CURRENT (mA)
0.4
0.2
0
2.5
SUPPLY VOLTAGE (V)
Figure 15. Supply Current vs. Supply Voltage
REF
REF
= 4.096V
= 2.5V
04762-014
70000600005000040000300002000010000
04762-015
6.05.55.04.54.03.53.0
Rev. B | Page 9 of 20
Page 10
AD5061
1.8
1.6
1.4
1.2
1.0
0.8
0.6
0.4
0.2
OFFSET ERROR (mV)
0
–0.2
–0.4
–0.6
–40
VDD = 5.5V, V
= 2.7V, V
V
DD
OFFSET ERROR @ VDD = 5.5V
= 4.096V
REF
= 2.0V
REF
OFFSET ERROR @ V
TEMPERATURE (°C)
Figure 16. Offset vs. Temperature
DD
= 2.7V
CH3 = SCLK
CH2 = V
OUT
CH1 = TRIGG ER
04762-012
140120100806040200–20
CH2 2V/DIVCH1 2V/DIVTIME BASE = 5.00µsCH3 2V
04762-019
Figure 19. Exiting Power-Down Time to Midscale
24TH CLOCK FALLI NG
CH1 = SCLK
CH2 = V
OUT
CH2 50mV/DIV CH1 2V/DIVTIME BASE 400ns/ DIV
Figure 17. Digital-to-Analog Glitch Impulse; See Figure 21
Figure 31. Typical Glitch upon Exiting Software Power-Down to Zero-Scale
C2
25mV p-p
4.995
4.990
DAC OUTPUT (V)
4.985
4.980
4.975
5.505.005.055.105.155.205.255.305.355.405. 45
VDD (V)
04762-065
Figure 29. Typical Output Voltage vs. Supply Voltage
C4 = 143mV p-p
1kΩ TO GNDZERO-SCALE
CH4 50.0mVM4.00µsCH1 1.64V
04762-047
Figure 30. Typical Glitch upon Entering Software Power-Down to Zero-Scale
2
3
CH3 2.00V CH2 50mVM1.00msCH3 1.36V
T
T
C3
4.96V p-p
C3 FALL
935.0µs
C3 RISE
∞s
NO VALID
EDGE
04762-049
Figure 32. Typical Glitch upon Exiting Hardware Power-Down to Three State
C2
30mV p-p
2
3
CH3 2.00V CH2 50mVM1.00msCH3 1.36V
T
T
C3
4.96V p-p
C3 FALL
∞s
NO VALID
EDGE
C3 RISE
946.2µs
04762-050
Figure 33. Typical Glitch upon Entering Hardware Power-Down to Zero-Scale
Rev. B | Page 12 of 20
Page 13
AD5061
0.0010
CODE = MIDSCAL E
= 5V, V
V
0.0008
DD
= 3V, V
V
DD
0.0006
0.0004
0.0002
0
∆ VOLTAGE (V)
–0.0002
VDD = 5.5V
–0.0004
–0.0006
–0.0008
–25 –20 –15 –10 –50510 15 20 25 30
= 4.096V
REF
= 2.5V
REF
VDD = 3V
CURRENT (mA)
Figure 34. Typical Output Load Regulation
04762-051
2.1
VDD = 5.5V
V
= 4.096V
2.0
REF
10% TO 90% RISE TIME = 0.688µs
SLEW RATE = 1.16 V/µs
1.9
1.8
1.7
1.6
1.5
1.4
1.3
1.2
1.1
1.0
–10µs9.96µs8µs6µs4µs2µs0–2µs–4µs–6µ s–8µs
Figure 36. Typical Output Slew Rate
DAC
OUTPUT
1.04V
2.04V
04762-052
0.10
CODE = MIDSCAL E
= 5V, V
V
0.08
DD
= 3V, V
V
DD
0.06
0.04
0.02
(V)
0
OUT
∆ V
–0.02
–0.04
–0.06
–0.08
–0.10
–25 –20 –15 –10 –50510 15 20 25 30
= 4.096V
REF
= 2.5V
REF
VDD = 5V, V
REF
= 4.096V
I
OUT
VDD = 3V, V
(mA)
REF
= 2.5V
04762-063
Figure 35. Typical Current Limiting Plot
Rev. B | Page 13 of 20
Page 14
AD5061
TERMINOLOGY
Relative Accuracy
For the DAC, relative accuracy or integral nonlinearity (INL) is
a measure of the maximum deviation, in LSBs, from a straight
line passing through the endpoints of the DAC transfer
function. A typical INL vs. code plot is shown in Figure 4.
Differential Nonlinearity (DNL)
Differential nonlinearity is the difference between the measured
change and the ideal 1 LSB change between any two adjacent codes.
A specified differential nonlinearity of ±1 LSB maximum ensures
monotonicity. This DAC is guaranteed monotonic by design. A
typical AD5061 DNL vs. code plot is shown in Figure 6.
Zero-Code Error
Zero-code error is a measure of the output error when zero
code (0x0000) is loaded to the DAC register. Ideally, the output
should be 0 V. The zero-code error is always positive in the
AD5061 because the output of the DAC cannot go below 0 V.
This is due to a combination of the offset errors in the DAC and
output amplifier. Zero-code error is expressed in mV.
Full-Scale Error
Full-scale error is a measure of the output error when full-scale
code (0xFFFF) is loaded to the DAC register. Ideally, the output
should be V
of full-scale range.
Gain Error
This is a measure of the span error of the DAC. It is the deviation in slope of the DAC transfer characteristic from ideal
expressed as a percent of the full-scale range.
− 1 LSB. Full-scale error is expressed in percent
DD
Tot a l Un a dj us t ed Er ro r (T UE )
Total unadjusted error is a measure of the output error taking
all the various errors into account. A typical TUE vs. code plot
is shown in Figure 5.
Zero-Code Error Drift
This is a measure of the change in zero-code error with a
change in temperature. It is expressed in μV/°C.
Gain Error Drift
This is a measure of the change in gain error with changes in
temperature. It is expressed in (ppm of full-scale range)/°C.
Digital-to-Analog Glitch Impulse
Digital-to-analog glitch impulse is the impulse injected into the
analog output when the input code in the DAC register changes
state. It is normally specified as the area of the glitch in nV-s
and is measured when the digital input code is changed by
1 LSB at the major carry transition; see Figure 17 and Figure 21.
The expanded view in Figure 17 shows the glitch generated
following completion of the calibration routine; Figure 21
zooms in on this glitch.
Digital Feedthrough
Digital feedthrough is a measure of the impulse injected into
the analog output of the DAC from the digital inputs of the
DAC, but is measured when the DAC output is not updated. It
is specified in nV-s and measured with a full-scale code change
on the data bus; that is, from all 0s to all 1s, and vice versa.
Rev. B | Page 14 of 20
Page 15
AD5061
V
THEORY OF OPERATION
The AD5061 is a single 16-bit, serial input, voltage output DAC.
It operates from supply voltages of 2.7 V to 5.5 V. Data is written to the AD5061 in a 24-bit word format, via a 3-wire serial
interface.
The AD5061 incorporates a power-on reset circuit that ensures
the DAC output powers up to zero-scale or midscale. The
device also has a software power-down mode pin that reduces
the typical current consumption to less than 1 μA.
DAC ARCHITECTURE
The DAC architecture of the AD5061 consists of two matched
DAC sections. A simplified circuit diagram is shown in
Figure 37. The four MSBs of the 16-bit data word are decoded
to drive 15 switches, E1 to E15. Each of these switches connects
one of 15 matched resistors to either DACGND or V
output.
The remaining 12 bits of the data word drive switches
buffer
REF
S0 to S11 of a 12-bit voltage mode R-2R ladder network.
OUT
2R
2R
2R
2R
S1
S0
V
REF
12-BIT R-2R L ADDERFOUR MSBs DECODED INTO
Figure 37. DAC Ladder Structure
2R
2R
E1
S11
15 EQUAL SEGMENTS
E2
2R
E15
REFERENCE BUFFER
The AD5061 operates with an external reference. The reference
input (V
) has an input range of 2 V to VDD − 50 mV. This
REF
input voltage is then used to provide a buffered reference for the
DAC core.
SERIAL INTERFACE
The AD5061 has a 3-wire serial interface (
DIN), which is compatible with SPI, QSPI, and MICROWIRE
interface standards, as well as most DSPs. See for a
timing diagram of a typical write sequence.
SYNC
, SCLK, and
Figure 2
DB15 (MSB)DB0 (LSB)
The write sequence begins by bringing the
from the DIN line is clocked into the 24-bit shift register on the
falling edge of SCLK. The serial clock frequency can be as high
as 30 MHz, making these parts compatible with high speed
DSPs. On the 24th falling clock edge, the last data bit is clocked
in and the programmed function is executed (that is, a change
in the DAC register contents and/or a change in the mode of
operation).
At this stage, the
SYNC
line may be kept low or be brought
high. In either case, it must be brought high for a minimum of
12 ns before the next write sequence so that a falling edge of
SYNC
can initiate the next write sequence. Because the
buffer draws more current when V
V
= 0.8 V,
IH
should be idled low between write sequences
SYNC
IH
for an even lower power operation of the part. As previously
indicated, however, it must be brought high again just before
the next write sequence.
INPUT SHIFT REGISTER
The input shift register is 24 bits wide; see Figure 38. PD1 and
PD0 are control bits that control which mode of operation the
part is in (normal mode or any one of three power-down
modes). There is a more complete description of the various
047762-027
modes in the Power-Down Modes section. The next 16 bits are
the data bits. These are transferred to the DAC register on the
24th falling edge of SCLK.
SYNC INTERRUPT
In a normal write sequence, the
least 24 falling edges of SCLK and the DAC is updated on the
24th falling edge. However, if
24th falling edge, this acts as an interrupt to the write sequence.
The shift register is reset and the write sequence is seen as
invalid. Neither an update of the DAC register contents nor a
change in the operating mode occurs; see . Figure 41
SYNC
SYNC
SYNC
line low. Data
SYNC
= 1.8 V than it does when
line is kept low for at
is brought high before the
0000 00PD1PD0
D15D14D13D12D11D10D9D8D7D6D5D4D3D2D1D0
DATA BITS
0
0
1
1
NORMAL O PERATION
0
3-STATE
1
100kΩ TO GND
0
1
1kΩ TO GND
Figure 38. Input Register Contents
Rev. B | Page 15 of 20
POWER-DOW N MODES
04762-028
Page 16
AD5061
POWER-ON TO ZERO-SCALE OR MIDSCALE
The AD5061 contains a power-on reset circuit that controls the
output voltage during power-up. The DAC register is filled with
the zero-scale or midscale code and the output voltage is zeroscale or midscale. It remains there until a valid write sequence is
made to the DAC. This is useful in applications where it is
important to know the state of the output of the DAC while it is
in the process of powering up.
SOFTWARE RESET
The device can be put into software reset by setting all bits in
the DAC register to 1; this includes writing 1s to Bit D23 to
Bit D16, which is not the normal mode of operation. Note that
the
interrupt command cannot be performed if a
SYNC
software reset command is started.
POWER-DOWN MODES
The AD5061 contains four separate modes of operation. These
modes are software-programmable by setting two bits (DB17
and DB16) in the control register. Table 6 shows how the state
of the bits corresponds to the mode of operation of the device.
Table 6. Modes of Operation
DB17 DB16 Operating Mode
0 0 Normal operation
Power-down mode:
0 1 3-state
1 0 100 kΩ to GND
1 1 1 kΩ to GND
When both bits are set to 0, the part works normally with its
normal power consumption. However, for the three powerdown modes, the supply current falls to less than 1 A at 5 V
(265 nA at 3 V). Not only does the supply current fall, but the
output stage is also internally switched from the output of the
amplifier to a resistor network of known values. This has the
advantage that the output impedance of the part is known while
the part is in power-down mode. There are three different
options. The output is connected internally to GND through a
1 kΩ resistor or a 100 kΩ resistor, or it is left open-circuited
(3-state). The output stage is illustrated in Figure 39.
OUTPUT
AD5061
DAC
Figure 39. Output Stage During Power-Down
BUFFER
POWER-DOWN
CIRCUITRY
RESISTOR
NETWORK
V
OUT
04762-029
The bias generator, the DAC core and other associated linear
circuitry are all shut down when the power-down mode is
activated. However, the contents of the DAC register are
unaffected when in power-down. The time to exit power-down
is typically 2.5 µs for V
= 5 V, and 5 µs for VDD = 3 V;
DD
see Figure 19.
MICROPROCESSOR INTERFACING
AD5061-to-ADSP-2101/ADSP-2103 Interface
Figure 40 shows a serial interface between the AD5061 and the
ADSP-2101/ADSP-2103. The ADSP-2101/ADSP-2103 should
be set up to operate in the SPORT transmit alternate framing
mode. The ADSP-2101/ADSP-2103 SPORT is programmed
through the SPORT control register and should be configured
as follows: internal clock operation, active low framing, 16-bit
word length. Transmission is initiated by writing a word to the
Tx register after the SPORT has been enabled.
Figure 42 shows a serial interface between the AD5061 and the
68HC11/68L11 microcontroller. SCK of the 68HC11/68L11
drives the SCLK pin of the AD5061, while the MOSI output
drives the serial data line of the DAC. The
SYNC
signal is
derived from a port line (PC7). The set-up conditions for
correct operation of this interface require that the 68HC11/
68L11 be configured so that its CPOL bit is 0 and its CPHA bit
is 1. When data is being transmitted to the DAC, the
SYNC
line
is taken low (PC7). When the 68HC11/68L11 is configured
where its CPOL bit is 0 and its CPHA bit is 1, data appearing on
the MOSI output is valid on the falling edge of SCK. Serial data
from the 68HC11/68L11 is transmitted in 8-bit bytes with only
eight falling clock edges occurring in the transmit cycle. Data is
transmitted MSB first. To load data to the AD5061, PC7 is left
low after the first eight bits are transferred, a second serial write
operation is performed to the DAC, and PC7 is taken high at
the end of this procedure.
AD5061-to-80C51/80L51 Interface
Figure 44 shows a serial interface between the AD5061 and the
80C51/80L51 microcontroller. The setup for the interface is:
TxD of the 80C51/80L51 drives SCLK of the AD5061 while
RxD drives the serial data line of the part. The
SYNC
signal is
again derived from a bit-programmable pin on the port. In this
case, Port Line P3.3 is used. When data is to be transmitted to
the AD5061, P3.3 is taken low. The 80C51/80L51 transmits data
only in 8-bit bytes; thus only eight falling clock edges occur in
the transmit cycle. To load data to the DAC, P3.3 is left low after
the first eight bits are transmitted, and a second write cycle is
initiated to transmit the second byte of data. P3.3 is taken high
following the completion of this cycle. The 80C51/80L51 outputs the serial data in a format that has the LSB first. The
AD5061 requires its data with the MSB as the first bit received.
The 80C51/80L51 transmit routine should take this into account.
80C51/80L51
1
AD5061
1
68HC11/
1
68L11
PC7
SCK
MOSI
1
ADDITIONAL PI NS OMITTED FOR CLARI TY
SYNC
SCLK
DIN
AD5061
1
Figure 42. AD5061-to-68HC11/68L11 Interface
AD5061-to-Blackfin® ADSP-BF53x Interface
Figure 43 shows a serial interface between the AD5061 and the
Blackfin ADSP-53x microprocessor. The ADSP-BF53x processor family incorporates two dual-channel synchronous serial
ports, SPORT1 and SPORT0, for serial and multiprocessor
communications. Using SPORT0 to connect to the AD5061,
the setup for the interface is: DT0PRI drives the DIN pin of
the AD5061, while TSCLK0 drives the SCLK of the part; the
SYNC
Figure 45 shows an interface between the AD5061 and any
MICROWIRE-compatible device. Serial data is shifted out on
the falling edge of the serial clock and is clocked into the
AD5061 on the rising edge of the SK.
MICROWIRE
1
ADDITIONAL PI NS OMITTED FOR CLARI TY
1
CS
SK
SO
Figure 45. AD5061-to-MICROWIRE Interface
AD5061
SYNC
SCLK
DIN
1
04762-035
04762-033
Rev. B | Page 17 of 20
Page 18
AD5061
Ω
APPLICATIONS
CHOOSING A REFERENCE
To achieve the optimum performance from the AD5061,
thought should be given to the choice of a precision voltage
reference. The AD5061 has just one reference input, V
voltage on the reference input is used to supply the positive
input to the DAC. Therefore, any error in the reference is
reflected in the DAC.
There are four possible sources of error when choosing a voltage reference for high accuracy applications: initial accuracy,
ppm drift, long-term drift, and output voltage noise. Initial
accuracy on the output voltage of the DAC leads to a full-scale
error in the DAC. To minimize these errors, a reference with
high initial accuracy is preferred. Also, choosing a reference
with an output trim adjustment, such as the ADR43x family,
allows a system designer to trim out system errors by setting a
reference voltage to a voltage other than the nominal. The trim
adjustment can also be used at the operating temperature to
trim out any errors.
REF
. The
Table 7 shows examples of recommended precision references
for use as a supply to the AD5061.
Table 7. Precision References Part List for the AD5061
The AD5061 has been designed for single-supply operation, but
a bipolar output range is also possible using the circuit shown in
Figure 47. The circuit shown yields an output voltage range of
±5 V. Rail-to-rail operation at the amplifier output is achievable
using an AD8675/AD820/AD8032 or an OP196/OP295.
Because the supply current required by the AD5061 is
extremely low, the parts are ideal for low supply applications.
The ADR395 voltage reference is recommended. This requires
less than 100 μA of quiescent current and can, therefore, drive
multiple DACs in one system, if required. It also provides very
good noise performance at 8 μV p-p in the 0.1 Hz to 10 Hz range.
7V
5V
AD5061
V
OUT
= 0V TO 5V
3-WIRE
SERIAL
INTERFACE
ADR395
SYNC
SCLK
DIN
Figure 46. ADR395 as Reference to the AD5061
Long-term drift is a measure of how much the reference drifts
over time. A reference with a tight long-term drift specification
ensures that the overall solution remains relatively stable during
its entire lifetime. The temperature coefficient of a reference’s
output voltage affects INL, DNL, and TUE. A reference with a
tight temperature coefficient specification should be chosen to
reduce temperature dependence of the DAC output voltage on
ambient conditions.
In high accuracy applications, which have a relatively low noise
budget, reference output voltage noise needs to be considered. It
is important to choose a reference with as low an output noise
voltage as practical for the system noise resolution required.
Precision voltage references, such as the ADR435, produce low
output noise in the 0.1 Hz to 10 Hz region.
The output voltage for any input code can be calculated as
follows:
+
⎡
⎛
×=
VV
O
⎜
⎢
⎝
⎣
65536
⎞
×
⎟
⎠
2R1RD
⎛
⎜
⎝
⎞
V
⎟
1R
⎠
2R
⎤
⎞
⎛
×−
DDDD
⎟
⎜
⎥
1R
⎠
⎝
⎦
where D represents the input code in decimal (0 to 65536).
With V
= 5 V, R1 = R2 = 10 kΩ,
REF
10
×=D
65536
⎞
−
⎟
⎠
⎛
V
⎜
O
⎝
V5
This is an output voltage range of ±5 V with 0x0000 corresponding to a −5 V output and 0xFFFF corresponding to a +5 V output.
04762-036
+5V
10µF
0.1µF
Figure 47. Bipolar Operation with the AD5061
R1 = 10kΩ
V
REF
AD5061
3-WIRE
SERIAL
INTERFACE
V
BF
V
OUT
R2 = 10k
–
AD820/
OP295
+
+5V
–5V
±5V
04762-037
Rev. B | Page 18 of 20
Page 19
AD5061
USING A GALVANICALLY-ISOLATED INTERFACE
CHIP
In process control applications in industrial environments, it is
often necessary to use a galvanically-isolated interface to protect
and isolate the controlling circuitry from any hazardous
common-mode voltages that may occur in the area where the
DAC is functioning. iCoupler
2.5 kV. Because the AD5061 uses a 3-wire serial logic interface,
the ADuM130x family provides an ideal digital solution for the
DAC interface.
The ADuM130x isolators provide three independent isolation
channels in a variety of channel configurations and data rates.
They operate across the full range from 2.7 V to 5.5 V, providing
compatibility with lower voltage systems and enabling a voltage
translation functionality across the isolation barrier.
Figure 48 shows a typical galvanically-isolated configuration
using the AD5061. The power supply to the part also needs to
be isolated; this is accomplished by using a transformer. On the
DAC side of the transformer, a 5 V regulator provides the 5 V
supply required for the AD5061.
POWER
ADuM130x
® provides isolation in excess of
5V
REGULATOR
SCLKV0AV1ASCLK
SYNCV0BV1BSDI
V
DD
AD5061
V
OUT
0.1µF10µ F
POWER SUPPLY BYPASSING AND GROUNDING
When accuracy is important in a circuit, it is helpful to carefully
consider the power supply and ground return layout on the
board. The printed circuit board containing the AD5061 should
have separate analog and digital sections, each having its own
area of the board. If the AD5061 is in a system where other
devices require an AGND-to-DGND connection, then the
connection should be made at one point only. This ground
point should be as close as possible to the AD5061.
The power supply to the AD5061 should be bypassed with
10 μF and 0.1 μF capacitors. The capacitors should be physically
as close as possible to the device with the 0.1 μF capacitor
ideally right up against the device. The 10 μF capacitors are the
tantalum bead type. It is important that the 0.1 μF capacitor has
low effective series resistance (ESR) and effective series
inductance (ESI), as do common ceramic types of capacitors.
This 0.1 μF capacitor provides a low impedance path to ground
for high frequencies caused by transient currents due to internal
logic switching.
The power supply line itself should have as large a trace as
possible to provide a low impedance path and reduce glitch
effects on the supply line. Clocks and other fast switching
digital signals should be shielded from other parts of the board
by digital ground. Avoid crossover of digital and analog signals,
if possible. When traces cross on opposite sides of the board,
ensure that they run at right angles to each other to reduce
feedthrough effects through the board. The best board layout
technique is the microstrip technique where the component
side of the board is dedicated to the ground plane only, and the
signal traces are placed on the solder side. However, this is not
always possible with a 2-layer board.
DINV0CV1CDATA
GND
Figure 48. AD5061 with a Galvanically-Isolated Interface
04762-038
Rev. B | Page 19 of 20
Page 20
AD5061
0
0
OUTLINE DIMENSIONS
INDICATOR
.15 MAX
.05 MIN
1.70
1.60
1.50
1.30
1.15
0.90
PIN 1
3.00
2.90
2.80
76
8
1234
1.95
BSC
5
0.38 MAX
0.22 MIN
0.65 BSC
1.45 MAX
0.95 MIN
3.00
2.80
2.60
SEATING
PLANE
0.22 MAX
0.08 MIN
8°
0.60
4°
BSC
0°
0.60
0.45
0.30
COMPLIANT TO JEDEC STANDARDS MO-178-BA
12-16-2008-A
Figure 49. 8-Lead Small Outline Transistor Package [SOT-23]
(RJ-8)
Dimensions shown in millimeters
ORDERING GUIDE
Temperature
Model1
AD5061BRJZ-1REEL7
Range INL Description
−40°C to +85°C 4 LSB 2.7 V to 5.5 V, Reset to 0 V 8-Lead SOT-23 RJ-8 D43
AD5061BRJZ-1500RL7 −40°C to +85°C 4 LSB 2.7 V to 5.5 V, Reset to 0 V 8-Lead SOT-23 RJ-8 D43
AD5061BRJZ-2REEL7
−40°C to +85°C 4 LSB 2.7 V to 5.5 V, Reset to Midscale 8-Lead SOT-23 RJ-8 D44
AD5061BRJZ-2500RL7 −40°C to +85°C 4 LSB 2.7 V to 5.5 V, Reset to Midscale 8-Lead SOT-23 RJ-8 D44
AD5061YRJZ-1500RL7 −40°C to +125°C 4 LSB 2.7 V to 5.5 V, Reset to 0 V 8-Lead SOT-23 RJ-8 D6G
AD5061YRJZ-1REEL7 −40°C to +125°C 4 LSB 2.7 V to 5.5 V, Reset to 0 V 8-Lead SOT-23 RJ-8 D6G
EVAL-AD5061EBZ