Antijam GPS receivers
Wireless and wired broadband communications
Communications test equipment
OTR_A
PDWN
OEB_A
PDWNB
OEB_B
OTR_B
FUNCTIONAL BLOCK DIAGRAM
CLKA
INA
DFS
CLKB
INB
LPF
LPF
Figure 1.
AD15252
AD15252
DATA
BUS A
DATA
BUS B
05154-001
GENERAL DESCRIPTION
The AD15252 is a dual, 12-bit, 65 MSPS, analog-to-digital
converter (ADC). It features a differential front-end
amplification circuit followed by a sample-and-hold amplifier
and multistage pipeline ADC. It is designed to operate with a
3.3 V analog supply and a 2.5 V/3.3 V digital supply. Each input
is fully differential, ac-coupled, and terminated in 100 Ω input
impedances. The full-scale differential signal input range is
296 mV p-p.
Two parallel, 12-bit digital output buses provide data flow from
t
he ADCs. The digital output data is presented in either straight
binary or twos complement format. Out-of-range (OTR) signals
indicate an overflow condition, which can be used with the
most significant bit to determine low or high overflow. Dual
single-ended clock inputs control all internal conversion cycles.
A duty cycle stabilizer allows wide variations in the clock duty
cycle while maintaining excellent performance. The AD15252 is
optimized for applications in antijam global positioning
receivers and is well suited for communications applications.
PRODUCT HIGHLIGHTS
1. Dual 12-bit, 65 MSPS ADC with integrated analog signal
conditioning optimized for antijam global positioning
system receiver (AJ-GPS) applications.
perates from a single 3.3 V power supply and features a
2. O
separate digital output driver supply to accommodate 2.5 V
and 3.3 V logic families.
ackaged in a space-saving 8 mm × 8 mm chip scale
3. P
package ball grid array (CSP_BGA) and is specified over
the industrial temperature range (–40°C to +85°C).
Rev. 0
Information furnished by Analog Devices is believed to be accurate and reliable.
However, no responsibility is assumed by Analog Devices for its use, nor for any
infringements of patents or other rights of third parties that may result from its use.
Specifications subject to change without notice. No license is granted by implication
or otherwise under any patent or patent rights of Analog Devices. Trademarks and
registered trademarks are the property of their respective owners.
No Missing Codes 25°C IV Guaranteed
Offset Error 25°C I −6 ±1.7 +6 % FSR
Gain Error 25°C I −12.5 ±2.0 +12.5 % FSR
Differential Nonlinearity (DNL) Full V ±0.35 LSB
Integral Nonlinearity (INL) Full V ±0.8 LSB
TEMPERATURE DRIFT
Offset Error Full V ±9 ppm/°C
Gain Error Full V ±172 ppm/°C
MATCHING CHARACTERISTICS
OBSOLETE
Offset Error Full V ±2.0 % FSR
Gain Error Full V ±1.0 % FSR
Input Referred Noise Full V 0.87 LSB rms
ANALOG INPUT
Input Range Full IV 296 mV p-p
Input Resistance (RIN)
Input Capacitance (CIN)
CLOCK INPUTS
High Level Input Voltage (VIH) Full IV 2.0 V
Low Level Input Voltage (V
High Level Input Current (IIH) Full IV −10 +10 μA
Low Level Input Current (IIL) Full IV −10 +10 μA
Input Capacitance (CIN) Full V 2 pF
LOGIC OUTPUTS
High Level Output Voltage (VOH) Full IV 2.49 V
Low Level Output Voltage (VOL) Full IV 0.2 V
INTERFACE TIMING
Maximum Conversion Rate Full VI 65 MSPS
Minimum Conversion Rate Full IV 1 MSPS
Clock Period (tC) Full V 15.4 ns
Clock Width High (tCH) Full IV 6.2 ns
Clock Width Low (tCL) Full IV 6.2 ns
Clock to Data (tOD) Full IV 2 6 ns
Pipeline Delay (Latency) Full V 7 Cycles
POWER SUPPLIES
Supply Voltages
AVDD Full IV 3.0 3.3 3.6 V
DRVDD Full IV 2.25 2.5 3.6 V
Supply Currents
AVDD Full VI 254 280 mA
DRVDD Full VI 12 15 mA
Total Power Dissipation Full VI 0.87 1.0 W
1
1
IL)
25°C V 100 Ω
25°C V 1.8 pF
Full IV 0.8 V
Rev. 0 | Page 3 of 20
Page 4
AD15252
www.BDTIC.com/ADI
Parameter Temp Test Level Min Typ Max Unit
SIGNAL-TO-NOISE RATIO (SNR)
f
= 70 MHz 25°C I 62.7 64.2 dBFS
INPUT
f
= 110 MHz 25°C V 64.1 dBFS
INPUT
f
= 140 MHz 25°C I 62.5 64 dBFS
INPUT
SINAD
f
= 70 MHz 25°C I 62.4 63.9 dBFS
INPUT
f
= 110 MHz 25°C V 63.7 dBFS
INPUT
f
= 140 MHz 25°C I 61.9 63.3 dBFS
INPUT
THD
f
= 70 MHz Full V −76 dBFS
INPUT
f
= 110 MHz Full V −74 dBFS
INPUT
f
= 140 MHz Full V −72 dBFS
INPUT
SPURIOUS-FREE DYNAMIC RANGE (SFDR)
f
= 70 MHz 25°C I 72.7 77.8 dBFS
INPUT
f
= 110 MHz 25°C V 75.9 dBFS
INPUT
f
= 140 MHz 25°C I 68 73.8 dBFS
INPUT
OBSOLETE
CROSSTALK 25°C V −70 dB
1
Input resistance and capacitance shown as differential.
Table 2. Explanation of Test Levels
Test Level Description
I 100% production tested.
II 100% production tested at 25°C, and sample tested at specified temperatures.
III Sample tested only.
IV Parameter is guaranteed by design and characterization testing.
V Parameter is a typical value only.
VI
All devices are 100% production tested at 25°C, guaranteed by design and characterization testing for industrial
ature range; 100% production tested at temperature extremes for military devices.
temper
Rev. 0 | Page 4 of 20
Page 5
AD15252
www.BDTIC.com/ADI
ABSOLUTE MAXIMUM RATINGS
Table 3.
Parameter Rating
AVDD to AGND −0.3 V, +3.9 V
DRVDD to DRGND −0.3 V, +3.9 V
DRGND to AGND −0.3 V, +0.3 V
DRVDD to AVDD −3.9 V, +3.9 V
Analog Inputs −0.3 V, AVDD + 0.3 V
Digital Outputs −0.3 V, DRVDD + 0.3 V
CLK −0.3 V, AVDD + 0.3 V
Operational Case Temperature −40°C to 85°C
Storage Temperature Range −65°C to 150°C
Lead Temperature: Infrared, 15 sec 230°C
OBSOLETE
ESD CAUTION
ESD (electrostatic discharge) sensitive device. Electrostatic charges as high as 4000 V readily accumulate on
the human body and test equipment and can discharge without detection. Although this product features
proprietary ESD protection circuitry, permanent damage may occur on devices subjected to high energy
electrostatic discharges. Therefore, proper ESD precautions are recommended to avoid performance
degradation or loss of functionality.
Stresses above those listed under Absolute Maximum Ratings
may cause permanent damage to the device. This is a stress
rating only; functional operation of the device at these or any
other conditions above those indicated in the operational
section of this specification is not implied. Exposure to absolute
maximum rating conditions for extended periods may affect
device reliability.
Rev. 0 | Page 5 of 20
Page 6
AD15252
www.BDTIC.com/ADI
PIN CONFIGURATION AND FUNCTION DESCRIPTIONS
87654321
Figure 2. Pin Configuration
Table 4. Pin Function Descriptions
Pin No. Mnemonic Description
A1 VINA Analog Input Pin (+) for Channel A.
OBSOLETE
A2 VINAAnalog Input Pin (−) for Channel A.
H1 VINB
H2
B4 CLK_A
G4 CLK_B Clock Input Pin for Channel B.
C4 PDWN_A Power-Down Function Selection for Channel A (Active High).
F4 PDWN_B Power-Down Function Selection for Channel B (Active High).
A4 OTR_A Out-of-Range Indicator for Channel A.
E8 OTR_B Out-of-Range Indicator for Channel B.
A3 VCM_A Channel A Common Mode.
H3 VCM_B Channel B Common Mode.
D4 OEB_A Output Enable for Channel A. Logic 0 enables Data Bus A; Logic 1 sets outputs to high-Z.
E4 OEB_B Output Enable for Channel B. Logic 0 enables Data Bus B; Logic 1 sets outputs to high-Z.
C5 D11_A(MSB) Channel A Data Output Bit 11 (MSB).
A5 D10_A Channel A Data Output Bit 10.
B5 D09_A Channel A Data Output Bit 9.
A6 D08_A
B6 D07_A Channel A Data Output Bit 7.
A7 D06_A
B7 D05_A
A8 D04_A
C6 D03_A
B8 D02_A
C7 D01_A Channel A Data Output Bit 1.
C8 D00_A(LSB)
E3 DFS
E7 D11_B(MSB)
F8 D10_B Channel B Data Output Bit 10.
F7 D09_B
G8 D08_B Channel B Data Output Bit 8.
VINB
Analog Input Pin (+) for Channel B.
Analog Input Pin (−) for Channel B.
Clock Input Pin for Channel A.
Channel A Data Output Bit 8.
Channel A Data Output Bit 6.
Channel A Data Output Bit 5.
Channel A Data Output Bit 4.
Channel A Data Output Bit 3.
Channel A Data Output Bit 2.
Channel A Data Output Bit 0 (LSB).
Data Output Format Select Bit (Logic 0 for offset binary, Logic 1 for twos complement).
Channel B Data Output Bit 11 (MSB).
Channel B Data Output Bit 9.
BOTTOM VIEW
(Not to Scale)
A
B
C
D
E
F
G
H
05154-003
Rev. 0 | Page 6 of 20
Page 7
AD15252
www.BDTIC.com/ADI
Pin No. Mnemonic Description
F6 D07_B Channel B Data Output Bit 7.
H8 D06_B Channel B Data Output Bit 6.
G7 D05_B Channel B Data Output Bit 5.
H7 D04_B Channel B Data Output Bit 4.
G6 D03_B Channel B Data Output Bit 3.
H6 D02_B Channel B Data Output Bit 2.
G5 D01_B Channel B Data Output Bit 1.
H5 D00_B Channel B Data Output Bit 0 (LSB).
C1 to C3, F1 to F3 AVDD Analog Power Supply.
B1 to B3, D3, G1 to G3 AGND Analog Ground.
D6, E6 DRVDD Digital Output Driver Supply.
D5, E5 DRGND Digital Output Ground.
E1 REFT Differential Reference (+).
E2 REFB Differential Reference (−).
OBSOLETE
D1 VREF Voltage Reference.
D2 REF_RTN Voltage Reference Return
H4, F5, D7, D8 DNC1 to DNC4 No Connect.
Rev. 0 | Page 7 of 20
Page 8
AD15252
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TYPICAL PERFORMANCE CHARACTERISTICS
0
–1
–2
–3
–4
–5
–6
–7
–8
ATTENUATION (dB)
–9
–10
–11
–12
10
OBSOLETE
Figure 3. Gain Flatness
100
FREQUENCY (MHz)
05154-004
1000
90
85
80
75
SFDR (dBFS)
70
65
60
–15
–14–13–12–11–10–9–8–7–6–5–4–3–2–1
INPUT AMPLITUDE (dBFS)
Figure 6. Single-Tone SFDR vs. AIN with fIN = 70 MHz
0
05154-007
0
–0.25
–0.50
–0.75
–1.00
–1.25
–1.50
–1.75
30MHz FLATNESS (dB)
–2.00
–2.25
–2.50
–2.75
125130135140145150155
120160
FREQUENCY (MHz)
Figure 4. Gain Flatness fIN =125MHz to 155 MHz
0
–10
–20
–30
–40
–50
–60
CROSSTALK (dBFS)
–70
–80
–90
1
10100
FREQUENCY (MHz)
Figure 5. Typical Crosstalk
90
85
80
75
SFDR (dBFS)
70
65
05154-005
60
–16
–14–12–10–8–6–4–2
INPUT AMPLITUDE (dBFS)
Figure 7. Single-Tone SFDR vs. AIN with fIN = 110 MHz
Figure 17. Single-Tone FFT of Channel B Digitizing f
While Channel A Digitizes f
= 110 MHz @ −9 dBFS
IN
2
5
= 110 MHz @ −9 dBFS
IN
05154-026
Rev. 0 | Page 10 of 20
Page 11
AD15252
www.BDTIC.com/ADI
THEORY OF OPERATION
The AD15252 consists of two high performance ADC channels.
The dual ADC paths are independent, except for a shared
internal band gap reference source, VREF. Each path consists of
a differential front end amplification circuit followed by a
sample-and-hold amplifier and multistage pipeline ADC.
The output-staging block aligns the data, carries out the error
rrection, and passes the data to the output buffers. The output
co
buffers are powered from a separate supply, allowing adjustment
of the output voltage swing.
ANALOG INPUT
Each analog input is fully differential, allowing sampling of
differential input signals. The differential input signals are accoupled and terminated in 100 Ω input impedances. The fullscale differential signal input range is 296 mV p-p.
OBSOLETE
VOLTAGE REFERENCE
The internal voltage reference of the ADC is pin strapped to a
fixed value of 0.5 V. A 10 μF capacitor should be used between
REFT and REFB.
CLOCK INPUT AND CONSIDERATIONS
Typical high speed ADCs use both clock edges to generate a
variety of internal timing signals and, as a result, can be
sensitive to clock duty cycle. Commonly, a 5% tolerance is
required on the clock duty cycle to maintain dynamic
performance characteristics.
The AD15252 provides separate clock inputs for each channel.
ptimum performance is achieved with the clocks operated
The o
at the same frequency and phase. Clocking the channels
asynchronously can significantly degrade performance. In some
applications, it is desirable to skew the clock timing of adjacent
channels. The AD15252’s separate clock inputs allow clock
timing skew (typically ±1 ns) between the channels without
significant performance degradation.
The AD15252 contains two internal clock duty cycle stabilizers
(D
CS), one for each converter, which retime the nonsampling
edge, providing an internal clock with a nominal 50% duty
cycle. Input clock rates of over 40 MHz can use the DCS so that
a wide range of input clock duty cycles can be accommodated.
Maintaining a 50% duty cycle clock is particularly important in
high speed applications, when proper track-and-hold times for
the converter are required to maintain high performance.
The duty cycle stabilizer uses a delay-locked loop to create the
n
onsampling edge. As a result, any change to the sampling
frequency requires approximately 2 μs to 3 μs to allow the DLL
to acquire and settle to the new rate.
High speed, high resolution ADCs are sensitive to the quality of
he clock input. The degradation in SNR at a given full-scale
t
input frequency (f
calculated by
SNR Degradation = 20 × log 10
In the equation, the rms aperture jitter, t
sum square of all jitter sources, which includes the clock input,
analog input signal, and ADC aperture jitter specification.
Undersampling applications are particularly sensitive to jitter.
For optimal performance, especially in cases where aperture
tter can affect the dynamic range of the AD15252, it is
ji
important to minimize input clock jitter. The clock input
circuitry should use stable references, for example, using analog
power and ground planes to generate the valid high and low
digital levels for the AD15252 clock input. Power supplies for
clock drivers should be separated from the ADC output driver
supplies to avoid modulating the clock signal with digital noise.
Low jitter crystal-controlled oscillators make the best clock
sources. If the clock is generated from another type of source
(by gating, dividing, or other methods), it should be retimed by
the original clock at the last step.
) due only to aperture jitter (tJ) can be
INPUT
(1/2 × p × f
, represents the root-
J
INPUT
× tJ)
POWER DISSIPATION AND STANDBY MODE
The power dissipated by the AD15252 is proportional to its
sampling rates. The digital (DRVDD) power dissipation is
determined primarily by the strength of the digital drivers and
the load on each output bit. The digital drive current can be
calculated by
I
= V
DRVDD
where:
he number of bits changing.
N is t
is the average load on the digital pins that changed.
C
LOAD
The analog circuitry is optimally biased so that each speed
g
rade provides excellent performance while affording reduced
power consumption. Each speed grade dissipates a baseline
power at low sample rates that increase with clock frequency.
Either channel of the AD15252 can be placed into standby mode
inde
pendently by asserting the PDWN_A or PDWN_B pins.
The minimum standby power is achieved when both channels
re placed into full power-down mode using PDWN_A =
a
PDWN_B = high. Under this condition, the internal references
are powered down. When either or both of the channel paths
are enabled after a power-down, the wake-up time is directly
related to the recharging of the REFT and REFB decoupling
capacitors and to the duration of the power-down. Typically, it
takes approximately 5 ms to restore full operation with fully
discharged 10 μF decoupling capacitors on REFT and REFB.
DRVDD
× C
LOAD
× f
CLOCK
× N
Rev. 0 | Page 11 of 20
Page 12
AD15252
www.BDTIC.com/ADI
A single channel can be powered down for moderate power
savings. The powered-down channel shuts down internal
circuits, but both the reference buffers and shared reference
remain powered. Because the buffer and voltage reference
remain powered, the wake-up time is reduced to several clock
cycles.
When using only one channel of the AD15252, the clock for the
abled channel should also be disabled, or distortion occurs in
dis
the channel in use.
DIGITAL OUTPUTS
The AD15252 output drivers can be configured to interface
with 2.5 V or 3.3 V logic families by matching DRVDD to the
digital supply of the interfaced logic. The output drivers are
sized to provide sufficient output current to drive a wide variety
of logic families. However, large drive currents tend to cause
current glitches on the supplies, which can affect converter
OBSOLETE
performance. Applications requiring the ADC to drive large
capacitive loads or large fan-outs can require external buffers or
latches.
The data format can be selected for either offset binary or twos
mplement. This is discussed later in the Data Format section.
co
TIMING
The AD15252 provides latched data outputs with a pipeline
delay of seven clock cycles. Data outputs are available one
propagation delay (t
Refer to
Figure 20 for a detailed timing diagram.
) after the rising edge of the clock signal.
PD
The length of the output data lines and the loads placed on
em should be minimized to reduce transients within the
th
AD15252. These transients can detract from the converter’s
dynamic performance.
The lowest typical conversion rate of the AD15252 is 1 MSPS.
t clock rates below 1 MSPS, dynamic performance can degrade.
A
DATA FORMAT
The AD15252 data output format can be configured for either
twos complement or offset binary. This is controlled by the data
format select pin (DFS). Connecting DFS to AGND produces
offset binary output data. Conversely, connecting DFS to AVDD
formats the output data as twos complement.
A
A
–1
B
–1
Figure 20. Example of Multiplexed Data Format Using the Channel A Output and the Same Clock Tied to CLK_A, CLK_B, and MUX_SELECT