The CS61535A combines the complete analog transmit
and receive line interface for T1 or E1 applications in a
low power, 28-pi n dev i ce operating from a +5V su ppl y .
The device features a transmitter jitter attenuator making it ideal for use in asynchro nous multiplexor s ystems
with gapped transmit clocks. The CS61535A provides a
matched, constant impedance output stage to insure
signal qualit y on m ism atched, poorly term inated lines.
Both ICs use a digital Delay-Locked-Loop clock and
data recovery circuit which is continuously calibrated
from a crystal reference to provide excellent stability
and jitter tolerance.
Applications
• Interfacing network transmission equipment such as
SONET multiplexor and M13 to a DSX-1 cross connect.
• Interfacing customer premis es equipment to a CSU.
TV+
Input Voltage, Any Pin(Note 1)V
Input Current, Any Pin(Note 2)I
Ambient Operating TemperatureT
Storage TemperatureT
in
in
A
stg
-
-
6.0
(RV+) + 0.3
RGND-0.3(RV+) + 0.3V
-1010mA
-4085
-65150
WARNIN G: O perat ions at or beyond these l imits may resul t in perma nent da mage to t he devi ce.
Normal operation is not guaranteed at these extremes.
Notes: 1. Excluding RTIP, RRING, whic h must stay wit hin -6V to (RV+ ) + 0.3V.
2. Transient currents of up to 1 00 mA will not cause SCR la tch-up. Also TTIP, TRING, TV+ and TGND
can withstand a continuous current of 100 mA.
RECOMMENDED OPERATING CONDITIONS
ParameterSymbolMinTypMaxUnits
DC Supply(Note 3) RV+, TV+4.755.05.25V
Ambient Operating TemperatureT
Power Consumption(Notes 4, 5)P
Power Consumption(Notes 4, 6)P
Notes: 3. TV+ must not exceed RV+ by more than 0.3V.
4. Power consumption while driving line load over operating temperature range. Includes IC and load.
Digital input levels are within 10% of the supply rails and digital outputs are driving a 50 pF load.
5. Assumes 100% ones density and maximum line length at 5.25V.
6. Assumes 50% ones density and 300ft. line length at 5.0V.
A
C
C
-402585
-290350mW
-175-mW
V
V
°C
°C
°C
2DS40F2
CS61535A
DIGITAL CHARACTERISTICS (TA = -40°C to 8 5°C; TV+, RV + = 5.0V ±5%; GND = 0V)
Notes: 12. Not production tested. Parameters guaranteed by design and characterization.
13. At tenuation measured at the demodulator output of an HP3785B with input jitter equal to 3/4 of
measured jitter tolerance using a measurement bandwidth of 1 Hz (10<f<100Hz), 4Hz (100<f<1000
Hz) and 10 Hz (f> 1kHz) centered around the jitter frequency. With a 2
Crystal must meet specifcations in CXT6176/8192 datasheet.
14. J itter measured at the demodulator output of an HP3785A using a measurement
bandwidth not to exceed 20 Hz centered around the jitter frequency. With a 2
Crystal must meet specifications in CXT6176/8192 datasheet.
15. Output jitter increases significantly when attenuator input jitter tolerance is exceeded.
3.0
20
35
40
40
3.0
20
30
35
35
6.0
30
35
50
50
6.0
32
43
50
50
15
-1 PRBS data pattern.
-
-
-
-
-
-
-
-
-
-
15
-1 PRBS data pattern.
dB
dB
dB
dB
dB
dB
dB
dB
dB
dB
DS40F23
CS61535A
ANALOG SPECIFICATIONS (TA = -40°C to 85°C; TV+, RV+ = 5. 0V ±5%; GND = 0V)
120Ω application(Note 18)
Recommended Output Load at TTIP and TRING-75Jitter Added During Remote Loopback(Note 21)
10Hz - 8kHz
8kHz - 40k Hz
10Hz - 40k Hz
Broad Band
Power in 2kHz band about 772kHz(Notes 12, 16)12.61517.9dBm
Power in 2kHz band about 1.544MHz(Notes 12, 16)
(referenced to power in 2kHz band at 772kHz)
Positive to Negative Pulse Imbalance(Notes 12, 16)
T1, DSX-1
E1 amplitude at center of pulse
E1 pulse width at 50% of nominal amplitude
Transmitter Return Loss(Notes 12, 16, 22)
51 kHz to 102 kHz
102 kHz to 2.048 MHz
2.048 MHz to 3.072 MHz
Transmitter Short Circuit Current(Notes 12, 23)--50mA RMS
Notes: 16. Usi ng a 0.47 µF capacitor in series with the primary of a transformer recommended
in the Applications Section.
17. Amplitude measured at the transformer (CS61535A-1:1 or 1:1.26) output across a
75 Ω load for line length settin g LEN2/1/0 = 0 /0/0.
18. Amplitude measured at the transformer (CS61535A-1:1.26) output across a
120 Ω load for line length setting LEN2/1/0 = 0/0/0.
19. Amplitude measured at the transformer (CS61535A-1:1.15) output across a
100 Ω load for line length setting LEN2/1/0 = 0/1/0.
20. Amplitude measured across a 100 Ω load at the DSX-1 cross-connect for line length settings
LEN2/1/0 = 0/1/1, 1/0/0, 1/0/1, 1/1/0 and 1/1/1 after the length of #22 AWG ABAM equivalent cable
specified in Table 3. The CS61535A requires a 1:1.15 transformer.
21. Input signal to RTIP/RRING is jitter free. Values will reduce slightly if jitter free clock is input to TCLK.
22. Return loss = 20 log
z0 = imped anc e of lin e loa d. Mea sur ed wi th a re pea ting 101 0 da ta p att ern wit h LEN 2/1 /0 = 0/ 0/0
and a 1:1 transformer terminated with a 75Ω load, or a 1:1.26 transformer terminated with a
120Ω load.
23. Measured broadband through a 0.5 Ω resistor across the secondary of a 1:1.26 transformer
during the transmission of an all ones data pattern for LEN2/1/0 = 0/0/0.
ABS((z1 +z0)/(z1-z0)) wher e z1 = impedance of the transmitter, and
10
2.14
2.7
2.7
2.4
-0.237
-0.3
-
-
-
-
-29-3 8-dB
-
-5
-5
8
14
10
2.37
3.0
3.0
3.0
-
-
0.005
0.008
0.010
0.015
0.2
-
-
-
-
-
2.6
3.3
3.3
3.6
0.237
0.3
0.02
0.025
0.025
0.05
0.5
5
5
-
-
-
V
V
V
V
V
V
Ω
UI
UI
UI
UI
dB
%
%
dB
dB
dB
4DS40F2
CS61535A
ANALOG SPECIFICATIONS (TA = -40°C to 85°C; TV+, RV+ = 5. 0V ±5%; GND = 0V)
ParameterMinTypMaxUnits
Driver Performance Monitor
MTIP/MRING Sensitivity:
Differential Voltage Required for Detection
25. For input amplitude of 0.5 Vpk to 1.2 Vpk and from 4. 14 Vpk to RV+.
26. For input amplitude of 1.05 Vpk to 3.3 Vpk.
27. J itter tolerance increases at lower frequencies. See Figure 11.
28. LOS goes high after 160 to 190 consecutive zeros are received. A zero is output on RPOS and
RNEG (or RDATA) for each bit period where the input signal amplitude remains below the data
decision threshold. The analog input squelch circuit operates when the input signal amplitude above
ground on the RTIP and RRING pins falls within the squelch range long enough for the internal
slicing threshold to decay within this range. Operation of the squelch causes zeros to be output on
RPOS and RNEG as long as the input amplitude remains below 0.25V. During receive LOS, pulses
greater than 0.25V in amplitude may be output on RPOS and RNEG. LOS returns low after the ones
density reaches 12.5% (based upon 175 bit periods starting with a one and containing
less than 100 consecutive zeros) as prescribed in ANSI T1.231-1993.
Rise Time, All Digital Outputs(Note 33)t
Fall Time, All Digital Outputs(Note 33)t
TPOS/TNEG (TDATA) to TCLK Falling Setup Timet
TCLK Falling to TPOS/TNEG (TDATA) Hold Timet
RPOS/RNEG Valid Before RCLK Falling(Note 34)t
RDATA Valid Before RCLK Falling(Note 35)t
RPOS/RNEG Valid Before RCLK Rising(Note 31)t
RPOS/RNEG Valid After RCLK Falling(Note 34)t
RDATA Valid After RCLK Falling(Note 35)t
RPOS/RNEG Valid After RCLK Rising(Note 31)t
TCLK Frequencyf
TCLK Pulse Width(Notes 12, 31, 34, 36, 37)
c
pwh3/tpw3
aclki
pwh1/tpw1
pw1
t
pwh1
t
pwl1
r
f
su2
h2
su1
su1
su1
h1
h1
h1
tclk
t
pwh2
(Notes 35, 36, 37)
Notes: 29. Cr ystal must meet specifications described in CXT6176/CXT8192 data sheet.
30. ACLKI provided by an external source or TCLK, but
not
RCLK.
31. Hardware Mode, or Host Mode (CLKE = 0).
32. RCLK cycle width will vary wit h extent by which p ulses displaced b y jitter. Specifie d under worst case
jitter conditions: 0.4 UI AMI data displacement for T1 and 0.2 UI AMI data displacement for E1.
33. At max load of 1.6 mA and 50 pF.
34. Host Mode (CLKE = 1).
35. Extended Hardware Mode.
36. The maximum TCLK burs t rate is 5 MHz and t
(min) = 200 ns. The maximum gap size that can
pw2
be tolerated on TCLK is 12 VI.
37. The transmitted pulse width does not depend on the TCLK duty cycle.
ACLKI Frequency(Note 30)f
RCLK Duty Cycle(Notes 31, 32) t
pwh1/tpw1
RCLK Cycle Width(Note 32)t
t
pwh1
t
RCLK Cycle Width(Note 32)t
t
pwh1
t
Rise Time, All Digital Outputs(Note 33)t
Fall Time, All Digital Outputs(Note 33)t
TPOS/TNEG (TDATA) to TCLK Falling Setup Timet
TCLK Falling to TPOS/TNEG (TDATA) Hold Timet
RPOS/RNEG Valid Before RCLK Falling(Note 34)t
RDATA Valid Before RCLK Falling(Note 35)t
RPOS/RNEG Valid Before RCLK Rising(Note 31)t
RPOS/RNEG Valid After RCLK Falling(Note 34)t
RDATA Valid After RCLK Falling(Note 35)t
RPOS/RNEG Valid After RCLK Rising(Note 31)t
TCLK Frequencyf
TCLK Pulse Width(Notes 31, 34, 36, 37)
SWITCHING CHARACTERISTICS (TA = -40 ° to 85°C; TV +, RV+ = ±5% ;
Inputs: Logic 0 = 0V, Logic 1 = RV+)
ParameterSymbolMinTypMaxUnits
SDI to SCLK Setup Timet
SCLK to SDI Hold Timet
SCLK Low Timet
SCLK High Timet
SCLK Rise and Fall Timet
CS to SCLK Setup Timet
SCLK to CS Hold Time(Note 38)t
CS Inactive Timet
SCLK to SDO Valid(Note 39)t
CS to SDO High Zt
Input Valid To PCS Falling Setup Timet
PCS Rising to Input Invalid Hold Timet
PCS Active Low Timet
Notes: 38. For CLKE = 0,
CS must remain low at least 50 ns after the 16th falling edge of SCLK.
39. Output load capacitance = 50pF.
dc
cdh
cl
ch
, t
r
cc
cch
cwh
cdv
cdz
su4
h4
pcsl
f
50--ns
50--ns
240--ns
240--ns
--50ns
50--ns
50--ns
250--ns
--200ns
-100-ns
50--ns
50--ns
250--ns
CS61535A
CS
SCLK
SDI
t
t
t
dc
LSB
cc
ch
t
t
cdh
cl
LSB
CONTROL BYTEDATA BYTE
Figure 4. Serial Port Write Timing Diagram
t
cdh
MSB
t
cch
t
cwh
8DS40F2
CS
SCLK
t
cdv
CS61535A
t
cdz
SDO
CLKE = 1
Figure 5. Seria l Port R ead Timi ng Di agra m
PCS
t
su4
t
LEN0/1/2, TAOS,
RLOOP, LLOOP,
RCODE, TCODE
Figure 6. Exte nded Ha rdwa re Mo de Par allel Chip Select Timin g Dia gram
VALID INPUT DATA
pcsl
t
h4
HIGH Z
DS40F29
CS61535A
THEORY OF OPERATION
Enhancement s in CS61535 A
The CS61535A provides higher performance and
more features than the CS61535 including:
•50% lower power consumption,
•Internally matched transmitter output imped-
ance for improved signal quality,
•Optional AMI, B8ZS, HDB3 enc oder/de cod er
or external line coding support,
•Receiver AIS (unframed all ones) detection,
•ANSI T1.231-1993 compliant receiver Loss
of Signal (LOS) handling,
•Transmitter TTIP and TRING outputs are
forced low when TCLK is static,
•The Driver Performance Monitor operates
over a wider range of input signal levels.
•Elimination of the requirement that a refer-
ence clock be input on the ACLKI pin.
Existing designs using the CS61535 can be converted
to the higher performance, pin-compatible CS61535A
if the transmit transformer is repl aced by a pin-compatible transform er with a new turns ratio and th e 4.4
Ω resistor use d in E1 75 Ω applications is shorted.
Introduction to Op erating Modes
The CS61535A supports three operating modes
which are se lected by th e level o f the MODE pi n
MODE
HARDWARE
MODE-PIN
INPUT LEVEL
CONTROL
METHOD
LINE CODE
ENCODER &
DECODER
AIS DETECTIONNOYESNO
DRIVER
PERFORM-
ANCE MONITOR
<0.2V
INDIVIDUAL
CONTROL
LINES
NONE
YESNOYES
EXTENDED
HARDWARE
FLOAT, or
2.5V
INDIVIDUAL
CONTROL
LINES &
P ARALLEL
CHIP
SELECT
AMI,
B8ZS,
HDB3
HOST
>(RV+) - 0.2V
SERIAL
µ-PROCESSOR
PORT
NONE
as shown in Ta bles 1 and 2, Figure 7, and Figures
A1-A3 of the Applications section.
The CS61535A modes are Hardware Mode, Extended Hardware Mode, and Host Mode. In
Hardware and Extended Hardware Modes, discrete
pins are used to configure and monitor the device.
The Extended Hardware Mode provides a parallel
chip select input which latches the control inputs
allowing individual ICs to be configured using a
common set of control lines. In the Host Mode, an
external processor monitors and configures the device through a serial interface. There are thirteen
multi-function pins whose functionality is determined by the operatin g mode (se e Table 2).
Transmitter
The transmitter takes data from a T1 (or E1 ) terminal, attenuates jitter, and produces pulses of
appropriate shape. The transmit clock, TCLK,
and transmit data, TPOS & TNEG or TDATA, are
supplied synchronously. Data is sampled on the
falling edge of the input clock, TCLK.
Either T1 (DSX-1 or Network Interface) or E1
G.703 pulse shapes may be selected. Pulse sh aping and signal level are determined by "line
length select" inputs as shown in Table 3. The
010FCC Part 68, Option A CSU NETWORK
011ANSI T1.403
AT&T C B113
(CS61535A only)
DSX-1
ABAM
(AT&T 600B
or 600C)
REPEATER
INTERFACE
Table 3. Line Length Selection
CS61535A line driver is desig ned to drive a 75 Ω
equivalent lo ad.
For T1 DSX-1 applications, line lengths from 0 to
655 feet (a s measured from t he transmitter to the
DSX-1 cross connect) are selectable. The five
partition arrangement meets ANSI T1.102-1993
requirements when using ABAM ca ble. A typical
output pulse is shown in Figure 8. These pulse
settings can also be used to meet CCITT pulse
shape requirements for 1.544 MHz operation.
width will meet the G.703 pulse shape template
shown in Fi gu r e 9, a n d specified in Table 4.
For E1 applications, the CS61535A driver provides 14 dB of return loss during the transmission
of both marks and spaces. This improves signal
quality by minimizing reflections off the transmitter. Similar levels of ret urn loss are provided
for T1 applications.
The CS61535A transmitter will detect a failed
TCLK, and will force the TTIP and TRING outputs low.
NORMALIZED
AMPLITUDE
1.0
0.5
AT&T CB 119
SPECIFICATION
For T1 Network Inte rface app lications , additi onal
options are provided. No te that the op timal pulse
width for Part 68 (324 ns) is narrower than the
optimal pulse width for DSX-1 (350 ns). The
CS61535A automatically adjusts the pulse width
based upon the "line length " se lection made.
The E1 G.703 pu lse shape is supported wit h line
length selection LEN2/1/0=0/0/0. The pulse
Nominal peak voltage of a mark (pulse)2.37 V3 V
Peak voltage of a spac e (n o pulse)
Nominal puls e wi dt h244 ns
Ratio of the amplitudes of positive and negative
pulses at the center of the pulse interval
Ratio of the widths of positive and negative
pulses at the nomi nal half amplitude
* When configured with a 0.47 µF nonpolarized capacitor in series with the TX transformer
primary as shown in Figures A1, A2 and A3.
0
CS61535A
OUTPUT
PULSE SHA PE
-0.5
02507501000
500
TIME (nanoseconds)
Figure 8. Typical Pulse Shape at DSX-1 Cross Connect
For coaxial cable,
75Ω load and
transformer specified
in Application Section.
For shielded twisted
pair, 120Ω load and
transformer specified
in Application Section.
0 ±0.237 V0 ±0.30 V
0.95 to 1.05*
0.95 to 1.05*
Table 4. CCITT G.703 S pecificati ons
12DS40F2
CS61535A
Percent of
nominal
peak
voltage
120
110
100
90
80
50
10
0
-10
-20
Figure 9 . Mask of the Pulse at the 2048 kbps Interface
269 ns
244 ns
194 ns
Nominal Pulse
219 ns
488 ns
When any transmit control pin (TAOS, LEN0-2
or LLOOP) is toggled, the transmitter stabilizes
within 22 bit periods. The transmitter will take
longer to stabilize when RLOOP is selected because the timi ng circuitry must adj ust to the new
frequency.
Jitter Attenuato r
The jitter attenu ator is designed to redu ce wander
and jitter i n the transmit clock signal. It c onsists
of a 32 bit FIFO, a cr ystal osci llator, a set of loa d
capacitors for the crystal, and cont rol logic. The
jitter attenuator exceeds the jitter attenuation requirements of Publications 43802 and REC.
G.742. A typical jitter attenuation curve is shown
in Figure 10.
The jitter attenuato r works in the following manner. Data on TPOS and TNEG (or TDATA) are
written into the jitter attenuator’s FIFO by TCLK.
The rate at which data is r ead out of th e F I FO and
transmitted is determined b y the oscillato r. Logic
circuits adju st the ca pacitive loadin g on the crys-
0
10
20
30
40
Attenuation in dB
b) Maximum
Attenuation
Limit
50
60
1101001 k10 k
Figure 10. Typical Jitter Attenuation Curve
a) Minimum Attenuation Limit
AT&T 62 41 1
Requirem ents
Measure d P er formance
Frequenc y in H z
tal to set its oscillation frequency to the average
of the TCLK freque ncy. Signal jit ter is absorbed
in the FIFO.
Jitter Tolera nce of Jitter Attenuator
The FIFO in the jitter attenuator is designed to
neither overflow nor underflow. If the jitter amplitude becomes very large, the read and write
pointers may get very close together. Should the
pointers attempt to cross, the oscillator’s divide
by four circuit adj usts by performing a divide by
3 1/2 or divide by 4 1/2 to pre vent the overflow
or underflow. When a divide by 3 1/2 or 4 1/2
occurs, the data bit will be driven on to the line
either an eighth bit period early or an eighth bit
period late.
When the T CLK frequency is close to th e center
frequency of the crystal oscillator, the high frequency jitt er tolerance is 23 UI before the divide
by 3 1/2 or 4 1/2 circuitry is activated. As the
center frequency of the oscillator and the TCLK
frequency deviat e from one anoth er, the jitter tolerance is reduced. As this frequency deviation
becomes large, the maximum jitter tolerance at
high frequencies is reduced to 12 UI before the
underflow/overflow circuitry is activated. In application, it is unlikely that the oscillator center
frequency will be precisely aligned with the
DS40F213
CS61535A
1 : 2
RTIP
Data
Level
Slicer
RRING
Edge
Detector
Figure 1 1. Re cei ver Bl oc k Di agr am
TCLK frequency due to allowable TCLK tolerance, part to part variations, crystal to crystal
variations, and crystal temperature drift. The oscillator tends to trac k l ow freque ncy ji tter s o jitt er
tolerance increases as ji tter frequency decreases.
The crystal frequ ency must be 4 times the nominal signal frequen cy: 6.176 MHz for 1.544 MHz
operation; 8.192 MHz for 2.048 MHz applications. Internal capacitors load the crystal,
controlling the oscillation frequency. The crystal
must be des igned so that ove r operating temperature, the oscillator frequency range exceeds the
system frequ ency tole rance. Cry stal Semicondu ctor offers the CXT6176 & CXT8192 crystals,
which yield optimum performance with the
CS61535A.
Transmit All Ones Select
The transmitter provides for all ones insertion a t
the frequency of ACLKI. Transmit all ones is selected when TAOS goes high, and causes
continuous ones to be transmitted on the line
(TTIP and TRING). In this mode , the TPOS and
TNEG (or TDATA) inputs are ignored. A TAOS
request will be ignored if remote loopback is in
effect. ACLKI jitte r will be attenuated. TAOS is
Data
Sampling
&
Clock
Extraction
Clock
Phase
Selector
Continuously
Calibrated
Delay Line
RPOS
RNEG
RCLK
ACLKI or
Oscillator in Jitter
Attenuator
not available on the CS61535A when ACLKI is
grounded.
Receiver
The recei ver extracts da ta and clock f r om an AMI
(Alternate Mark Inversion) coded signal and outputs clock an d synchronize d data. The re ceiver is
sensitive to sign als over the entire range of cable
lengths and requires no equalization or ALBO
(Automatic L ine Build Out) c ircuits. The signal is
received on bot h ends of a center-tapped, centergrounded transformer. The transformer is
center-tapped on t he IC side. The clock and data
recovery cir cuit ex ceeds th e jitte r toleran ce specifications of Publications 43802, 43801, 62411
amended, TR-TSY-000170, and CCITT REC.
G.823.
A block diagram of the rec eiver is shown in Figure 11. The two leads of the transformer (RTIP
and RRING) have oppo site polarity allowing the
receiver to treat RTIP and RRING as unipolar signals. Comparators are used to detect pulses on
RTIP and RRING. The compara tor threshold s are
dynamically established at a percent of the peak
level (50% of peak for E1, 6 5% of peak for T1;
with the slicing level selected by LEN2/1/0).
14DS40F2
CS61535A
The receiver us es an e dge detec tor and a con tinuously calibrated delay line to generate the
recovered clock. The delay line div ides its refer-
ence clock, ACLKI or the jitter attenuator’s
oscillator, into 13 equal divisions or phases . Continuous calib ration assures ti ming accuracy, even
if temperature or power supply voltage fluctuate.
The leading edge of an incoming data pulse triggers the clock ph ase selector. The phase selector
chooses one of the 13 avail able phases which th e
delay line pro duces for each bit perio d. The output from the phase selector feeds the clock and
data recovery circuits which generate the recovered clock and sample the incoming signal at
appropriate intervals to recover the data. The jitter
tolerance of the receiver exceeds that shown in
Figure 12.
300
100
28
PEAK
TO
10
PEAK
JITTER
(unit intervals)
1
.4
.1
Figure 12 . In put J itt er Tol eran ce of Receiv er
101k10k0100100k700
JITTER FREQUENCY (Hz)
300
the Host Mode, CLKE determines the clock polarity for which output data is stable and valid as
shown in Table 5.
MODE
(pin 5)
LOW
(<0.2V)
HIGH
(>(V+) - 0.2V)
HIGH
(>(V+) - 0.2V)
MIDDLE
(2.5V)
X = Don’t care
Table 5. Data Ou tput/Cl ock Relati onship
CLKE
(pin 28)
XRPOS
LOWRPOS
HIGHRPOS
XRDA TARCLKFalling
DATACLOCK Clock Edge for
RNEG
RNEG
SDO
RNEG
SDO
RCLK
RCLK
RCLK
RCLK
SCLK
RCLK
RCLK
SCLK
Valid Data
Rising
Rising
Rising
Rising
Falling
Falling
Falling
Rising
Jitter and R ecovered Clock
The CS61535A are designed for error free clock
and data recovery from an AMI encoded data
stream in the presence of m o re than 0.4 unit intervals of jitter at high frequency. The clock
recovery circuit is also tolerant of long strings of
zeros. The edge of an incoming data bit causes
the circui try to choose a phase from the delay line
which most closely corresponds with the arrival
time of the data edge, and that clock phase triggers a pulse whi ch is typ ically 1 40 ns in d urat ion.
This phase of the delay line will continue to be
selected unt il a data bit a rrives which is clo ser to
another of the 13 phases, causin g a new phase to
be selected. The largest jump allowed along the
delay line is six phases.
The CS61535A outputs a clock immediately upon
power-up. The clock recovery circuit is calibrated, and the device will lock onto the AMI
data input immediately. If loss of signal occurs,
the RCLK frequency will equal the ACLKI frequency.
In the Hardware Mode , data at RPOS and RNEG
is stable and may be sampled on the rising edge
of the recovered clock. In the Exte nded Hardware
Mode, data at RDATA is stable an d may be sampled on the fallin g edg e of the recov ered clock . In
When an i nput signal is jitter free, the phase selection will occasionally jump between two
adjacent p hases resulting in RCLK jitte r with an
amplitude of 1/13 UIpp . These single phase
jumps are due to differences in frequ ency of the
incoming data and the calibration clock input to
ACLKI. For T1 operation of the CS61535A, the
instantaneou s period can be 14/1 3 * 648 ns = 698
ns (1,662,769 Hz) or 12/13 * 648 ns = 598 ns
(1,425,231 Hz) when adjacent clock phases are
chosen. As long as the s ame phase is c hosen, the
DS40F215
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