Page 1
LTC6102
DYNAMIC RANGE (dB)
LTC6102-1/LTC6102HV
Precision Zero Drift
Current Sense Amplifier
FeaTures
n
Supply Range:
4V to 60V, 70V Maximum (LTC6102)
5V to 100V, 105V Maximum (LTC6102HV)
n
±10µV Input Offset Maximum
n
±50nV/°C Input Offset Drift Maximum
n
Fast Response: 1µs Step Response
n
Gain Configurable with Two Resistors
n
Low Input Bias Current: 3nA Maximum
n
PSRR 130dB Minimum
n
Output Currents up to 1mA
n
Operating Temperature Range: –40°C to 125°C
n
Disable Mode (LTC6102-1 Only): 1µA Maximum
n
Available in 8-Lead MSOP and 3mm × 3mm
DFN Packages
applicaTions
n
Current Shunt Measurement
n
Battery Monitoring
n
Remote Sensing
n
Load Protection
n
Motor Control
n
Automotive Controls
L, LT, LTC, LTM, Linear Technology and the Linear logo are registered trademarks of Linear
Technology Corporation. All other trademarks are the property of their respective owners.
DescripTion
The LT C®6102/LTC6102HV are versatile, high voltage, high-
side current sense amplifiers. Their high supply voltage
rating allows their use in many high side applications,
while the low drift and offset ensure accuracy across a
wide range of operating conditions. The LTC6102-1 is a
version of the LTC6102 that includes a low power disable
mode to conserve system standby power.
The LTC6102/LTC6102HV monitor current via the voltage
across an external sense resistor (shunt resistor). Internal
circuitry converts input voltage to output current, allowing
a small sense signal on a large common mode voltage to
be translated to a ground-referred signal. Low DC offset
allows the use of very low shunt resistor values and large
gain-setting resistors. As a result, power loss in the shunt
is reduced.
The wide operating supply and high accuracy make the
LTC6102 ideal for a large array of applications, from auto
motive, to industrial and power management. A maximum
input sense voltage of 2V allows a wide range of currents
and
voltages
to be monitored. Fast response makes the
LTC6102 the perfect choice for load current warnings and
shutoff protection control.
All versions of the LTC6102 are available in 8-lead MSOP
and 3mm × 3mm DFN packages.
-
Typical applicaTion
5V TO
105V
10A Current Sense with 10mA Resolution and 100mW
Maximum Dissipation
+
R
V
SENSE
1mΩ
+
IN
20Ω
+IN
–
+
L
–
V
O
A
D
LTC6102
R
OUT
= • V
V
OUT
SENSE
R
IN
–
= 249.5V
–INS
–INF
+
V
V
OUT
SENSE
0.1µF
REG
V
OUT
R
OUT
4.99k
*PROPER SHUNT SELECTION COULD ALLOW
MONITORING OF CURRENTS IN EXCESS OF 1000A
For more information www.linear.com/LTC6102
LTC2433-1
6102 TA01
Dynamic Current
Measurement Range
110
100
90
80
R
= 10mΩ
70
SENSE
Max V
SENSE
1µF
5V
TO µP
60
50
40
30
20
0.0001
MAXIMUM SENSE VOLTAGE (V)
R
= 100mΩ
SENSE
Max V
SENSE
= 100µV
DYNAMIC RANGE RELATIVE
TO 10µV OFFSET VOLTAGE
0.001 0.01 10.1
= 1V
6102 TA01b
6102fe
1
Page 2
LTC6102
TOP VIEW
TOP VIEW
LTC6102-1/LTC6102HV
absoluTe MaxiMuM raTings
(Note 1)
Total Supply Voltage (V+ to V–):
LTC6102/LTC6102-1
LTC6102HV
.........................................................105V
.............................................70V
Input Voltage Range
–INF, –INS
............................................ (V+ – 20V to V+ + 1V)
+IN
EN ............................................ (V
................................ (V+ – 4V to V+ + 0.3V)
–
– 0.3V to V– + 9V)
Differential (–INS – +IN), 1 Second ......................60V
Output Voltage Range
LTC6102/LTC6102HV ............... (V– – 0.3V to V– + 9V)
–
LTC6102-1 ............................. (V
– 0.3V to V– + 15V)
Input Current
–INF, –INS
...................................................................–10mA
+IN
........................................................±10mA
EN ....................................................................±10mA
pin conFiguraTion
Output Current .......................................(–1mA, +10mA)
Output Short Circuit Duration........................... Indefinite
Operating Temperature Range: (Note 2)
LTC6102C/LTC6102C-1/LTC6102HVC .. –40°C to 85°C
LTC6102I/LTC6102I-1/LTC6102HVI
...... –40°C to 85°C
LTC6102H/LTC6102H-1
LTC6102HVH...................................... –40°C to 125°C
Specified Temperature Range: (Note 2)
LTC6102C/LTC6102C-1/LTC6102HVC ...... 0°C to 70°C
LTC6102I/LTC6102I-1/LTC6102HVI
...... –40°C to 85°C
LTC6102H/LTC6102H-1
LTC6102HVH...................................... –40°C to 125°C
Storage Temperature Range ................... –65°C to 150°C
1–INS
–INF
2
–
V
/EN*
OUT
8-LEAD (3mm × 3mm) PLASTIC DFN
T
EXPOSED PAD (PIN 9) IS V
–
FOR THE LTC6102/LTC6102HV, EN FOR THE LTC6102-1
*V
JMAX
9
3
4
DD PACKAGE
= 150°C, θJA = 43°C/W
–
, MUST BE SOLDERED TO PCB
8
+IN
+
V
7
V
6
REG
–
V
5
*V
–INS
1
–INF
2
–
V
/EN*
3
OUT
4
MS8 PACKAGE
8-LEAD PLASTIC MSOP
= 150°C, θJA = 200°C/W
T
–
FOR THE LTC6102/LTC6102HV, EN FOR THE LTC6102-1
JMAX
8
+IN
+
7
V
V
6
REG
–
V
5
orDer inForMaTion
LEAD FREE FINISH TAPE AND REEL PART MARKING* PACKAGE DESCRIPTION SPECIFIED TEMPERATURE RANGE
LTC6102CDD#PBF LTC6102CDD#TRPBF LCKH 8-Lead (3mm × 3mm) Plastic DFN 0°C to 70°C
LTC6102IDD#PBF LTC6102IDD#TRPBF LCKH 8-Lead (3mm × 3mm) Plastic DFN –40°C to 85°C
LTC6102HDD#PBF LTC6102HDD#TRPBF LCKH 8-Lead (3mm × 3mm) Plastic DFN –40°C to 125°C
LTC6102CDD-1#PBF LTC6102CDD-1#TRPBF LDYB 8-Lead (3mm × 3mm) Plastic DFN 0°C to 70°C
LTC6102IDD-1#PBF LTC6102IDD-1#TRPBF LDYB 8-Lead (3mm × 3mm) Plastic DFN –40°C to 85°C
LTC6102HDD-1#PBF LTC6102HDD-1#TRPBF LDYB 8-Lead (3mm × 3mm) Plastic DFN –40°C to 125°C
LTC6102HVCDD#PBF LTC6102HVCDD#TRPBF LCVC 8-Lead (3mm × 3mm) Plastic DFN 0°C to 70°C
LTC6102HVIDD#PBF LTC6102HVIDD#TRPBF LCVC 8-Lead (3mm × 3mm) Plastic DFN –40°C to 85°C
LTC6102HVHDD#PBF LTC6102HVHDD#TRPBF LCVC 8-Lead (3mm × 3mm) Plastic DFN –40°C to 125°C
LTC6102CMS8#PBF LTC6102CMS8#TRPBF LTCKJ 8-Lead Plastic MSOP 0°C to 70°C
LTC6102IMS8#PBF LTC6102IMS8#TRPBF LTCKJ 8-Lead Plastic MSOP –40°C to 85°C
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2
For more information www.linear.com/LTC6102
Page 3
LTC6102
LTC6102-1/LTC6102HV
orDer inForMaTion
LEAD FREE FINISH TAPE AND REEL PART MARKING* PACKAGE DESCRIPTION SPECIFIED TEMPERATURE RANGE
LTC6102HMS8#PBF LTC6102HMS8#TRPBF LTCKJ 8-Lead Plastic MSOP –40°C to 125°C
LTC6102CMS8-1#PBF LTC6102CMS8-1#TRPBF LTDXZ 8-Lead Plastic MSOP 0°C to 70°C
LTC6102IMS8-1#PBF LTC6102IMS8-1#TRPBF LTDXZ 8-Lead Plastic MSOP –40°C to 85°C
LTC6102HMS8-1#PBF LTC6102HMS8-1#TRPBF LTDXZ 8-Lead Plastic MSOP –40°C to 125°C
LTC6102HVCMS8#PBF LTC6102HVCMS8#TRPBF LTCVB 8-Lead Plastic MSOP 0°C to 70°C
LTC6102HVIMS8#PBF LTC6102HVIMS8#TRPBF LTCVB 8-Lead Plastic MSOP –40°C to 85°C
LTC6102HVHMS8#PBF LTC6102HVHMS8#TRPBF LTCVB 8-Lead Plastic MSOP –40°C to 125°C
LEAD BASED FINISH TAPE AND REEL PART MARKING* PACKAGE DESCRIPTION SPECIFIED TEMPERATURE RANGE
LTC6102CDD LTC6102CDD#TR LCKH 8-Lead (3mm × 3mm) Plastic DFN 0°C to 70°C
LTC6102IDD LTC6102IDD#TR LCKH 8-Lead (3mm × 3mm) Plastic DFN –40°C to 85°C
LTC6102HDD LTC6102HDD#TR LCKH 8-Lead (3mm × 3mm) Plastic DFN –40°C to 125°C
LTC6102CDD-1 LTC6102CDD-1#TR LDYB 8-Lead (3mm × 3mm) Plastic DFN 0°C to 70°C
LTC6102IDD-1 LTC6102IDD-1#TR LDYB 8-Lead (3mm × 3mm) Plastic DFN –40°C to 85°C
LTC6102HDD-1 LTC6102HDD-1#TR LDYB 8-Lead (3mm × 3mm) Plastic DFN –40°C to 125°C
LTC6102HVCDD LTC6102HVCDD#TR LCVC 8-Lead (3mm × 3mm) Plastic DFN 0°C to 70°C
LTC6102HVIDD LTC6102HVIDD#TR LCVC 8-Lead (3mm × 3mm) Plastic DFN –40°C to 85°C
LTC6102HVHDD LTC6102HVHDD#TR LCVC 8-Lead (3mm × 3mm) Plastic DFN –40°C to 125°C
LTC6102CMS8 LTC6102CMS8#TR LTCKJ 8-Lead Plastic MSOP 0°C to 70°C
LTC6102IMS8 LTC6102IMS8#TR LTCKJ 8-Lead Plastic MSOP –40°C to 85°C
LTC6102HMS8 LTC6102HMS8#TR LTCKJ 8-Lead Plastic MSOP –40°C to 125°C
LTC6102CMS8-1 LTC6102CMS8-1#TR LTDXZ 8-Lead Plastic MSOP 0°C to 70°C
LTC6102IMS8-1 LTC6102IMS8-1#TR LTDXZ 8-Lead Plastic MSOP –40°C to 85°C
LTC6102HMS8-1 LTC6102HMS8-1#TR LTDXZ 8-Lead Plastic MSOP –40°C to 125°C
LTC6102HVCMS8 LTC6102HVCMS8#TR LTCVB 8-Lead Plastic MSOP 0°C to 70°C
LTC6102HVIMS8 LTC6102HVIMS8#TR LTCVB 8-Lead Plastic MSOP –40°C to 85°C
LTC6102HVHMS8 LTC6102HVHMS8#TR LTCVB 8-Lead Plastic MSOP –40°C to 125°C
Consult LTC Marketing for parts specified with wider operating temperature ranges. *The temperature grade is identified by a label on the shipping container.
For more information on lead free part marking, go to: http://www.linear.com/leadfree/
For more information on tape and reel specifications, go to: http://www.linear.com/tapeandreel/
For more information www.linear.com/LTC6102
6102fe
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Page 4
LTC6102
LTC6102-1/LTC6102HV
elecTrical characTerisTics
(LTC6102, LTC6102-1) The l denotes the specifications which apply over
the full operating temperature range, otherwise specifications are at TA = 25°C. RIN = 10Ω, R
= 10k, V
OUT
details), V+ = 12V, V– = 0V, VEN = 2.2V unless otherwise noted.
SYMBOL PARAMETER CONDITIONS MIN TYP MAX UNITS
+
V
V
OS
/ΔT
ΔV
OS
I
B
PSRR Power Supply Rejection Ratio V
V
SENSE(MAX)
V
OUT
I
OUT
t
r
BW Signal Bandwidth I
e
N
I
S
I
DIS
V
ENL
Supply Voltage Range 4 60 V
Input Offset Voltage
(Note 3)
Input Offset Voltage
(Note 4)
Input Offset Voltage Drift
(Note 3)
Input Bias Current (Note 5) RIN = 40k, V
Input Sense Voltage Full Scale
+
+
(V
– V
)
IN
Maximum Output Voltage
(LTC6102)
Maximum Output Voltage
(L
TC6102-1)
Maximum Output Current 6V ≤ V+ ≤ 60V, RIN = 1k, R
Input Step Response (to 2.5V on
a 5V Output Step)
V
= 100µV
SENSE
+
6V ≤ V
V
V
6V ≤ V
V
V
LTC6102C, LTC6102I, LTC6102C-1, LTC6102I-1
LTC6102H, LTC6102H-1
LTC6102C, LTC6102I, LTC6102C-1, LTC6102I-1
LTC6102H, LTC6102H-1
V
Error <1%, R
6V ≤ V
V
V
12V ≤ V
V
V
V
V
V
V
V
ΔV
R
V
OUT
I
OUT
≤ 60V
+
= 4V
= 100µV
SENSE
+
≤ 60V
+
= 4V
= 100µV
SENSE
= 2mV
SENSE
= 100µV, V+ = 6V to 60V
SENSE
= 100µV, V+ = 4V to 60V
SENSE
= 10k, R
IN
+
≤ 60V
+
= 4V
= 2mV, R
SENSE
+
= 6V
+
= 4V
= 2mV, R
SENSE
+
= 60V
+
= 12V
+
= 4V
+
= 4V, RIN = 10Ω, R
SENSE
= 4.99k, I
OUT
+
= 4V 1.5 µs
OUT
+
≤ 60V
OUT
= 100mV Transient, 6V ≤ V+ ≤ 60V, RIN = 100Ω,
OUT
= 200µA, RIN = 100Ω, R
= 1mA, RIN = 100Ω, R
OUT
= 100k
= 100k
= 1k, V
OUT
= 100µA
= 10k
OUT
OUT
OUT
= 1k, V
SENSE
= 4.99k
= 4.99k
SENSE
= 11mV
= 1.1V
l
l
l
l
l
l
l
l
l
l
l
l
l
l
l
l
130
125
120
115
0.8
14
11.7
3.8
0.5
Input Noise Voltage 0.1Hz to 10Hz 2 µV
Supply Current V+ = 4V, I
+
= 6V, I
V
+
= 12V, I
V
+
= 60V, I
V
LTC6102C, LTC6102I, LTC6102C-1, LTC6102I-1
LTC6102H, LTC6102H-1
Supply Current in Disable Mode
(LTC6102-1 Only)
VEN = 0.8V, V+ = 12V
V
= 0.8V, V+ = 60V
EN
Enable Input Voltage Low
= 0, RIN = 10k, R
OUT
= 0, RIN = 10k, R
OUT
= 0, RIN = 10k, R
OUT
= 0, RIN = 10k, R
OUT
= 100k
OUT
= 100k
OUT
= 100k
OUT
= 100k 420 575 µA
OUT
l
l
l
l
l
l
l
l
(LTC6102-1 Only)
2
8
3
1
1
+
= V+ (see Figure 1 for
SENSE
3
5
10
25
3
5
35
50
25
25
50
75
60
20
150 dB
140 dB
1 µs
140
200
275 400
475
290 425
500
300 450
525
650 µA
675 µA
18
0.8 V
µV
µV
µV
µV
nV/°C
nV/°C
pA
3
nA
nA
dB
dB
mA
mA
kHz
kHz
P-P
µA
µA
µA
µA
µA
µA
1
µA
µA
V
V
V
V
V
V
V
V
4
6102fe
For more information www.linear.com/LTC6102
Page 5
LTC6102
LTC6102-1/LTC6102HV
(LTC6102, LTC6102-1) The l denotes the specifications which apply over
elecTrical characTerisTics
the full operating temperature range, otherwise specifications are at TA = 25°C. RIN = 10Ω, R
details), V+ = 12V, V– = 0V, VEN = 2.2V unless otherwise noted.
SYMBOL PARAMETER CONDITIONS MIN TYP MAX UNITS
V
ENH
Enable Input Voltage High
(LTC6102-1 Only)
I
BEN
Enable Input Pin Current
VEN = 0V to 9V
(LTC6102-1 Only)
t
ON
Turn-On Time (LTC6102-1 Only) VEN = 2.2V, V
= 1mV, Output Settles to Within 1% of
SENSE
Final Value
t
OFF
Turn-Off Time (LTC6102-1 Only) VEN = 0.8V, V
= 1mV, Supply Current Drops to Less
SENSE
Than 10% of Nominal Value
f
S
elecTrical characTerisTics
(LTC6102HV) The l denotes the specifications which apply over the full
operating temperature range, otherwise specifications are at TA = 25°C. RIN = 10Ω, R
Sampling Frequency 10 kHz
OUT
V+ = 12V, V– = 0V unless otherwise noted.
SYMBOL PARAMETER CONDITIONS MIN TYP MAX UNITS
+
V
V
OS
/ΔT
ΔV
OS
I
B
PSRR Power Supply Rejection Ratio V
V
SENSE(MAX)
V
OUT
I
OUT
t
r
BW Signal Bandwidth I
e
N
Supply Voltage Range 5 100 V
Input Offset Voltage
(Note 3)
Input Offset Voltage
(Note 4)
Input Offset Voltage Drift (Note 3) V
V
SENSE
6V ≤ V
+
V
= 5V
V
SENSE
6V ≤ V
+
V
= 5V
SENSE
= 100µV
+
≤ 100V
= 100µV
+
≤ 100V
= 100µV
LTC6102HVC, LTC6102HVI
LTC6102HVH
Input Bias Current (Note 5) RIN = 40k, V
SENSE
= 2mV
LTC6102HVC, LTC6102HVI
LTC6102HVH
= 100µV, V+ = 6V to 100V
SENSE
= 100µV, V+ = 5V to 100V
V
SENSE
Input Sense Voltage Full Scale
+
(V
– V
)
+IN
Maximum Output Voltage V
Maximum Output Current 6V ≤ V+ ≤ 100V, RIN = 1k, R
Input Step Response (to 2.5V on a
5V Output Step)
Error <1%, R
6V ≤ V
+
V
= 5V
SENSE
12V ≤ V
+
V
= 5V
+
V
= 5V, RIN = 10Ω, R
ΔV
SENSE
R
= 100Ω, R
IN
+
= 5V 1.5 µs
V
= 200µA, RIN = 100Ω, R
OUT
I
= 1mA, RIN = 100Ω, R
OUT
IN
+
≤ 100V
= 2mV, R
+
≤ 100V
= 10k, R
OUT
OUT
= 100k
= 1k, V
OUT
= 10k
= 1k, V
OUT
SENSE
SENSE
= 11mV
= 100mV Transient, 6V ≤ V+ ≤ 100V,
= 4.99k, I
OUT
OUT
OUT
OUT
= 100µA
= 4.99k
= 4.99k
= 1.1V
Input Noise Voltage 0.1Hz to 10Hz 2 µV
OUT
l
l
= 10k, V
l
l
l
l
l
l
l
l
l
l
l
l
= 10k, V
2.2 V
+
SENSE
130
125
120
115
0.5
+
= V+ (see Figure 1 for
SENSE
8 µA
500 µs
100 µs
= V+ (see Figure 1 for details),
3
5
3
5
25
25
60
150 dB
140
2
1
8
3
1
1 µs
140
200
10
25
35
50
50
75
3
20
µV
µV
µV
µV
nV/°C
nV/°C
pA
nA
nA
dB
dB
dB
mA
mA
kHz
kHz
P-P
V
V
V
V
For more information www.linear.com/LTC6102
6102fe
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Page 6
LTC6102
LTC6102-1/LTC6102HV
elecTrical characTerisTics
(LTC6102HV) The l denotes the specifications which apply over the full
operating temperature range, otherwise specifications are at TA = 25°C. RIN = 10Ω, R
= 10k, V
OUT
V+ = 12V, V– = 0V unless otherwise noted.
SYMBOL PARAMETER CONDITIONS MIN TYP MAX UNITS
I
S
f
S
Supply Current V+ = 5V, I
+
= 6V, I
V
+
= 12V, I
V
+
= 100V, I
V
LTC6102HVC, LTC6102HVI
LTC6102HVH
Sampling Frequency 10 kHz
= 0, RIN = 10k, R
OUT
= 0, RIN = 10k, R
OUT
= 0, RIN = 10k, R
OUT
= 0, RIN = 10k, R
OUT
= 100k
OUT
= 100k
OUT
= 100k
OUT
= 100k 420 575 µA
OUT
SENSE
l
l
l
l
l
+
= V+ (see Figure 1 for details),
275 400
475
280 425
500
290 450
525
650 µA
675 µA
µA
µA
µA
µA
µA
µA
Note 1: Stresses beyond those listed under Absolute Maximum Ratings
may cause permanent damage to the device. Exposure to any Absolute
Maximum Rating condition for extended periods may affect device
reliability and lifetime. In addition to the Absolute Maximum Ratings, the
output current of the LTC6102 must be limited to ensure that the power
dissipation in the LTC6102 does not allow the die temperature to exceed
150°C. See the Applications Information “Output Current Limitations Due
to Power Dissipation” for further information.
Note 2: The LTC6102C/LTC6102C-1/LTC6102HVC are guaranteed to meet
specified performance from 0°C to 70°C. The LTC6102C/LTC6102C-1/
LTC6102HVC are designed, characterized and expected to meet specified
performance from –40°C to 85°C but are not tested or QA sampled at
these temperatures. LTC6102I/LTC6102I-1/LTC6102HVI are guaranteed
to meet specified performance from –40°C to 85°C. The LTC6102H/
LTC6102H-1/LTC6102HVH are guaranteed to meet specified performance
from –40°C to 125°C.
Note 3: These Parameters are guaranteed by design and are not 100%
tested. Thermocouple effects preclude measurements of these voltage
levels during automated testing.
Note 4: Limits are fully tested. Limit is determined by high speed
automated test capability.
Note 5: I
Please refer to the Typical Performance Characteristics section for
more information regarding actual typical performance. For tighter
specifications, please contact LTC Marketing.
specification is limited by practical automated test resolution.
B
6
6102fe
For more information www.linear.com/LTC6102
Page 7
20
20
3.0
15
15
6.5
Typical perForMance characTerisTics
MAXIMUM I
(mA)
GAIN (dB)
40
LTC6102
LTC6102-1/LTC6102HV
Input VOS vs Temperature
15
10
5
0
–5
INPUT OFFSET (μV)
–10
–15
–20
–40 1200 40 80
–20 20 60 100
TEMPERATURE (°C)
LTC6102: V
Maximum vs
OUT
Temperature
14
13
VS = 60V
12
11
VS = 12V
10
(V)
9
OUT
8
7
VS = 6V
6
5
MAXIMUM V
4
VS = 4V
3
2
1
0
–40 40 80 120100–20
VS = 5V
0 20 60
TEMPERATURE (°C)
VS = 4V
VS = 12V
6102 G01
6102 G04
Input VOS vs Supply Voltage
15
10
5
0
–5
INPUT OFFSET (μV)
–10
–15
–20
4 3212 168 24 2820 36 44 4840 52 56 60
LTC6102HV: V
SUPPLY VOLTAGE (V)
Maximum vs
OUT
Temperature
14
13
VS = 100V
12
11
VS = 12V
10
(V)
9
OUT
8
7
VS = 6V
6
5
MAXIMUM V
VS = 5V
4
3
2
1
0
–40 40 80 120100–20
0 20 60
TEMPERATURE (°C)
TA = –40°C
= 0°C
T
A
= 25°C
T
A
= 70°C
T
A
= 85°C
T
A
= 125°C
T
A
6102 G02
6102 G05
Input Sense Range
TA = 25°C
2.5
(V)
2.0
SENSE
1.5
1.0
MAXIMUM V
0.5
0
0 4020 12010060 80
V
SUPPLY
LTC6102/LTC6102-1: I
Maximum vs Temperature
6.0
VS = 12V
5.5
5.0
VS = 60V
4.5
(mA)
4.0
VS = 6V
OUT
3.5
3.0
2.5
VS = 5V
2.0
MAXIMUM I
1.5
VS = 4V
1.0
0.5
0
–40 40 80 120100–20 0 20 60
TEMPERATURE (°C)
(V)
OUT
6102 G03
6102 G06
LTC6102HV: I
Temperature
6.5
6.0
VS = 12V
5.5
5.0
VS = 100V
4.5
4.0
OUT
3.5
VS = 6V
3.0
2.5
2.0
VS = 5V
1.5
1.0
0.5
0
–40 40 80 120100–20 0 20 60
TEMPERATURE (°C)
Maximum vs
OUT
6102 G07
Gain vs Frequency
35
30
25
20
–10
15
10
5
0
–5
TA = 25°C
+
= 12V
V
R
IN
R
OUT
1k
= 100Ω
I
OUT
= 4.99k
10k 100k 10M1M
FREQUENCY (Hz)
For more information www.linear.com/LTC6102
= 200μA DC
I
OUT
= 1mA DC
6102 G09
Input Bias Current vs Temperature
100000
10000
1000
BIAS CURRENT (pA)
100
10
–40 40 80 120100–20
VS = 100V
= 60V
V
S
= 12V
V
S
= 6V
V
S
= 5V
V
S
0 20 60
TEMPERATURE (°C)
6102 G10
6102fe
7
Page 8
LTC6102
SUPPLY CURRENT (
A)
SUPPLY CURRENT (
A)
PSRR (dB)
160
NOISE (
V)
LTC6102-1/LTC6102HV
Typical perForMance characTerisTics
600
500
μ
400
300
200
100
V+ – 10mV
+
V
– 20mV
0.5V
LTC6102: Supply Current vs
Supply Voltage
TA = 85°C
TA = 125°C
TA = –40°C
0
8 16 48 5624 40284 12 44 5220 36 60
0
SUPPLY VOLTAGE (V)
TA = 70°C
TA = 0°C
32
Step Response 10mV to 20mV
–
V
SENSE
1V
V
OUT
TIME (10μs/DIV)
TA = 25°C
V
R
R
V
TA = 25°C
VIN = 0
= 2M
R
IN
+
= 12V
= 100Ω
IN
= 4.99k
OUT
+
SENSE
6102 G11
= V
6102 G14
+
600
500
μ
400
300
200
100
V
V+ – 100mV
5V
0V
LTC6102HV: Supply Current vs
Supply Voltage
TA = 85°C
TA = 70°C
TA = 125°C
TA = –40°C
0
8 16 48 56 64 72 80 88 9624 40
0
TA = 0°C
32
SUPPLY VOLTAGE (V)
Step Response 100mV
+
C
V
LOAD
V
SENSE
= 10pF
C
OUT
LOAD
–
= 1000pF
TIME (10μs/DIV)
TA = 25°C
+
= 12V
V
R
IN
R
OUT
V
SENSE
TA = 25°C
VIN = 0
= 2M
R
IN
6102 G12
= 100Ω
= 4.99k
+
= V
6102 G15
+
V+ – 10mV
0.5V
0V
5.5V
5V
0.5V
0V
Step Response 0mV to 10mV
V
SENSE
V
OUT
–
TIME (10μs/DIV)
+
V
Step Response Rising Edge
–
V
= 100mV
SENSE
TA = 25°C
V
R
I
= 0
OUT
I
= 100μA
V
OUT
OUT
TIME (500ns/DIV)
R
V
TA = 25°C
+
= 12V
V
= 100Ω
R
IN
= 4.99k
R
OUT
V
SENSE
+
= 12V
= 100Ω
IN
= 4.99k
OUT
+
SENSE
+
= V
6102 G13
= V
6102 G17
+
+
Step Response Falling Edge
–
V
= 100mV
SENSE
5.5V
5V
V
OUT
I
= 0
0.5V
0V
OUT
TIME (500ns/DIV)
8
I
OUT
= 100μA
TA = 25°C
+
= 12V
V
= 100Ω
R
IN
= 4.99k
R
OUT
V
SENSE
+
= V
6102 G18
PSRR vs Frequency
140
120
100
+
80
V+ = 12V
60
= 100Ω
R
IN
= 4.99k
R
OUT
40
= 49.9
A
V
= 500μA
I
OUT
20
0.1 1 10 100 1k 10k 100k 1M
FREQUENCY (Hz)
6102 G19
Input Referred Noise
0.1Hz to 10Hz
5
TA = 25°C
+
4
= 12V
V
= 10Ω
R
IN
3
= 1k
R
OUT
= 2mV
V
SENSE
2
1
μ
0
–1
–2
–3
–4
–5
0 1 2 3 4 5 6 7 8 9 10
TIME (s)
6102 G20
6102fe
For more information www.linear.com/LTC6102
Page 9
Typical perForMance characTerisTics
200
SUPPLY CURRENT (µA)
18
450
ENABLE PIN CURRENT (µA)
6
8
VOLTAGE (V)
LTC6102
LTC6102-1/LTC6102HV
Noise Spectral Density
100
VOLTAGE NOISE DENSITY (nV/√Hz)
0
100
1k 10k 1M100k
FREQUENCY (Hz)
400
350
300
250
200
150
100
SUPPLY CURRENT (µA)
50
0
–50
LTC6102-1: Supply Current vs
Supply Voltage
GAIN = 10
6102 G21
600
500
400
300
200
100
–100
0
0
LTC6102-1: Supply Current vs
Enable Voltage
V+ = 60V
V+ = 12V
TURN OFF (12V)
TA = 25°C
V
SENSE
21
0
ENABLE VOLTAGE (V)
43
6 7 9
5
8
VEN = 2V
V
SENSE
TA = 125°C
10 20
= 0V
10
6102 G24
= –0.1V
TA = 85°C
TA = –40°C
30 50
VOLTAGE SUPPLY (V)
TA = 25°C
40 60 70
6102 G22
LTC6102-1: Enable Pin Current vs
Enable Voltage
TA = 25°C
+
= 12V
V
5
4
3
2
1
0
–1
0
1
LTC6102-1: Supply Current vs
Supply Voltage when Disabled
VEN = 0.8V
16
14
12
10
8
6
4
SUPPLY CURRENT (µA)
2
TA = 125°C
0
–2
0
3
5
4
2
ENABLE VOLTAGE (V)
10
20
SUPPLY VOLTAGE (V)
7
6 8
TA = 25°C
TA = –40°C
30
40
10
9
6102 G25
TA = 85°C
50
7060
6102 G23
LTC6102-1: Turn-On Time LTC6102-1: Turn-Off Time
4.0
3.5
3.0
2.5
2.0
1.5
1.0
0.5
–0.5
0
–20
TA = 25°C
+
= 12V
V
V
SENSE
OUT
–10 0
–15
= 1mV
EN
–5 5 30
7
6
5
4
3
VOLTAGE (V)
2
1
0
–1
–200
TA = 25°C
+
= 12V
V
= 1mV
V
SENSE
EN
OUT
0 200 800
400 600
TIME (µs)
6102 G26
For more information www.linear.com/LTC6102
TIME (µs)
10 20
15 25
6102 G27
6102fe
9
Page 10
LTC6102
LTC6102-1/LTC6102HV
pin FuncTions
–INS (Pin 1): Amplifier Inverting Input. When tied to –INF,
the internal sense amplifier will drive –INS to the same
potential as +IN.
–INF (Pin 2): Force Input. This pin carries the input
current from R
resistor (R
= V
I
OUT
ternal R
–
V
SENSE/RIN
SENSE
(Pin 3, LTC6102/LTC6102HV Only): Negative Supply.
and must be tied to –INS near RIN. A
IN
) tied from V+ to –INF sets the output current
IN
. V
is the voltage across the ex-
SENSE
.
EN (Pin 3, LTC6102-1 Only): Enable Pin, Referenced to
the Negative Supply. When the enable pin is pulled high,
the LTC6102-1 is active. When the enable pin is pulled low
or left floating, the LTC6102-1 is disabled.
OUT (Pin 4): Open-Drain Current output. OUT will source
a current that is proportional to the sense voltage into
an external resistor. I
is the same current that enters
OUT
–INF.
V– (Pin 5): Negative Supply.
V
(Pin 6): Internal Regulated Supply. A 0.1µF (or
REG
larger) capacitor should be tied from V
REG
to V+. V
REG
is
not designed to drive external circuits.
+
(Pin 7): Positive Supply. Supply current is drawn
V
through this pin.
+IN (Pin 8): Amplifier Noninverting Input. Must be tied
to the system load end of the sense resistor. The +IN pin
has an internal 5k series resistor designed to allow large
input voltage transients or accidental disconnection of the
sense resistor. This pin can be held up to 20V below the
–INS pin indefinitely, or up to 60V below the –INS pin for
up to one second (see Absolute Maximum Ratings).
–
Exposed Pad (Pin 9, DFN Only): V
. The Exposed Pad
must be soldered to PCB.
10
6102fe
For more information www.linear.com/LTC6102
Page 11
block DiagraM
V
BATTERY
LTC6102
LTC6102-1/LTC6102HV
0.1µF
I
LOAD
V
SENSE
+
R
SENSE
–
L
O
A
D
R
IN
–INF
–INS
+IN
*LTC6102-1 ONLY
10V 5V
5k
5k
V
ENABLE
10V
EN*
+
V
V
REG
5V
–
+
OUT
–
V
–
V
6102 BD
I
OUT
R
SENSE
OUT
•
R
IN
= V
V
OUT
R
OUT
Figure 1. Block Diagram and Typical Connection
For more information www.linear.com/LTC6102
6102fe
11
Page 12
LTC6102
LTC6102-1/LTC6102HV
applicaTions inForMaTion
The LTC6102 high side current sense amplifier (Figure 1)
provides accurate monitoring of current through a userselected sense resistor. The sense voltage is amplified by
a user-selected gain and level shifted from the positive
power supply to a ground-referred output. The output
signal is analog and may be used as is or processed with
an output filter.
Theory of Operation
An internal sense amplifier loop forces –INS to have the
same potential as +IN. Connecting an external resistor,
, between –INS and V+ forces a potential across RIN
R
IN
that is the same as the sense voltage across R
corresponding current, V
SENSE/RIN
, will flow through RIN.
SENSE
. A
The high impedance inputs of the sense amplifier will not
conduct this input current, so it will flow through the –INF
pin and an internal MOSFET to the output pin.
The output current can be transformed into a voltage by
–
adding a resistor from OUT to V
then V
= V– + I
O
OUT
• R
OUT
.
. The output voltage is
Useful Gain Configurations
GAIN R
200 49.9Ω 10k 25mV
500 20Ω 10k 10mV
1000 10Ω 10k 5mV
4990 1Ω 4.99k 1mV
IN
R
OUT
V
SENSE
AT V
OUT
= 5V
Selection of External Current Sense Resistor
The external sense resistor, R
, has a significant effect
SENSE
on the function of a current sensing system and must be
chosen with care.
First, the power dissipation in the resistor should be
considered. The system load current will cause both heat
dissipation and voltage loss in R
. As a result, the sense
SENSE
resistor should be as small as possible while still providing
the input dynamic range required by the measurement.
Note that input dynamic range is the difference between
the maximum input signal and the minimum accurately
reproduced signal, and is limited primarily by input DC
offset of the internal amplifier of the LTC6102. In addition,
R
SENSE
must be small enough that V
does not exceed
SENSE
the maximum sense voltage specified by the LTC6102 or
the sense resistor, even under peak load conditions. As
an example, an application may require that the maximum
sense voltage be 100mV. If this application is expected
to draw 20A at peak load, R
should be no more
SENSE
than 5mΩ.
Once the maximum R
value is determined, the
SENSE
minimum sense resistor value will be set by the resolution or dynamic range required. The minimum signal
can
that
be accurately represented by this sense amp is
limited by the input offset. As an example, the LTC6102
has a typical input offset of 3µV. If the minimum current
is 1mA, a sense resistor of 3mΩ will set V
SENSE
to 3µV.
This is the same value as the input offset. A larger sense
resistor will reduce the error due to offset by increasing
the sense voltage for a given load current.
For this example, choosing a 5mΩ R
will maximize
SENSE
the dynamic range and provide a system that has 100mV
across the sense resistor at peak load (20A), while input
offset causes an error equivalent to only 0.6mA of load
current.
Peak dissipation is 2W. If a 0.5mΩ sense resistor is em
ployed, then the effective current error is 6mA (0.03%
of full-scale), while the peak sense voltage is reduced to
10mV at 20A, dissipating only 200mW.
The low offset and corresponding large dynamic range of
the LTC6102 make it more flexible than other solutions
in this respect. The 3µV typical offset gives 100dB of dy
namic range for a sense voltage that is limited to 300mV
max, and over 116dB of dynamic range if a maximum of
2V is allowed.
The previous example assumes that a large output dynamic
range is required. For circuits that do not require large
dynamic range, the wide input range of the LTC6102 may
be used to reduce the size of the sense resistor, reducing
power loss and increasing reliability. For example, in a
100A circuit requiring 60dB of dynamic range, the input
offset and drift of most current-sense solutions will require
that the shunt be chosen so that the sense voltage is at
least 100mV at full scale so that the minimum input is
greater than 100µV. This will cause power dissipation in
excess of 10W at full scale! That much power loss can put
6102fe
12
For more information www.linear.com/LTC6102
Page 13
applicaTions inForMaTion
LTC6102
LTC6102-1/LTC6102HV
a significant load on the power supply and create thermal
design headaches. In addition, heating in the sense resistor
can reduce its accuracy and reliability.
In contrast, the large dynamic range of the LTC6102 allows
the use of a much smaller sense resistor. The LTC6102
allows the minimum sense voltage to be reduced to less
than 10µV. The peak sense voltage would then be 10mV,
dissipating only 1W at 100A in a 100µΩ sense resistor!
With a specialized sense resistor, the same system would
allow peak currents of more than 1000A without exceeding
the input range of the LTC6102 or damaging the shunt.
Dynamic Range vs Maximum
Power Dissipation in R
110
100
DYNAMIC RANGE (dB)
R
90
100dB: MAX
80
V
SENSE
70
60
50
40
30
R
SENSE
20
0.001 0.01 0.1 1 10 100
MAXIMUM POWER DISSIPATION (W)
DYNAMIC RANGE RELATIVE
TO 10µV, MINIMUM V
MAX I
MAX I
MAX I
SENSE
= 1V
= 1mΩ
SENSE
= 1Ω
R
SENSE
SENSE
SENSE
= 100mΩ
SENSE
= 1A
= 10A
= 100A
= 100µΩ
SENSE
R
SENSE
40dB: MAX
V
SENSE
R
SENSE
SENSE
= 10mΩR
= 1mV
= 10µΩ
6102 AI01
Sense Resistor Connection
Kelvin connection of +IN and –INS to the sense resistor
should be used in all but the lowest power applications.
Solder connections and PC board interconnections that
carry high current can cause significant error in measure
ment due to their relatively large resistances. One 10mm
× 10mm square trace of one-ounce copper is approximately 0.5mΩ. A 1mV error can be caused by as little
2A
flowing through this small interconnect. This will
as
cause a 1% error in a 100mV signal. A 10A load current
in the same interconnect will cause a 5% error for the
same 100mV signal. An additional error is caused by the
change in copper resistance over temperature, which is in
excess of 0.4%/°C. By isolating the sense traces from the
high-current paths, this error can be reduced by orders of
magnitude. A sense resistor with integrated Kelvin sense
terminals will give the best results. Figure 2 illustrates the
recommended method. Note that the LTC6102 has a Kelvin
input structure such that current flows into –INF. The –INS
and –INF pins should be tied as close as possible to R
This reduces the parasitic series resistance so that R
IN
IN
.
may be as low as 1Ω, allowing high gain settings to be
used with very little gain error.
+
R
SENSE
V
LOAD
OUTPUT
TIE AS CLOSE TO R
–
R
IN
+
R
IN
+
–
V
LTC6102
R
IN
SENSE
–
LTC6102
+
R
R
OUT
*VISHAY VCS1625 SERIES
–
V
WITH 4 PAD KELVIN CONNECTION
–
IN
*
R
AS POSSIBLE
–INS+IN
–INF
+
V
V
REG
OUT
R
LOADV
+
IN
C
REG
–
V
OUT
6102 F02
0.1µF
V
OUT
Figure 2. Kelvin Input Connection Preserves Accuracy
with Large Load Current and Large Output Current
Selection of External Input Resistor, R
IN
The external input resistor, RIN, controls the transconductance of the current sense circuit, I
example, if R
1mA for V
should be chosen to provide the required resolution
R
IN
= 100, then I
IN
= 100mV.
SENSE
OUT
OUT
= V
= V
SENSE
SENSE/RIN
/100 or I
. For
OUT
=
while limiting the output current. At low supply voltage,
may be as much as 1mA. By setting RIN such that
I
OUT
For more information www.linear.com/LTC6102
6102fe
13
Page 14
LTC6102
RR
•
IR
101
+
LTC6102-1/LTC6102HV
applicaTions inForMaTion
the largest expected sense voltage gives I
= 1mA, then
OUT
the maximum output dynamic range is available. Output
dynamic range is limited by both the maximum allowed
output current (Note 1) and the maximum allowed output
voltage, as well as the minimum practical output signal. If
less dynamic range is required, then R
can be increased
IN
accordingly, reducing the output current and power dissipation. If small sense currents must be resolved accurately in a system that has very wide dynamic range, a
smaller R
another way, such as with a Schottky diode across R
may be used if the max current is limited in
IN
SENSE
(Figure 3). This will reduce the high current measurement
accuracy by limiting the result, while increasing the low
current measurement resolution. This approach can be
helpful in cases where occasional large burst currents
may be ignored.
V
6102 F03
D
SENSE
R
SENSE
LOAD
Figure 3. Shunt Diode Limits Maximum Input Voltage to Allow
Better Low Input Resolution Without Overranging
Care should be taken when designing the PC board layout for R
interconnect impedances will increase the effective R
, especially for small RIN values. All trace and
IN
IN
value, causing a gain error. It is important to note that the
large temperature drift of copper resistance will cause a
change in gain over temperature if proper care is not taken
to reduce this effect.
To further limit the effect of trace resistance on gain,
maximizing the accuracy of these circuits, the LTC6102 has
been designed with a Kelvin input. The inverting terminal
(–INS) is separate from the feedback path (–INF). During
operation, these two pins must be connected together.
The design of the LTC6102 is such that current into –INS
is input bias current only, which is typically 60pA at 25°C.
Almost all of the current from R
flows into –INF, through
IN
the LTC6102, and into R
via the OUT pin. In order to
OUT
minimize gain error, –INS should be routed in a separate
path from –INF to a point as close to R
addition, the higher potential terminal of R
connected directly to the positive terminal of R
any input voltage source). For the highest accuracy, R
as possible. In
IN
should be
IN
SENSE
(or
IN
should be a four-terminal resistor if it is less than 10Ω.
Selection of External Output Resistor, R
The output resistor, R
rent is converted to voltage. V
, determines how the output cur-
OUT
is simply I
OUT
OUT
OUT
• R
OUT
.
In choosing an output resistor, the max output voltage
must first be considered. If the circuit that is driven by the
output does not have a limited input voltage, then R
OUT
must be chosen such that the max output voltage does
not exceed the LTC6102 max output voltage rating. If the
following circuit is a buffer or ADC with limited input range,
then R
must be chosen so that I
OUT
OUT(MAX)
• R
OUT
is less
than the allowed maximum input range of this circuit.
In addition, the output impedance is determined by R
OUT
. If
the circuit to be driven has high enough input impedance,
then almost any output impedance will be acceptable.
However, if the driven circuit has relatively low input imped
ance, or draws spikes of current, such as an ADC might
do, then a lower R
value may be required in order to
OUT
preserve the accuracy of the output. As an example, if the
input impedance of the driven circuit is 100 times R
then the accuracy of V
VI
=
OUT OUT
IIR
=
OUT OUT OUT OUT
OUT IN DRIVEN
•
RR
OUT IN DRIVEN
•• .• •
will be reduced by 1% since:
OUT
()
+
()
100
099=
OUT
,
Error Sources
The current sense system uses an amplifier and resistors
to apply gain and level shift the result. The output is then
dependent on the characteristics of the amplifier, such as
gain and input offset, as well as resistor matching.
14
6102fe
For more information www.linear.com/LTC6102
Page 15
+
applicaTions inForMaTion
R
==
100
LTC6102
LTC6102-1/LTC6102HV
Ideally, the circuit output is:
VV
OUT SENSE
OUT
•; •
VRI
R
SENSESENSE SENSE
IN
In this case, the only error is due to resistor mismatch,
which provides an error in gain only.
Output Error, E
Voltage, V
E
OUT(VOS)
OS
, Due to the Amplifier DC Offset
OUT
= VOS • (R
OUT/RIN
)
The DC offset voltage of the amplifier adds directly to
the value of the sense voltage, V
. This error is very
SENSE
small (3µV typ) and may be ignored for reasonable values
. See Figure 4. For very high dynamic range, this
of R
IN
offset can be calibrated in the system due to its extremely
low drift.
VIN = 10µV
10
1
0.1
0.01
OUTPUT ERROR (%)
0.001
0.0001
0.00001 0.0001 0.001 0.01 0.1 1
Figure 4. LTC6102 Output Error Due to Typical Input Offset
vs Input Voltage
FOR A 500µΩ SHUNT
= 100mV, I
V
IN
ERROR DUE TO V
INPUT VOLTAGE (V)
SHUNT
= 200A
IS 6mA
OS
6102 F04
For instance if I
is 1nA and R
BIAS
is 10k, the output
OUT
error is –10µV.
Note that in applications where R
a voltage offset in R
(–) and E
I
B
, the bias current error can be similarly reduced if an
R
IN
external resistor R
OUT(IBIAS)
IN
that cancels the error due to
SENSE
≈ 0. In applications where R
(+) = (RIN – R
≈ RIN, IB(+) causes
SENSE
) is connected as
SENSE
SENSE
shown in Figure 5. Under both conditions:
E
OUT(IBIAS)
Adding R
= ± R
+
as described will maximize the dynamic
IN
range of the circuit. For less sensitive designs, R
• IOS; IOS = IB(+) – IB(–)
OUT
IN
not necessary.
V
–
R
IN
R
SENSE
LOAD
+
R
IN
+IN
V
–
LTC6102
+ =
R
IN
–
+
– –
R
R
IN
SENSE
–INS
–INF
+
V
V
REG
OUT
6102 F05
R
OUT
Figure 5. Second Input R Minimizes
Error Due to Input Bias Current
0.1µF
V
OUT
+
<
is
Output Error, E
(+) and IB(–)
I
B
, Due to the Bias Currents,
OUT
The input bias current of the LTC6102 is vanishingly small.
However, for very high resolution, or at high temperatures
where I
significant.
The bias current I
internal op amp. I
E
Since I
E
increases due to leakage, the current may be
B
(+) flows into the positive input of the
B
(–) flows into the negative input.
B
OUT(IBIAS)
(+) ≈ IB(–) = I
B
OUT(IBIAS)
= R
≈ –R
((IB(+) • (R
OUT
BIAS
• I
OUT
, if R
BIAS
SENSE/RIN
<< RIN then,
SENSE
) – IB(–))
For more information www.linear.com/LTC6102
Clock Feedthrough, Input Bias Current
The LTC6102 uses auto-zeroing circuitry to achieve an
almost zero DC offset over temperature, sense voltage,
and power supply voltage. The frequency of the clock
used for auto-zeroing is typically 10kHz. The term clock
feedthrough is broadly used to indicate visibility of this
clock frequency in the op amp output spectrum. There are
typically two types of clock feedthrough in auto zeroed
amps like the LTC6102.
The first form of clock feedthrough is caused by the
settling of the internal sampling capacitor and is input
referred; that is, it is multiplied by the internal loop gain
6102fe
15
Page 16
LTC6102
LTC6102-1/LTC6102HV
applicaTions inForMaTion
of the amp. This form of clock feedthrough is independent of the magnitude of the input source resistance or
the magnitude of the gain setting resistors. The LTC6102
input
has a residue clock feedthrough of less then 1
µV
RMS
referred at 10kHz.
The second form of clock feedthrough is caused by the
small amount of charge injection occurring during the
sampling and holding of the amp’s input offset voltage.
The current spikes are multiplied by the impedance seen
at the input terminals of the amp, appearing at the output
multiplied by the internal loop gain of the internal op amp.
To reduce this form of clock feedthrough, use smaller
valued gain setting resistors and minimize the source
resistance at the input.
Input bias current is defined as the DC current into the
input pins of the op amp. The same current spikes that
cause the second form of clock feedthrough described
above, when averaged, dominate the DC input bias current
of the op amp below 70°C.
As temperature increases, the leakage of the ESD protec
tion diodes on the inputs increases the input bias currents
of both inputs in the positive direction, while the current
caused by the charge injection stays relatively constant. At
temperatures above 70°C, the leakage current dominates
and both the negative and positive pins’ input bias currents
are in the positive direction (into the pins).
Output Current Limitations Due to Power Dissipation
IN
-
and
TC6102 can deliver more than 1mA continuous cur
The L
rent to the output pin. This current flows through R
enters the current sense amp via the –INF pin. The power
dissipated in the LTC6102 due to the output current is:
OUT
= (V
P
Since V
–INF
–INF
– V
≈ V+, P
OUT
OUT
) • I
OUT
≈ (V+ – V
OUT
) • I
OUT
There is also power dissipated due to the quiescent supply current:
P
= IS • V
Q
+
At maximum supply and maximum output current, the
total power dissipation can exceed 100mW. This will
cause significant heating of the LTC6102 die. In order to
prevent damage to the LTC6102, the maximum expected
dissipation in each application should be calculated. This
number can be multiplied by the θ
value listed in the
JA
package section on page 2 to find the maximum expected
die temperature. This must not be allowed to exceed 150°C
or performance may be degraded.
As an example, if an LTC6102 in the MSOP package is to
be biased at 55V ±5V supply with 1mA output current at
80°C:
• V
+ T
• V
+
RISE
+
(MAX)
(MAX)
= 39mW
= 60mW
P
Q(MAX)
P
OUT(MAX)
T
RISE
T
MAX
T
MAX
P
TOTAL(MAX)
= I
DD(MAX)
= I
OUT
= θJA • P
= T
TOTAL(MAX)
AMBIENT
must be < 125°C
≈ 99mW and the max die temp
will be 100°C
If this same circuit must run at 125°C, the max die temp
will increase to 145°C. (Note that supply current, and
therefore P
, is proportional to temperature. Refer to
Q
Typical Performance Characteristics section.) Note that
the DD package has a smaller θ
than the MSOP pack-
JA
age, which will substantially reduce the die temperature
at similar power levels.
The LTC6102HV can be used at voltages up to 105V
. This
additional voltage requires that more power be dissipated
for a given level of current. This will further limit the allowed
output current at high ambient temperatures.
It is important to note that the LTC6102 has been designed
to provide at least 1mA to the output when required, and
can deliver more depending on the conditions. Care must
be taken to limit the maximum output current by proper
choice of sense and input resistors and, if input fault
conditions are likely, an external clamp.
The total power dissipated is the output current dissipation
plus the quiescent dissipation:
P
TOTAL
16
= P
OUT
+ P
Q
For more information www.linear.com/LTC6102
6102fe
Page 17
V
applicaTions inForMaTion
RC
OUT OUT
Input Voltage: V
= IR
•
SENSE
IIN
LTC6102
LTC6102-1/LTC6102HV
Output Filtering
The output voltage, V
, is simply I
OUT
OUT
• Z
OUT
. This
makes filtering straightforward. Any circuit may be used
which generates the required Z
response. For example, a capacitor in parallel with R
to get the desired filter
OUT
OUT
will give a low pass response. This will reduce unwanted
noise from the output, and may also be useful as a charge
reservoir to keep the output steady while driving a switch
ing circuit such as a mux or ADC. This output capacitor
in parallel with an output resistor will create a pole in the
output response at:
f
dB
–
3
•• •
2=π
1
Useful Equations
Voltage
GGain:
Current Gain:
Transconductance:
Transimpedance:
SENSE
V
V
SENSE
I
OUT
I
EENSE
S
OUT
SENSESENSE
R
=
R
=
I
OUT
V
SENSE
V
OUT
I
OUT
R
IN
SENSE
R
IN
11
=
R
IN
= •
R
SENSE
R
OUT
R
BAT
R
IN
R
SENSE
+IN
–
V
–
–
+
LTC6102
LTC6102
–
+
LOAD
+
– 2V) TO V
(V
Figure 6. V+ Powered Separately from Load Supply (V
R
SENSE
V
BAT
LOAD
+
V
R
IN
+IN
–INS
–INF
+
V
V
REG
OUT
6102 F06
–INS
–INF
V
V
OUT
+
REG
+
V
0.1µF
V
OUT
R
OUT
BAT
0.1µF
V
OUT
R
OUT
6102 F07
)
Input Sense Range
The inputs of the LTC6102 can function from V
Not only does this allow a wide V
the input reference to be separate from the positive supply
(Figure 6). Note that the difference between V
must be no more than the input sense voltage range listed
in the Electrical Characteristics table.
Monitoring Voltages Above V
The LTC6102 may be configured to monitor voltages that are
higher than its supply, provided that the negative terminal
of the input voltage is within the input sense range of the
LTC6102. Figure 7 illustrates a circuit in which the LTC6102
has its supply pin tied to the lower potential terminal of the
sense resistor instead of the higher potential terminal. The
Figure 7. LTC6102 Supply Current Monitored with Load
+
to (V+ – 2V).
range, it also allows
SENSE
and V+
BAT
+
and Level Translation
operation of the LTC6102 is such that the –INS and –INF
pins will servo to within a few microvolts of +IN, which is
+
shorted to V
includes V
across R
causing current V
. Since the input sense range of the LTC6102
+
, the circuit will operate properly. The voltage
will be held across RIN by the LTC6102,
SENSE
SENSE/RIN
to flow to R
. In this case,
OUT
the supply current of the LTC6102 is also monitored, as
it flows through R
Because the voltage across R
the sense range of the LTC6102 in this circuit, V
SENSE
.
is not restricted to
SENSE
SENSE
can be large compared to the allowed sense voltage. This
facilitates the sensing of very large voltages, provided
that R
For more information www.linear.com/LTC6102
is chosen so that V
IN
SENSE/RIN
does not exceed
6102fe
17
Page 18
LTC6102
V
+
LTC6102-1/LTC6102HV
applicaTions inForMaTion
the allowed output current. The gain is still controlled by
R
OUT/RIN
, so either gain or attenuation may be applied to
the input signal as it is translated to the output. Finally,
the input may be a voltage source rather than a sense
resistor, as shown in Figure 8. This circuit allows the
translation of a wide variety of input signals across the
entire supply range of the LTC6102 with only a tiny offset
error while retaining simple gain control set by R
OUT/RIN
Again, very large voltages may be sensed as long as R
is chosen so that I
current. For example, V
1k, or as large as 10V with R
input and a 5V maximum output, R
will allow the LTC6102HV to translate V
does not exceed the allowed output
OUT
may be as large as 1V with RIN =
IN
= 10k. For a 10V maximum
IN
= 10k and R
IN
IN
to V
OUT
OUT
.
IN
= 5k
with a
common mode voltage of up to 100V. For the case where
a large input resistor is used, a similar resistor in series
with +IN will reduce error due to input bias current.
V
R
IN
V
IN
+IN
–
V
CM
+
–
V
–INS
–INF
+
V
V
REG
0.1µF
LTC6102 by effectively reducing the supply voltage to the
part by V
.
D
In addition, if the output of the LTC6102 is wired to a device
that will effectively short it to high voltage (such as through
an ESD protection clamp) during a reverse supply condi
tion, the LTC6102’s output should be connected through
a resistor or Schottky diode (Figure 10).
Response Time
TC6102 is designed to exhibit fast response to inputs
The L
for the purpose of circuit protection or signal transmission.
This response time will be affected by the external circuit
in two ways, delay and speed.
R
SENSE
+
V
BATT
L
O
A
D
V
D1
–
LTC6102
–
–INS+IN
–INF
V
V
OUT
+
REG
R1
100Ω
0.1µF
R2
4.99k
6102 F09
Figure 9. Schottky Prevents Damage During Supply Reversal
LTC6102
R
= VIN •
R
OUT
IN
V
OUT
OUT
Figure 8. Voltage Level-Shift Circuit
Reverse Supply Current
Some applications may be tested with reverse-polarity
supplies due to an expectation of this type of fault during
operation. The LTC6102 is not protected internally from
external reversal of supply polarity. To prevent damage
V
OUT
R
OUT
6102 F08
BATT
L
O
A
D
R
SENSE
+IN
V
D1
–
LTC6102
R1
100Ω
–INS
+
–
–INF
+
V
V
REG
OUT
0.1µF
R2
4.99k
R3
1k
ADC
6102 F10
that may occur during this condition, a Schottky diode
–
should be added in series with V
limit the reverse current through the LTC6102. Note that
(Figure 9). This will
Figure 10. Additional Resistor R3 Protects
Output During Supply Reversal
this diode will limit the low voltage performance of the
6102fe
18
For more information www.linear.com/LTC6102
Page 19
applicaTions inForMaTion
LTC6102
LTC6102-1/LTC6102HV
If the output current is very low and an input transient
occurs, there may be a delay before the output voltage
begins changing. This can be reduced by increasing the
minimum output current, either by increasing R
decreasing R
. The effect of increased output current
IN
SENSE
or
is illustrated in the step response curves in the Typical
Performance Characteristics section of this datasheet.
Note that the curves are labeled with respect to the initial
output currents.
The speed is also affected by the external circuit. In this
case, if the input changes very quickly, the internal ampli
fier will slew the gate of the internal output FET (Figure 1)
in order to close the internal loop. This results in current
flowing through R
and the internal FET. This current slew
IN
rate will be determined by the amplifier and FET characteristics as well as the input resistor, R
will allow the output current to increase more quickly,
R
IN
. Using a smaller
IN
decreasing the response time at the output. This will also
have the effect of increasing the maximum output current.
Using a larger R
since V
R
OUT
= I
OUT
will both have the effect of increasing the voltage
will also decrease the response time,
OUT
OUT
• R
. Reducing RIN and increasing
OUT
gain of the circuit.
Bandwidth
For applications that require higher bandwidth from the
LTC6102, care must be taken in choosing R
. For a gen-
IN
eral-purpose op-amp, the gain-bandwidth product is used
to determine the speed at a given gain. Gain is determined
by external resistors, and the gain-bandwidth product is
an intrinsic property of the amplifier. The same is true
for the L
TC6102, except that the feedback resistance is
determined by an internal FET characteristic. The feedback
impedance is approximately 1/g
of the internal MOSFET.
m
The impedance is reduced as current into –INF is increased.
At 1mA, the impedance of the MOSFET is on the order of
10kΩ. R
as 1/(R
(R
IN
sets the closed-loop gain of the internal loop
IN
• gm). The bandwidth is then limited to GBW •
IN
• gm), with a maximum bandwidth of around 2MHz.
This is illustrated in the characteristic curves, where gain
vs frequency for two input conditions is shown. The exact
impedance of the MOSFET is difficult to determine, as it
is a function of input current, process, and capacitance,
and has a very different characteristic for low currents
vs high currents. However, it is clear that smaller values
and smaller values of I
of R
IN
lower closed-loop bandwidth. V
chosen to maximize both I
will generally result in
OUT
and RIN should be
SENSE
and closed-loop gain for
OUT
highest speed. Theoretically, maximum bandwidth would
be achieved for the case where V
giving I
= 1mA and a closed-loop gain near 1. However,
OUT
= 10VDC and RIN = 10k,
IN
this may not be possible in a practical application. Note
that the MOSFET g
value of I
, not the peak value. Adding DC current to a
OUT
is determined by the average or DC
m
small AC input will help increase the bandwidth.
Bypassing
V
REG
The LTC6102 has an internally regulated supply near V+
for internal bias. It is not intended for use as a supply or
bias pin for external circuitry. A 0.1µF capacitor should be
connected between the V
and V+ pins. This capacitor
REG
should be located very near to the LTC6102 for the best
performance. In applications which have large supply tran
sients, a 6.8V zener diode may be used in parallel with this
bypass capacitor for additional transient suppression.
Enable Pin Operation
The LTC6102-1 includes an enable pin which can place
the part into a low power disable state. The enable pin is a
–
logic input pin referenced to V
logic levels regardless of the V
and accepts standard TTL
+
voltage. When the enable
pin is driven high, the part is active. When the enable pin is
floating or pulled low, then the part is disabled and draws
very little supply current. When driven high, the enable pin
draws a few microamps of input bias current.
If there is no external logic supply available, the enable
+
pin can be pulled to the V
supply through a large value
resistor. The voltage at the enable pin will be clamped
by the built-in ESD protection structure (which acts like
a zener diode). The resistor should be sized so that the
current through the resistor is a few milliamps or less to
prevent any reduction in long-term reliability. For practi
cal purposes, the current through the resistor should be
minimized to save power. The resistor value is limited
by the input bias current requirements of the enable
For more information www.linear.com/LTC6102
6102fe
19
Page 20
LTC6102
+
ENABLE VOLTAGE (V)
LTC6102-1/LTC6102HV
applicaTions inForMaTion
V
–
R
IN
R
SENSE
LOAD
R
2.7M
BIAS
+
R
IN
+IN
V
EN
–
R
+
LTC6102-1
+ =
R
IN
IN
–
– –
R
SENSE
–INS
–INF
+
V
V
REG
OUT
6102 F11
0.1µF
V
OUT
R
OUT
Figure 11
pin. Figure 11 shows the LTC6102-1 with a 2.7M pull-up
resistor to limit the current to less than 20µA with a 60V
supply, which is enough to satisfy the input bias current
requirement.
Start-Up Current
The start-up current of the LTC6102 when the part is
powered on or enabled (LTC6102-1) consists of three
parts: the first is the current necessary to charge the
bypass capacitor, which is nominally 0.1µF. Since the
V
REG
voltage charges to approximately 4.5V below the V+
V
REG
voltage, this can require a significant amount of start-up
current. The second source is the active supply current of
the LTC6102 amplifier, which is not significantly greater
during start-up than during normal operation. The third
source is the output current of the LTC6102, which upon
start-up may temporarily drive the output high. This could
cause milliamps of output current (limited mostly by the
input resistor R
) to flow into the output resistor and/or
IN
the output limiting ESD structure in the LTC6102. This is
a temporary condition which will cease when the LTC6102
amplifier settles into normal closed-loop operation.
When the LTC6102-1 is disabled, the internal amplifier is
also shut down, which means that the discharge rate of
the 0.1µF capacitor is very low. This is significant when the
LTC6102-1 is disabled to save power, because the recharg
ing of the 0.1µF capacitor is a significant portion of the
overall power consumed in startup. Figure 12 shows the
discharge rate of the 0.1
µF capacitor after the L
TC6102-1
is shut down at room temperature.
In a system where the LTC6102-1 is disabled for short
periods, the start-up power (and therefore the average
power) can be reduced since the V
bypass capacitor
REG
is never significantly discharged. The time required to
charge the V
capacitor will also be reduced, allowing
REG
the LTC6102-1 to start-up more quickly.
2.25
2.00
1.75
1.50
1.25
1.00
0.75
0.50
0.25
0
–2
4
0
6
2
TIME (ms)
Figure 12. LTC6102-1 V
TA = 25°C
+
V
V
REG
EN
8 16
10
12
Voltage During
REG
Bypass Capacitor Discharge when Disabled
= 12V
14
6102 F12
8.3
8.2
8.1
8.0
7.9
7.8
7.7
7.6
7.5
7.4
V
REG
VOLTAGE (V)
20
6102fe
For more information www.linear.com/LTC6102
Page 21
Typical applicaTions
Bidirectional Current Sense Circuit with Separate Charge/Discharge Output
LTC6102
LTC6102-1/LTC6102HV
R
IN C
100Ω
V
BATT
V
–
LTC6102
V
OUT D
V
OUT C
I
CHARGE
+
–
= I
DISCHARGE • RSENSE
= I
CHARGE • RSENSE
R
SENSE
V
DISCHARGE
CHARGE
OUT D
≥ 0CHARGING:
R
IN D
100Ω
–INS +IN
0.1µF
V
REG
OUT
+
R
OUT D
4.99k
–
≥ 0DISCHARGING:
R
IN C
100Ω
–INS+IN
–INF –INF
+
V
0.1µF
V
REG
OUT
R
R
( )
+
OUT C
V
4.99k
OUT C
R
OUT C
–
R
OUT D
WHEN I
( )
R
IN D
WHEN I
IN C
V
+
I
DISCHARGE
–
+
LTC6102
CHARGER
R
IN D
100Ω
–
V
L
O
A
D
6102 TA02
V
OUT
LTC6102 Monitors Its Own Supply Current
R
SENSE
L
V
BATT
= 49.9 • R
O
D
A
SENSE
I
LOAD
–
V
(I
+ I
LOAD
LTC6102
SUPPLY
+
–
)
–INS+IN
–INF
V
V
OUT
+
REG
R2
4.99k
R1
100
0.1µF
6102 TA03
+
–
I
SUPPLY
V
OUT
For more information www.linear.com/LTC6102
6102fe
21
Page 22
LTC6102
LTC6102-1/LTC6102HV
Typical applicaTions
16-Bit Resolution Unidirectional Output into LTC2433 ADC
4V TO 60V
I
LOAD
POWER ENABLE
FAULT
OFF ON
1µF
V
+
V
SENSE
–
L
O
A
D
–
V
EN
LTC6102-1
V
= • V
OUT
+
–
R
R
OUT
IN
SENSE
= 49.9V
–INS+IN
–INF
V
V
REG
OUT
R
4.99k
+
OUT
SENSE
V
R
100Ω
0.1µF
OUT
IN
Intelligent High-Side Switch with Current Monitor
LOGIC
47k
10µF
63V
3
4
LT1910 LTC6102
2
1 5
14V
100Ω
8
6
1%
R
S
100Ω
SUB85N06-5
–INS
–INF
+IN
2 1
+
REF
4
+
IN
LTC2433-1
–
IN
5
REF–GND
ADC FULL-SCALE = 2.5V
+
V
–
V
1µF
5V
V
CC
9
SCK
8
C
7
4.99k
TO µP
6102 TA05
V
O
V
REG
OUT
SDD
C
F
O
1063
0.1µF
22
= 49.9 • RS • I
V
L
O
I
L
A
D
O
FOR RS = 5mΩ,
= 2.5V AT IL = 10A (FULL SCALE)
V
O
For more information www.linear.com/LTC6102
L
6102 TA06
6102fe
Page 23
Typical applicaTions
DANGER! Lethal Potentials Present — Use Caution
R
SENSE
LOAD
LTC6102
LTC6102-1/LTC6102HV
Input Overvoltage Protection
+
V
–
R
IN
D
1k
3W
Z
–
V
1k
–
+
–INS+IN
–INF
V
V
+
REG
0.1µF
DZ: CENTRAL SEMICONDUCTOR
CMZ5931B 18V 1.5W ZENER DIODE
500V
+
V
R
SENSE
I
SENSE
SENSE
–
L
O
A
D
–
V
LTC6102
Simple 500V Current Monitor
–INS+IN
–INF
V
V
REG
OUT
+
0.1µF
M1
LTC6102
+
–
R
IN
100Ω
OUT
BAT46
R
OUT
6102 TA07
DANGER!!
HIGH VOLTAGE!!
51V
BZX884-C51
M1 AND M2 ARE FQD3P50 TM
R
OUT
V
= • V
OUT
R
IN
SENSE
= 49.9 V
For more information www.linear.com/LTC6102
SENSE
V
OUT
R
OUT
4.99k
M2
2M
6102 TA08
6102fe
23
Page 24
LTC6102
R = 0.125
LTC6102-1/LTC6102HV
package DescripTion
DD Package
8-Lead Plastic DFN (3mm × 3mm)
(Reference LTC DWG # 05-08-1698 Rev C)
3.5 ±0.05
0.70 ±0.05
1.65 ±0.05
(2 SIDES)2.10 ±0.05
PACKAGE
OUTLINE
0.25 ± 0.05
0.50
BSC
2.38 ±0.05
RECOMMENDED SOLDER PAD PITCH AND DIMENSIONS
APPLY SOLDER MASK TO AREAS THAT ARE NOT SOLDERED
NOTE:
1. DRAWING TO BE MADE A JEDEC PACKAGE OUTLINE M0-229 VARIATION OF (WEED-1)
2. DRAWING NOT TO SCALE
3. ALL DIMENSIONS ARE IN MILLIMETERS
4. DIMENSIONS OF EXPOSED PAD ON BOTTOM OF PACKAGE DO NOT INCLUDE
MOLD FLASH. MOLD FLASH, IF PRESENT, SHALL NOT EXCEED 0.15mm ON ANY SIDE
5. EXPOSED PAD SHALL BE SOLDER PLATED
6. SHADED AREA IS ONLY A REFERENCE FOR PIN 1 LOCATION
ON TOP AND BOTTOM OF PACKAGE
PIN 1
TOP MARK
(NOTE 6)
0.200 REF
MS8 Package
8-Lead Plastic MSOP
(Reference LTC DWG # 05-08-1660 Rev F)
3.00 ±0.10
(4 SIDES)
0.75 ±0.05
1.65 ± 0.10
0.00 – 0.05
TYP
(2 SIDES)
0.25 ± 0.05
BOTTOM VIEW—EXPOSED PAD
2.38 ±0.10
0.40 ± 0.10
85
14
0.50 BSC
(DD8) DFN 0509 REV C
0.889 ± 0.127
(.035 ± .005)
GAUGE PLANE
5.23
(.206)
MIN
0.42 ± 0.038
(.0165 ± .0015)
TYP
RECOMMENDED SOLDER PAD LAYOUT
NOTE:
1. DIMENSIONS IN MILLIMETER/(INCH)
2. DRAWING NOT TO SCALE
3. DIMENSION DOES NOT INCLUDE MOLD FLASH, PROTRUSIONS OR GATE BURRS.
MOLD FLASH, PROTRUSIONS OR GATE BURRS SHALL NOT EXCEED 0.152mm (.006") PER SIDE
4. DIMENSION DOES NOT INCLUDE INTERLEAD FLASH OR PROTRUSIONS.
INTERLEAD FLASH OR PROTRUSIONS SHALL NOT EXCEED 0.152mm (.006") PER SIDE
5. LEAD COPLANARITY (BOTTOM OF LEADS AFTER FORMING) SHALL BE 0.102mm (.004") MAX
3.20 – 3.45
(.126 – .136)
0.65
(.0256)
BSC
0.18
(.007)
0.254
(.010)
DETAIL “A”
0° – 6° TYP
DETAIL “A”
0.53 ± 0.152
(.021 ± .006)
SEATING
PLANE
3.00 ± 0.102
(.118 ± .004)
(NOTE 3)
4.90 ± 0.152
(.193 ± .006)
(.043)
0.22 – 0.38
(.009 – .015)
TYP
1.10
MAX
8
1 2
0.65
(.0256)
BSC
0.52
5
4
(.0205)
REF
3.00 ± 0.102
(.118 ± .004)
(NOTE 4)
0.86
(.034)
REF
0.1016 ± 0.0508
(.004 ± .002)
MSOP (MS8) 0307 REV F
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7
6
3
24
For more information www.linear.com/LTC6102
Page 25
LTC6102
LTC6102-1/LTC6102HV
revision hisTory
REV DATE DESCRIPTION PAGE NUMBER
D 8/10 Updated graph 21 8
E 6/14 Web Links Added
Correction to Output Current Absolute Maximum Ratings, (–1mA, +10mA) instead of (+1mA, –10mA)
Correction to Supply Current at V
(Revision history begins at Rev D)
+
=60V. Specification does not apply over the full operating temperature range
All
2
4
Information furnished by Linear Technology Corporation is believed to be accurate and reliable.
However, no responsibility is assumed for its use. Linear Technology Corporation makes no representation that the interconnection of its circuits as described herein will not infringe on existing patent rights.
6102fe
25
Page 26
LTC6102
LTC6102-1/LTC6102HV
Typical applicaTion
Remote Current Sense with Simple Noise Filter
+
R
SENSE
V
LOAD
–
R
IN
V
–
LTC6102
TIE AS CLOSE TO R
+
–
AS POSSIBLE
IN
6102 TA09
–INS+IN
–INF
V
V
OUT
+
REG
0.1µF
LONG WIRE
R
OUT
f
C
=
2 • π • R
C
OUT
1
• C
OUT
REMOTE ADC
OUT
ADC
relaTeD parTs
PART NUMBER DESCRIPTION COMMENTS
®
1636 Rail-to-Rail Input/Output, Micropower Op Amp VCM Extends 44V above VEE, 55µA Supply Current, Shutdown Function
LT
LT1637/LT1638/
Single/Dual/Quad, Rail-to-Rail, Micropower Op Amp V
LT1639
LT1787/LT1787HV Precision, Bidirectional, High Side Current Sense
Amplifier
LTC1921 Dual –48V Supply and Fuse Monitor ±200V Transient Protection, Drives Three Optoisolators for Status
LT1990 High Voltage, Gain Selectable Difference Amplifier ±250V Common Mode, Micropower, Pin Selectable Gain = 1, 10
LT1991 Precision, Gain Selectable Difference Amplifier 2.7V to ±18V, Micropower, Pin Selectable Gain = –13 to 14
LTC2050/LTC2051/
Single/Dual/Quad Zero-Drift Op Amp 3µV Offset, 30nV/°C Drift, Input Extends Down to V
LTC2052
LTC4150 Coulomb Counter/Battery Gas Gauge Indicates Charge Quantity and Polarity
LT6100 Gain-Selectable High Side Current Sense Amplifier 4.1V to 48V Operation, Pin-Selectable Gain: 10, 12.5, 20, 25, 40, 50V/V
LTC6101/
LTC6101HV
High Voltage High Side Current Sense Amplifier in
SOT-23
LTC6103 Dual High Side Precision Current Sense Amplifier 4V to 60V, Gain Configurable, 8-Pin MSOP
LTC6104 Bidirectional High Side Precision Current Sense
Amplifier
LT6105 Precision Rail-to-Rail Input Current Sense Amplifier Input V
LT6106 Low Cost, High Side Precision Current Sense
Amplifier
LT6107 High Temperature High Side Current Sense Amplifier
in SOT-23
Extends 44V above VEE, 0.4V/µs Slew Rate, >1MHz Bandwidth, <250µA
CM
Supply Current per Amplifier
2.7V to 60V Operation, 75µV Offset, 60µA Current Draw
–
4V to 60V/5V to 100V Operation, External Resistor Set Gain
4V to 60V, Gain Configurable, 8-Pin MSOP
Extends 44V Above and 0.3V Below V–, 2.85V to 36V Operation
CM
2.7V to 36V, Gain Configurable, SOT23
2.7V to 36V, Fully Tested at –55°C and 150°C
26
Linear Technology Corporation
1630 McCarthy Blvd., Milpitas, CA 95035-7417
(408) 432-1900 ● FAX: (408) 434-0507
For more information www.linear.com/LTC6102
●
www.linear.com/LTC6102
6102fe
LT 0614 REV E • PRINTED IN USA
LINEAR TECHNOLOGY CORPORATION 2007
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