Allows safe board insertion and removal from a live
backplane
Controls supply voltages from 3.15 V to 16.5 V
Precision current sense amplifier
Precision voltage input
12-bit ADC for current and voltage readback
Charge pumped gate drive for external N-channel FET
Adjustable analog current limit with circuit breaker
±3% accurate hot swap current limit level
Fast response limits peak fault current
Automatic retry or latch-off on current fault
Programmable hot swap timing via TIMER pin
Active-high ON pin
ALERTB output for overcurrent interrupt
2
C® fast mode-compliant interface (400 kHz maximum)
I
10-lead MSOP
APPLICATIONS
Power monitoring/power budgeting
Central office equipment
Telecommunication and data communication equipment
PCs/servers
GENERAL DESCRIPTION
The ADM1178 is an integrated hot swap controller and current
sense amplifier that offers digital current and voltage monitoring
via an on-chip, 12-bit analog-to-digital converter (ADC),
communicated through an I
An internal current sense amplifier senses voltage across the sense
resistor in the power path via the VCC pin and the SENSE pin.
2
C interface.
VCC
SENSE
ON
3.15V TO 16.5
ADM1178
FUNCTIONAL BLOCK DIAGRAM
ADM1178
MUX
V
A
CURRENT
SENSE
AMPLIFIER
1.3V
UV COMPARATOR
GND
R
ADM1178
ON
TIMER
Figure 2. Applications Diagram
SENSE
GND
0
I
1
SENSEVCC
GATE
ALERTB
12-BIT
ADC
ALERT
FET DRIVE
CONTROLLER
TIMER
Figure 1.
N-CHANNEL FET
SDA
SCL
ADR
CONTROLLER
SDA
SCL
INTERRUPT
2
C
I
P = VI
SDA
SCL
ADR
ALERTB
GATE
06048-001
06048-002
The ADM1178 limits the current through this resistor by controlling the gate voltage of an external N-channel FET in the power
path, via the GATE pin. The sense voltage (and, therefore, the
inrush current) is kept below a preset maximum.
The ADM1178 protects the external FET by limiting the time
that it spends with the maximum current running in it. This
current limit period is set by the choice of capacitor attached
to the TIMER pin. Additionally, the device provides protection
from overcurrent events that may occur after the hot swap event
is complete. In case of a short-circuit event, the current in the
sense resistor exceeds an overcurrent trip threshold, and the
FET is switched off immediately by pulling down the GATE pin.
Rev. 0
Information furnished by Analog Devices is believed to be accurate and reliable. However, no
responsibility is assumed by Anal og Devices for its use, nor for any infringements of p atents or other
rights ofthird partiesthatmay result fromits use. Specifications subject to change without notice. No
licenseis grantedby implication or otherwise under any patent or patent rights of Analog Devices.
Trademarks and registeredtrademarks arethe property of their respective owners.
A 12-bit ADC can measure the current seen in the sense
resistor, as well as the supply voltage on the VCC pin. An alert
output can be set to trigger when the ADC current reading
exceeds a programmed overcurrent limit threshold.
2
An industry-standard I
C interface allows a controller to read
current and voltage data from the ADC. Measurements can be
initiated by an I
2
C command. Alternatively, the ADC can run
continuously, and the user can read the latest conversion data
whenever it is required. Up to four unique I
2
C addresses can be
created, depending on the way the ADR pin is connected.
C Timing.................................................................... 16
2
C Bus............................... 16
REVISION HISTORY
9/06—Revision 0: Initial Version
Rev. 0 | Page 2 of 24
ADM1178
SPECIFICATIONS
VCC = 3.15 V to 16.5 V; TA = −40°C to +85°C; typical values at TA = 25°C, unless otherwise noted.
Table 1.
Parameter Min Typ Max Unit Conditions
VCC PIN
Operating Voltage Range, V
Supply Current, I
CC
Undervoltage Lockout, V
Undervoltage Lockout Hysteresis, V
VCC
UVLO
UVLOHYST
ON PIN
Input Current, I
INON
−2 +2 μA
Rising Threshold, V
Trip Threshold Hysteresis, V
ONTH
ONHYST
Glitch Filter Time 3 μs
ALERTB PIN
Output Low Voltage, V
ALERTOL
1 1.5 mA I
Input Current, I
ALERT
SENSE PIN
Input Leakage, I
Overcurrent Fault Timing Threshold, V
Overcurrent Limit Threshold, V
Fast Overcurrent Trip Threshold, V
SENSE
OCTIM
LIM
OCFAST
GATE PIN
Drive Voltage, V
GATE
Pull-Up Current 8 12.5 17 μA V
Pull-Down Current 1.5 mA V
5 mA V
7 mA V
TIMER PIN
Pull-Up Current (Power On Reset), I
Pull-Up Current (Fault Mode), I
Pull-Down Current (Retry Mode), I
Pull-Down Current, I
Trip Threshold H igh, V
Trip Threshold Low, V
100 μA Normal operation, V
TIMERDN
TIMERH
TIMERL
TIMERUPPOR
TIMERUPFAULT
TIMERDNRETRY
ADR PIN
Set Address to 00, V
Set Address to 01, R
Set Address to 10, I
Set Address to 11, V
Input Current for 11 Decode, I
Input Current for 00 Decode, I
ADRLOWV
ADRLOWZ
ADRHIGHZ
ADRHIGHV
ADRLOW
ADRHIGH
3.15 16.5 V
1.7 2.5 mA
2.8 V VCC rising
80 mV
−100
+100 nA ON < 1.5 V
1.26 1.3 1.34 V ON rising
35 50 65 mV
0.05 0.1 V I
−1 +1 μA V
−1 +1 μA V
92 mV
= −100 μA
ALERT
= −2 mA
ALERT
= VCC; ALERTB not asserted
ALERT
= V
SENSE
VCC
V
= (V
OCTRIM
VCC
− V
SENSE
TIMER pin
97 100 103 mV
V
= (V
− V
LIM
VCC
), closed-loop regulation to a
SENSE
current limit
115 mV
V
OCFAST
= (V
VCC
− V
SENSE
turned on
3 6 9 V V
9 11 13 V V
7 10 13 V V
−3.5 −5 −6.5 μA Initial cycle, V
GATE
GATE
GATE
GATE
GATE
GATE
GATE
− V
VCC
− V
VCC
− V
VCC
= 0 V
= 3 V, V
= 3 V, V
= 3 V, V
, V
, V
, V
VCC
VCC
VCC
VCC
VCC
VCC
TIMER
= 3.15 V
= 5 V
= 16.5 V
= 3.15 V
= 5 V
= 16.5 V
= 1 V
−40 −60 −80 μA During current fault, V
2 3 μA
After current fault and during a cool-down
period on a retry device, V
1.26 1.3 1.34 V TIMER rising
0.175 0.2 0.225 V TIMER falling
0 0.8 V Low state
135 150 165 kΩ
Resistor to ground state, load pin with specified
resistance for 01 decode
−1 +1 μA
Open state, maximum load allowed on ADR pin
for 10 decode
2 5.5 V High state
3 10 μA V
−40 −22 μA V
= 2.0 V to 5.5 V
ADR
= 0 V to 0.8 V
ADR
), fault timing starts on the
), gate pull-down current
= 1 V
TIMER
= 1 V
TIMER
= 1 V
TIMER
Rev. 0 | Page 3 of 24
ADM1178
Parameter Min Typ Max Unit Conditions
MONITORING ACCURACY1
Current Sense Absolute Accuracy −1.45
−1.8
−2.8
−5.7
−1.5
−1.8
−2.95
−6.1
−1.95
−2.45
−3.85
−6.7
V
for ADC Full Scale 105.84 mV
SENSE
Voltage Sense Accuracy −0.85
−0.9 +0.9 %
−0.85
−0.9 +0.9 %
−0.9
−1.15 +1.15 %
VCC for ADC Full Scale,
6.65 V
Low Range (VRANGE = 1)
VCC for ADC Full Scale,
26.35 V
High Range (VRANGE = 0)
I2C TIMING
Low Level Input Voltage, V
High Level Input Voltage, V
Low Level Output Voltage on SDA, V
Output Fall Time on SDA from V
Maximum Width of Spikes Suppressed by
Input Filtering on SDA and SCL Pins
Input Current, II, on SDA/SCL When Not
Driving Out a Logic Low
0.3 V
IL
0.7 V
IH
0.4 V I
OL
to V
IHMIN
ILMAX
V
BUS
20 +
0.1 C
250 ns CB = bus capacitance from SDA to GND
B
50 250 ns
−10 +10 μA
Input Capacitance on SDA/SCL 5 pF
SCL Clock Frequency, f
400 kHz
SCL
Low Period of the SCL Clock 600 ns
High Period of the SCL Clock 1300 ns
+1.45 % V
+1.8 % V
+2.8 % V
+5.7 % V
+1.5 % V
+1.8 % V
+2.95 % V
+6.1 % V
+1.95 % V
+2.45 % V
+3.85 % V
+6.7 % V
+0.85 %
+0.85 %
+0.9 %
V
BUS
= 75 mV 0°C to +70°C
SENSE
= 50 mV 0°C to +70°C
SENSE
= 25 mV 0°C to +70°C
SENSE
= 12.5 mV 0°C to +70°C
SENSE
= 75 mV 0°C to +85°C
SENSE
= 50 mV 0°C to +85°C
SENSE
= 25 mV 0°C to +85°C
SENSE
= 12.5 mV 0°C to +85°C
SENSE
= 75 mV −40°C to +85°C
SENSE
= 50 mV −40°C to +85°C
SENSE
= 25 mV −40°C to +85°C
SENSE
= 12.5 mV −40°C to +85°C
SENSE
This is an absolute value to be used when
converting ADC codes to current readings;
any inaccuracy in this value is factored into
absolute current accuracy values (see specs
for Current Sense Absolute Accuracy)
VCC = 3 V minimum
0°C to +70°C
(low range)
= 6 V minimum
V
CC
0°C to +70°C
(high range)
VCC = 3 V minimum
0°C to +85°C
(low range)
= 6 V minimum
V
CC
0°C to +85°C
(high range)
VCC = 3 V minimum
−40°C to +85°C
(low range)
= 6 V minimum
V
CC
−40°C to +85°C
(high range)
These are absolute values to be used when
converting ADC codes to voltage readings;
any inaccuracy in these values is factored into
voltage accuracy values (see specs for Voltage
Accuracy)
= 3 mA
OL
Rev. 0 | Page 4 of 24
ADM1178
Parameter Min Typ Max Unit Conditions
Setup Time for a Repeated Start Condition,
t
SU;STA
SDA Output Data Hold Time, t
Setup Time for a Stop Condition, t
HD;DAT
SU;STO
Bus Free Time Between a Stop and a Start
Condition, t
BUF
Capacitive Load for Each Bus Line 400 pF
1
Monitoring accuracy is a measure of the error in a code that is read back for a particular voltage/current. This is a combination of amplifier error, reference error, ADC
error, and error in ADC full-scale code conversion factor.
600 ns
100 900 ns
600 ns
1300 ns
Rev. 0 | Page 5 of 24
ADM1178
ABSOLUTE MAXIMUM RATINGS
Table 2.
Parameter Rating
VCC Pin 20 V
SENSE Pin 20 V
TIMER Pin −0.3 V to +6 V
ON Pin −0.3 V to +20 V
ALERTB Pin 30 V
GATE Pin 30 V
SDA Pin, SCL Pin −0.3 V to +6 V
ADR Pin −0.3 V to +7 V
Storage Temperature Range −65°C to +125°C
Operating Temperature Range −40°C to +85°C
Lead Temperature Range (Soldering, 10 sec) 300°C
Junction Temperature 150°C
Stresses above those listed under Absolute Maximum Ratings
may cause permanent damage to the device. This is a stress
rating only; functional operation of the device at these or any
other conditions above those indicated in the operational
section of this specification is not implied. Exposure to absolute
maximum rating conditions for extended periods may affect
device reliability.
Table 3. Thermal Resistance
Package Type θ
10-Lead MSOP 137.5 °C/W
JA
Unit
ESD CAUTION
Rev. 0 | Page 6 of 24
ADM1178
PIN CONFIGURATION AND FUNCTION DESCRIPTIONS
1
VCC
SENSE
2
ADM1178
ON
3
TOP VIEW
(Not to Scale)
GND
4
5
TIMER
Figure 3. Pin Configuration
Table 4. Pin Function Descriptions
Pin No. Mnemonic Description
1 VCC
Positive Supply Input Pin. The operating supply voltage range is from 3.15 V to 16.5 V. An undervoltage
lockout (UVLO) circuit resets the ADM1178 when a low supply voltage is detected.
2 SENSE
Current Sense Input Pin. A sense resistor between the VCC pin and the SENSE pin sets the analog current
limit. The hot swap operation of the ADM1178 controls the external FET gate to maintain the (V
voltage at 100 mV or below.
3 ON
Undervoltage Input Pin. Active high pin. An internal ON comparator has a trip threshold of 1.3 V, and the
output of this comparator is used as an enable for the hot swap operation. With an external resistor divider
from VCC to GND, this pin can be used to enable the hot swap operation on a specific voltage on VCC, giving
an undervoltage function.
4 GND Chip Ground Pin.
5 TIMER
Timer Pin. An external capacitor, C
TIMER
The GATE pin turns off when the TIMER pin is pulled beyond the upper threshold. An overvoltage detection
with an external Zener can be used to force this pin high.
6 SCL I2C Clock Pin. Open-drain input requires an external resistive pull-up.
7 SDA I2C Data I/O Pin. Open-drain input/output. Requires an external resistive pull-up.
8 ADR
9 GATE
2
C Address Pin. This pin can be tied low, tied high, left floating, or tied low through a resistor to set four
I
different I
2
C addresses.
GATE Output Pin. This pin is the high-side gate drive of an external N-channel FET. This pin is driven by the
FET drive controller, which utilizes a charge pump to provide a 12.5 μA pull-up current to charge the FET
GATE pin. The FET drive controller regulates to a maximum load current (100 mV through the sense resistor)
by modulating the GATE pin.
10 ALERTB
Alert Output Pin. Active-low, open-drain configuration. This pin asserts when an overcurrent condition is
present. The overcurrent level that causes an alert to be asserted is digitally programmable via the I
interface. This function can also be enable/disabled via I
10
ALERTB
GATE
9
ADR
8
SDA
7
6
SCL
06048-003
− V
SENSE
)
VCC
, sets a 270 ms/μF initial timing cycle delay and a 21.7 ms/μF fault delay.
2
2
C.
C
Rev. 0 | Page 7 of 24
ADM1178
TYPICAL PERFORMANCE CHARACTERISTICS
2.0
1.8
1.6
1.4
1.2
1.0
(mA)
CC
I
0.8
0.6
0.4
0.2
0
02468101411216
VCC (V)
Figure 4. Supply Current vs. Supply Voltage
8
06048-021
2.0
1.8
1.6
1.4
1.2
1.0
(mA)
CC
I
0.8
0.6
0.4
0.2
0
–40806040200–20
TEMPERATURE (°C)
Figure 7. Supply Current vs. Temperature (Gate On)
06048-022
12
10
8
6
DRIVE VOLTAGE (V)
4
2
0
01
Figure 5. Drive Voltage (V
0
–2
–4
–6
(µA)
–8
GATE
I
–10
VCC (V)
− VCC) vs. Supply Voltage
GATE
8161412108642
06048-029
12
10
8
6
DRIVE VOLTAGE (V)
4
2
0
–40806040200–20
Figure 8. Drive Voltage (V
0
–2
–4
–6
(µA)
–8
GATE
I
–10
5V VIN
3.15V VIN
TEMPERATURE (°C)
− VCC) vs. Temperature
GATE
06048-030
–12
–14
01
VCC (V)
101216148642
8
06048-027
Figure 6. Gate Pull-Up Current vs. Supply Voltage
–12
–14
–40806040200–20
Figure 9. Gate Pull-Up Current vs. Temperature
Rev. 0 | Page 8 of 24
TEMPERATURE (°C)
06048-028
ADM1178
12
10
8
(mA)
6
GATE
I
4
2
0
01
Figure 10. Gate Pull-Down Current vs. V
VCC (V)
CC
at V
GATE
161412108642
8
06048-031
= 5 V
2.0
1.8
1.6
1.4
1.2
1.0
0.8
0.6
TIMER THRES HO LD (V)
0.4
0.2
0
018101216148642
HIGH
LOW
VCC (V)
06048-038
Figure 13. Timer Threshold vs. Supply Voltage
2
0
–2
–4
(µA)
–6
GATE
I
–8
–10
–12
–14
01
V
GATE
(V)
Figure 11. Gate Pull-Up Current vs. Gate Voltage at V
20
15
(mA)
10
GATE
I
5
VCC = 3V
0
02
V
V
CC
GATE
V
CC
= 5V
(V)
= 12V
1412108642
6
06048-040
= 5 V
CC
2015105
5
06048-043
Figure 12. Gate Pull-Down Current vs. Gate Voltage
2.0
1.8
1.6
1.4
1.2
1.0
0.8
0.6
TIMER HIG H THRESHOLD (V)
0.4
0.2
0
–4080
Figure 14. Timer Threshold vs. Temperature
100
90
80
70
60
50
40
GATE ON TIME (ms)
30
20
10
0
05.04.54.03.53.02.52.01.51.00.5
Figure 15. Current Limit On Time vs. Timer Capacitance
HIGH
LOW
TEMPERATURE (°C)
C
(µF)
TIMER
6040200–20
06048-039
06048-050
Rev. 0 | Page 9 of 24
ADM1178
0
0
–1
–2
(µA)
–3
TIMER
I
–4
–5
–6
018
VCC (V)
101216148642
06048-032
Figure 16.Timer Pull-Up Current (Initial Cycle) vs. Supply Voltage
0
–10
–20
–30
(µA)
–40
TIMER
I
–50
–60
–1
–2
(µA)
–3
TIMER
I
–4
–5
–6
–40806040200–20
Figure 19. Timer Pull-Up Current (Initial Cycle) vs. Temperature
0
–10
–20
–30
(µA)
–40
TIMER
I
–50
–60
TEMPERATURE (°C)
06048-033
–70
–80
018
VCC (V)
101216148642
06048-034
Figure 17. Timer Pull-Up Current (C. B. Delay) vs. Supply Voltage
3.0
2.5
2.0
(µA)
1.5
TIMER
I
1.0
0.5
0
018101216148642
VCC (V)
06048-036
Figure 18. Timer Pull-Down Current (Cool-Off Cycle) vs. Supply Voltage
–70
–80
–40806040200–20
Figure 20. Timer Pull-Up Current (C. B. Delay) vs. Temperature
3.0
2.5
2.0
(µA)
1.5
TIMER
I
1.0
0.5
0
–40806040200–20
Figure 21. Timer Pull-Down Current (Cool-Off Cycle) vs. Temperature
TEMPERATURE (°C)
TEMPERATURE (°C)
06048-035
06048-037
Rev. 0 | Page 10 of 24
ADM1178
120
115
110
105
(mV)
100
LIM
V
95
90
85
80
21
VCC (V)
8
16141210864
06048-041
Figure 22. Circuit Breaker Limit Voltage vs. Supply Voltage
110
108
106
104
102
100
V (mV)
98
96
94
92
90
–40806040200–20
Figure 23. V
V
OCFAST
V
LIM
V
OCTIM
TEMPERATURE (°C)
, V
, V
OCTIM
LIM
OCFAST
vs. Temperature
06048-042
1000
900
800
700
600
500
400
300
HITS PER CO DE (1000 RE ADS)
200
100
0
20472048204920502046
CODE
Figure 25. ADC Noise, Current Channel, Midcode Input, 1000 Reads
1000
900
800
700
600
500
400
300
HITS PER CO DE (1000 RE ADS)
200
100
0
780781782783779
CODE
Figure 26. ADC Noise, 14:1 Voltage Channel, 5 V Input, 1000 Reads
06048-060
06048-061
11 DECODE10 DECODE01 DECODE 00 DECODE
3.2
3.0
2.8
2.6
2.4
2.2
2.0
1.8
1.6
ADR
V
1.4
1.2
1.0
0.8
0.6
0.4
0.2
0
–35–30–25–20–15–10–50510
I
ADR
(µA)
Figure 24. Address Pin Voltage vs. Address Pin Current
for Four Addressing Options
06048-026
Rev. 0 | Page 11 of 24
1000
900
800
700
600
500
400
300
HITS PER CO DE ( 1000 RE ADS)
200
100
0
30793080308130823078
CODE
Figure 27. ADC Noise, 7:1 Voltage Channel, 5 V Input, 1000 Reads
06048-062
ADM1178
4
3
2
1.0
0.8
INL (LSB)
DNL (LSB)
1
0
–1
–2
–3
–4
040002500 3000 3500200015001000500
4
3
2
1
0
–1
–2
–3
–4
040002500 3000 3500200015001000500
CODE
Figure 28. INL for ADC
CODE
Figure 29. DNL for ADC
0.6
0.4
OUTPUT LOW (V)
0.2
0
211514131211109876543
06048-023
VCC (V)
6
06048-048
Figure 31. Output Low Voltage vs. Supply @ 1 mA
2.0
1.8
1.6
1.4
1.2
1.0
0.8
OUTPUT LOW (V)
0.6
0.4
0.2
0
032.82.62.42.22.01.81.61.41.21.00.80.60.40.2
06048-024
LOAD CURRENT (mA)
.0
06048-049
Figure 32. Output Low Voltage vs. Load Current
0.60
0.55
0.50
0.45
0.40
0.35
0.30
0.25
ALERTB LO W ( V)
0.20
0.15
0.10
0.05
0
–40806040200–20
TEMPERATURE (°C)
06048-047
Figure 30. Output Low Voltage vs. Temperature @ 1 mA
Rev. 0 | Page 12 of 24
ADM1178
OVERVIEW OF THE HOT SWAP FUNCTION
When circuit boards are inserted into a live backplane, discharged
supply bypass capacitors draw large transient currents from the
backplane power bus as they charge. Such transient currents can
cause permanent damage to connector pins, as well as dips on
the backplane supply that can reset other boards in the system.
The ADM1178 is designed to turn a circuit board supply
voltage on and off in a controlled manner, allowing the circuit
board to be safely inserted into or removed from a live backplane.
The ADM1178 can reside either on the backplane or on the
circuit board itself.
The ADM1178 controls the inrush current to a fixed maximum
level by modulating the gate of an external N-channel FET placed
between the live supply rail and the load. This hot swap function
protects the card connectors and the FET itself from damage
and limits any problems that may be caused by the high current
loads on the live supply rail.
The ADM1178 holds the GATE pin down (and, thus, the FET is
held off) until a number of conditions are met. An undervoltage
lockout circuit ensures that the device is provided with an adequate
input supply voltage. Once this has been successfully detected,
the device goes through an initial timing cycle to provide a delay
before it attempts to hot swap. This delay ensures that the board is
fully seated in the backplane before the board is powered up.
Once the initial timing cycle is complete, the hot swap function
is switched on under control of the ON pin. When the ON pin
is asserted high, the hot swap operation starts.
The ADM1178 charges up the gate of the FET to turn on the
load. It continues to charge up the GATE pin until the linear
current limit (set to 100 mV/R
) is reached. For some
SENSE
combinations of low load capacitance and high current limit,
this limit may not be reached before the load is fully charged up.
If current limit is reached, the ADM1178 regulates the GATE
pin to keep the current at this limit. For currents above the
overcurrent fault timing threshold, nominally 100 mV/R
SENSE
,
the current fault is timed by sourcing a current out to the
TIMER pin. If the load becomes fully charged before the fault
current limit time is reached (when the TIMER pin reaches
1.3 V), the current drops below the overcurrent fault timing
threshold. The ADM1178 then charges the GATE pin higher
to fully enhance the FET for lowest R
, and the TIMER pin
ON
is pulled down again.
The ADM1178-1 retries the hot swap operation indefinitely,
keeping the FET in its safe operating area (SOA) by using the
TIMER pin to time a cool-down period between hot swap
attempts. The current and voltage threshold combinations
on the TIMER pin set the retry duty cycle to 3.8%.
The ADM1178 is designed to operate over a range of supplies
from 3.15 V to 16.5 V.
UNDERVOLTAGE LOCKOUT
An internal undervoltage lockout (UVLO) circuit resets the
ADM1178 if the VCC
supply is too low for normal operation.
The UVLO has a low-to-high threshold of 2.8 V, with 80 mV
hysteresis. Above 2.8 V supply voltage, the ADM1178 starts the
initial timing cycle.
ON FUNCTION
The ADM1178 has an active-high ON pin. The ON pin is the
input to a comparator that has a low-to-high threshold of 1.3 V,
an 50 mV hysteresis, and a glitch filter of 3 s. A low input on
the ON pin turns off the hot swap operation by pulling the
GATE pin to ground, turning off the external FET. The TIMER
pin is also reset by turning on a pull-down current on this pin.
A low-to-high transition on the ON pin starts the hot swap
operation. A 10 k pull-up resistor connecting the ON pin to
the supply is recommended.
Alternatively, an external resistor divider at the ON pin can be
used to program an undervoltage lockout value higher than the
internal UVLO circuit, thereby setting a voltage level at the
VCC supply, where the hot swap operation is to start. An RC
filter can be added at the ON pin to increase the delay time at
card insertion if the initial timing cycle delay is insufficient.
TIMER FUNCTION
The TIMER pin handles several timing functions with an
external capacitor, C
V
(0.2 V) and V
TIMERH
sources are a 5 µA pull-up, a 60 µA pull-up, a 2 µA pull-down,
and a 100 µA pull-down. The 100 µA pull-down is a non-ideal
current source, approximating a 7 k resistor below 0.4 V.
These current and voltage levels, together with the value of C
chosen by the user, determine the initial timing cycle time, the
fault current limit time, and the hot swap retry duty cycle.
. There are two comparator thresholds:
TIMER
(1.3 V). The four timing current
TIMERL
TIMER
If the fault current limit time is reached before the load drops
below the current limit, a fault has been detected, and the hot
swap operation is aborted by pulling down on the GATE pin to
turn off the FET. The ADM1178-2 is latched off at that point
and attempts to hot swap again only when the ON pin is deasserted
and then asserted again.
Rev. 0 | Page 13 of 24
ADM1178
GATE AND TIMER FUNCTIONS DURING
A HOT SWAP
During hot insertion of a board onto a live supply rail at VCC,
the abrupt application of supply voltage charges the external
FET drain/gate capacitance, which can cause an unwanted gate
voltage spike. An internal circuit holds GATE low before the
internal circuitry wakes up. This reduces the FET current surges
substantially at insertion. The GATE pin is also held low during
the initial timing cycle and until the ON pin has been taken
high to start the hot swap operation.
During hot swap operation, the GATE pin is first pulled up by
a 12 A current source. If the current through the sense resistor
reaches the overcurrent fault timing threshold, V
current of 60 µA on the TIMER pin, is turned on; and this pin
starts charging up. At a slightly higher voltage in the sense resistor, the error amplifier servos the GATE pin to maintain a constant
current to the load by controlling the voltage across the sense
resistor to the linear current limit, V
LIM
.
A normal hot swap is complete when the board supply capacitors
near full charge and the current through the sense resistor
drops to eventually reach the level of the board load current.
As soon as the current drops below the overcurrent fault timing
threshold, the current into the TIMER pin switches from being
a 60 A pull-up to being a 100 A pull-down. The ADM1178
then drives the GATE voltage as high as it can to fully enhance
the FET and reduce R
losses to a minimum.
ON
A hot swap fails if the load current does not drop below the
overcurrent fault timing threshold, V
, before the TIMER
OCTIM
pin has charged up to 1.3 V. In this case, the GATE pin is then
pulled down with a 2 mA current sink. The GATE pull-down
stays on until a hot swap retry starts, which can be forced by
deasserting and then re-asserting the ON pin. On the ADM1178-1,
the device retries automatically after a cool-down period.
The ADM1178 also features a method of protection from
sudden load current surges, such as a low impedance fault,
when the current seen across the sense resistor may go well
beyond the linear current limit. If the fast overcurrent trip
threshold, V
, is exceeded, the 2 mA GATE pull-down is
OCFAST
turned on immediately. This pulls the GATE voltage down
quickly to enable the ADM1178 to limit the length of the
current spike that gets through and also to bring the current
through the sense resistor back into linear regulation as quickly
as possible. This process protects the backplane supply from
sustained overcurrent conditions that may otherwise cause the
backplane supply to droop during the overcurrent event.
OCTIM
, a pull-up
CALCULATING CURRENT LIMITS AND FAULT
CURRENT LIMIT TIME
The nominal linear current limit is determined by a sense
resistor connected between the VCC pin and the SENSE pin,
as given by the Equation 1.
I
LIMIT(NOM)
= V
LIM(NOM)/RSENSE
= 100 mV/R
SENSE
(1)
The minimum linear fault current is given by Equation 2.
I
LIMIT(MIN)
= V
LIM(MIN)/RSENSE(MAX)
= 90 mV/R
SENSE(MAX)
(2)
The maximum linear fault current is given by Equation 3.
I
LIMIT(MAX)
= V
LIM(MAX)/RSENSE(MIN)
= 110 mV/R
SENSE(MIN)
(3)
The power rating of the sense resistor should be rated at the
maximum linear fault current level.
The minimum overcurrent fault timing threshold current is
given by Equation 4.
I
OCTIM(MIN)
= V
OCTIM(MIN)/RSENSE(MAX)
= 85 mV/R
SENSE(MAX)
(4)
The maximum fast overcurrent trip threshold current is given
by Equation 5.
I
OCFAST(MAX)
= V
OCFAST(MAX)/RSENSE(MIN)
= 115 mV/R
SENSE(MIN)
(5)
The fault current limit time is the time that a device spends
timing an overcurrent fault and is given by Equation 6.
t
FAULT
≈ 21.7 × C
ms/F (6)
TIMER
INITIAL TIMING CYCLE
When VCC is first connected to the backplane supply, the
internal supply (Time Point (1) in
must be charged up. A very short time later (significantly less
than 1 ms), the internal supply is fully up and, because the
undervoltage lockout voltage has been exceeded at VCC, the
device comes out of reset. During this first short reset period,
the GATE pin is held down with a 25 mA pull-down current,
and the TIMER pin is pulled down with a 100 A current sink.
The ADM1178 then goes through an initial timing cycle. At
Time Point (2), the TIMER pin is pulled high with 5 µA. At
Time Point (3), the TIMER reaches the V
the first portion of the initial cycle ends. The 100 µA current
source then pulls down the TIMER pin until it reaches 0.2 V at
Time Point (4). The initial cycle delay (Time Point (2) to Time
Point (4)) is related to C
≈ 270 × C
t
INITIAL
TIMER
ms/F (7)
TIMER
Figure 33) of the ADM1178
threshold, and
TIMERL
by Equation 7.
Rev. 0 | Page 14 of 24
ADM1178
When the initial timing cycle terminates, the device is ready to
start a hot swap operation (assuming the ON pin is asserted).
In the example shown in
Figure 33, the ON pin was asserted at
the same time as VCC was applied, so the hot swap operation
starts immediately after Time Point (4). At this point the FET
gate is charged up with a 12 A current source.
At Time Point (5), the threshold voltage of the FET is reached
and the load current begins to flow. The FET is controlled to
keep the sense voltage at 100 mV (this corresponds to a
maximum load current level defined by the value of R
At Time Point (6), V
GATE
and V
have reached their full
OUT
SENSE
).
potential, and the load current has settled to its nominal level.
Figure 34 illustrates the situation where the ON pin is asserted
after V
is applied.
CC
(1)
(2)(3)(4)(5)(6)
V
VCC
V
ON
V
TIMER
V
GATE
V
SENSE
V
OUT
INITIAL TIMING
CYCLE
Figure 33. Startup (ON Asserts as Power Is Applied)
06048-004
(1)(2)(3)(4)(5)(6)(7)
V
VCC
V
ON
V
TIMER
V
GATE
V
SENSE
V
OUT
INITIAL TIMING
CYCLE
06048-005
Figure 34. Startip (ON Asserts After Power Is Applied)
HOT SWAP RETRY CYCLE ON THE ADM1178-1
With the ADM1178-1, the device turns off the FET after an
overcurrent fault and then uses the TIMER pin to time a delay
before automatically retrying to hot swap.
As with all ADM1178 devices, on overcurrent fault is timed by
charging the TIMER cap with a 60 A pull-up current. When
the TIMER pin reaches 1.3 V, the fault current limit time has
been reached, and the GATE pin is pulled down. On the
ADM1178-1, the TIMER pin is then pulled down with a 2 A
current sink. When the TIMER pin reaches 0.2 V, it automatically restarts the hot swap operation.
The cool-down period is related to C
t
COOL
≈ 550 × C
ms/F (8)
TIMER
Thus, the retry duty cycle is given by Equation 9.
by Equation 8.
TIMER
Rev. 0 | Page 15 of 24
t
FAULT
/(t
COOL
+ t
) × 100% = 3.8% (9)
FAULT
ADM1178
VOLTAGE AND CURRENT READBACK
In addition to providing hot swap functionality, the ADM1178
also contains the components to allow voltage and current
readback over an Inter-IC (I
current sense amplifier and the voltage on the VCC pin are fed
into a 12-bit ADC via a multiplexer. The device can be instructed
to convert voltage and/or current at any time during operation
2
via an I
C command. When all conversions are complete, the
voltage and/or current values can be read out to 12-bit accuracy
in two or three bytes.
SERIAL BUS INTERFACE
Control of the ADM1178 is carried out via the I2C bus. This
interface is compatible with I
The ADM1178 is connected to this bus as a slave device, under
the control of a master device.
IDENTIFYING THE ADM1178 ON THE I2C BUS
The ADM1178 has a 7-bit serial bus slave address. When the
device powers up, it does so with a default serial bus address.
The three MSBs of the address are set to 111, and the two MSBs
are set to 10, giving an address of 111x10. Bit A2 and Bit A3 are
determined by the state of the ADR pin. There are four different
configurations available on the ADR pin that correspond to
four different I
2
C addresses for these bits (see Table 5 ). This
scheme allows four ADM1178 devices to operate on a single
2
I
C bus.
2
Table 5. Setting I
ADR Configuration Address
Low state 0xE4
Resistor to GND 0xEC
Floating (unconnected) 0xF4
High state 0xFC
C Addresses via the ADR Pin
GENERAL I2C TIMING
Figure 35 and Figure 36 show timing diagrams for general read
and write operations using the I
conditions for different types of read and write operations, which
are discussed later. The general I
1. The master initiates data transfer by establishing a start
condition, defined as a high-to-low transition on the serial
data line, SDA, while the serial clock line, SCL, remains
high. This indicates that a data stream follows.
2
C) bus. The voltage output of the
2
C fast mode (400 kHz maximum).
2
C. The I2C specification defines
2
C protocol operates as follows:
All slave peripherals connected to the serial bus respond to
the start condition and shift in the next eight bits, consisting
of a 7-bit slave address (MSB first), plus an R/
W
bit that
determines the direction of the data transfer; that is,
whether data is written to or read from the slave device (0
= write, 1 = read).
The peripheral whose address corresponds to the transmitted
address responds by pulling the data line low during the
low period before the ninth clock pulse, known as the
acknowledge bit, and holding it low during the high period
of this clock pulse. All other devices on the bus remain
idle, while the selected device waits for data to be read
from it or written to it. If the R/
writes to the slave device. If the R/
W
bit is 0, the master
W
bit is 1, the master
reads from the slave device.
2. Data is sent over the serial bus in sequences of nine clock
pulses: eight bits of data followed by an acknowledge bit
from the slave device. Data transitions on the data line
must occur during the low period of the clock signal and
remain stable during the high period because a low-tohigh transition when the clock is high can be interpreted as
a stop signal.
If the operation is a write operation, the first data byte after
the slave address is a command byte. This tells the slave
device what to expect next. It can be an instruction, such
as telling the slave device to expect a block write; or it can
be a register address that tells the slave where subsequent
data is to be written.
Because data can flow in only one direction, as defined by
W
the R/
bit, it is not possible to send a command to a slave
device during a read operation. Before doing a read operation,
it may first be necessary to do a write operation to tell the
slave what sort of read operation to expect and/or the
address from which data is to be read.
3. When all data bytes have been read or written, stop
conditions are established. In write mode, the master pulls
the data line high during the 10th clock pulse to assert
a stop condition. In read mode, the master device releases
the SDA line during the low period before the ninth clock
pulse, but the slave device does not pull it low. This is known as
a no acknowledge. The master then takes the data line low
during the low period before the 10th clock pulse, then high
during the 10th clock pulse to assert a stop condition.
Rev. 0 | Page 16 of 24
ADM1178
SCL
SDA
START BY MAST E R
SCL
(CONTINUED)
SDA
(CONTINUED)
SCL
SDA
START BY MAST E R
SCL
(CONTINUED)
SDA
(CONTINUED)
9
SLAVE
SLAVE
9
SLAVE
MASTER
1
D6
D7
9
2
C Write Timing Diagram
1
D7
9
2
C Read Timing Diagram
D5
1
D6
D5
1
D4
COMMAND CODE
D4
DATA BYTE
D3
FRAME 2
D3
FRAME 2
D2D1
D2D1
ACKNOWLEDGE BY
FRAME N
DATA BYTE
ACKNOWLEDGE BY
FRAME N
DATA BYTE
D0
SLAVE
D0
MASTER
1
0
0
11
FRAME 1
SLAVE ADDRESS
1
D7D6D5D4D3D2D1D0D7D6D5D4D3D2D1D0
A1A0 R/W
1
FRAME 3
DATA BYTE
ACKNOWLEDG E BY
ACKNOWLEDGE BY
Figure 35. General I
1
0
0
11
FRAME 1
SLAVE ADDRESS
1
D7D6D5D4D3D2D1D0D7D6D5D4D3D2D1D0
A1A0 R/W
1
FRAME 3
DATA BYTE
ACKNOWLEDG E BY
ACKNOWLEDGE BY
Figure 36. General I
9
9
ACKNOWLEDG E BY
SLAVE
9
9
NO ACKNOWLEDGE
STOP
BY
MASTER
STOP
BY
MASTER
06048-006
06048-007
t
SU;STA
t
HD;STA
t
SU;STO
P
06048-008
SCLSCL
SDA
t
LOW
t
HD;STA
t
BUF
S
P
t
t
HD;DAT
HIGH
t
F
t
SU;DAT
S
R
t
Figure 37. Serial Bus Timing Diagram
Rev. 0 | Page 17 of 24
ADM1178
WRITE AND READ OPERATIONS
The I2C specification defines several protocols for different
types of read and write operations. The operations used in the
ADM1178 are discussed in the sections that follow.
Tabl e 6
shows the abbreviations used in the command diagrams.
Table 6. I
2
C Abbreviations
AbbreviationCondition
SStart
PStop
RRead
WWrite
AAcknowledge
N No acknowledge
QUICK COMMAND
The quick command operation allows the master to check if the
slave is present on the bus, as follows:
1. The master device asserts a start condition on SDA.
2. The master sends the 7-bit slave address, followed by the
write bit (low).
3. The addressed slave device asserts an acknowledge on SDA.
12 3
SLAVE
S
ADDRESS
Figure 38. Quick Command
WA
06048-009
WRITE COMMAND BYTE
In the write command byte operation, the master device sends
a command byte to the slave device, as follows:
1. The master device asserts a start condition on SDA.
2. The master sends the 7-bit slave address, followed by the
write bit (low).
3. The addressed slave device asserts an acknowledge on SDA.
4. The master sends the command byte. The command byte
is identified by an MSB =0. An MSB =1 indicates an
extended register write (see the
section.)
5. The slave asserts an acknowledge on SDA.
6. The master asserts a stop condition on SDA to end the
transaction.
12 3 456
SLAVE
S
ADDRESS
Figure 39. Write Command Byte
WA
The seven LSBs of the command byte are used to configure and
control the ADM1178.
Tabl e 7 provides details of the function
of each bit.
Write Extended Byte
COMMAND
BYTE
AP
06048-010
Table 7. Command Byte Operations
Bit Default Name Function
C00V_CONT
Set to convert voltage continuously. If readback is attempted before the first conversion is complete, the
ADM1178 asserts an acknowledge and returns all 0s in the returned data.
C1 0V_ONCE
Set to convert voltage once. Self-clears. I2C asserts a no acknowledge on attempted reads until the ADC
conversion is complete.
C20I_CONT
Set to convert voltage continuously. If readback is attempted before the first conversion is complete, the
ADM1178 asserts an acknowledge and returns all 0s in the returned data.
C30 I_ONCE
Set to convert current once. Self-clears. I2C asserts a no acknowledge on attempted reads until the ADC
conversion is complete.
C40VRANGE
Selects different internal attenuation resistor networks for voltage readback. A 0 in C4 selects a 14:1 voltage
divider. A 1 in C4 selects a 7:2 voltage divider. With an ADC full scale of 1.902 V, the voltage at the VCC pin for
an ADC full-scale result is 26.35 V for VRANGE = 0 and 6.65 V for VRANGE = 1.
C50N/AUnused.
C60STATUS_RD
Status read. When this bit is set, the data byte read back from the ADM1178 is the STATUS byte. This contains
the status of the device alerts. See
Table 15 for full details of the STATUS byte.
Rev. 0 | Page 18 of 24
ADM1178
WRITE EXTENDED BYTE
In the write extended byte operation, the master device writes
to one of the three extended registers of the slave device, as follows:
1. The master device asserts a start condition on SDA.
2. The master sends the 7-bit slave address, followed by the
write bit (low).
3. The addressed slave device asserts an acknowledge on SDA.
7. The slave asserts an acknowledge on SDA.
8. The master asserts a stop condition on SDA to end the
transaction.
12 345678
S
ADDRESS
SLAVE
REGISTER
WA
ADDRESS
Figure 40. Write Extended Byte
REGISTER
A
DATA
AP
06048-011
4. The master sends the register address byte. The MSB of
this byte is set to 1 to indicate an extended register write.
Tabl e 9, Ta b le 1 0, and Tab l e 1 1 give details of each extended
register.
The two LSBs indicate which of the three extended registers
are written to (see
Tabl e 8). All other bits should be set to 0.
Table 8. Extended Register Addresses
A6 A5 A4 A3 A2 A1 A0 Extended Register
5. The slave asserts an acknowledge on SDA.
6. The master sends the command byte. The command byte
is identified by an MSB = 0. An MSB = 1 indicates an
0000001ALERT_EN
0000010ALERT_TH
0000011CONTROL
extended register write.
Table 9. ALERT_EN Register Operations
Bit Default Name Function
0 0 EN_ADC_OC1
Enabled if a single ADC conversion on the I channel has exceeded the threshold set in the ALERT_TH
register.
1 0 EN_ADC_OC4
Enabled if four consecutive ADC conversions on the I channel have exceeded the threshold set in the
ALERT_TH register.
2 1 EN_HS_ALERT
Enabled if the hot swap has either latched off or entered a cool-down cycle because of an overcurrent
event.
3 0 EN_OFF_ALERT
Enables an alert if the HS operation is turned off by a transition that deasserts the ON pin or by an
operation that writes the SWOFF bit high.
4 0 CLEAR
Clears the ON_ALERT, HS_ALERT, and ADC_ALERT status bits in the STATUS register. These may
immediately reset if the source of the alert has not been cleared or disabled with the other bits in this
register. This bit self-clears to 0 after the STATUS register bits have been cleared.
Table 10. ALERT_TH Register Operations
Bit Default Function
7:0 FF
The ALERT_TH register sets the current level at which an alert occurs. Defaults to ADC full scale. The ALERT_TH 8-bit
number corresponds to the top eight bits of the current channel data.
Table 11. CONTROL Register Operations
Bit Default Name Function
0 0 SWOFF Forces hot swap off. Equivalent to deasserting the ON pin.
Rev. 0 | Page 19 of 24
ADM1178
READ VOLTAGE AND/OR CURRENT DATA BYTES
The ADM1178 can be set up to provide information in three
different ways (see the
on how the device is configured, the following data can be read
out of the device after a conversion (or conversions).
Voltage and Current Readback
The ADM1178 digitizes both voltage and current. Three bytes
are read out of the device in the format shown in
Table 12. Voltage and Current Readback Format
Byte Contents B7 B6 B5 B4 B3 B2 B1 B0
1
Voltage
MSBs
2
Current
MSBs
3
Voltage
LSBs
Voltage Readback
The ADM1178 digitizes voltage only. Two bytes are read out of
the device in the format shown in
The following series of events occurs when the master receives
three bytes (voltage and current data) from the slave device:
Write Command Byte section). Depending
Tabl e 12 .
V11 V10 V9 V8 V7 V6 V5 V4
I11 I10 I9 I8 I7 I6 I5 I4
V3 V2 V1 V0 I3 I2 I1 I0
Tabl e 13 .
Tabl e 14 .
For cases where the master is reading voltage only or current
only, only two data bytes are read. Step 7 and Step 8 are not
required.
12 345678910
SLAVE
S
ADDRESS
12 345678
S
RA
DATA 1DATA 2NPDATA 3AA
Figure 41. Three-Byte Read from ADM1178
SLAVE
ADDRESS
Figure 42. Two-Byte Read from ADM1178
RA
REGISTER
ADDRESS
REGISTER
A
DATA
NP
06048-012
06048-013
Converting ADC Codes to Voltage and Current Readings
The following equations can be used to convert ADC codes
representing voltage and current from the ADM1175 12-bit
ADC into actual voltage and current values.
Voltage = (V
FULLSCALE
/4096) × Code
where:
V
= 6.65 (7:2 range) or 26.35 (14:1 range).
FULLSCALE
Code is the ADC voltage code read from the device (Bit V0
to
Bit V11).
Current = ((I
/4096) × Code)/Sense Resistor
FULLSCALE
where:
FULLSCALE
= 105.84 mV.
I
Code is the ADC current code read from the device (Bit I0 to
Bit I11).
Read Status Register
A single register of status data can also be read from the
ADM1178.
1. The master device asserts a start condition on SDA.
1. The master device asserts a start condition on SDA.
2. The master sends the 7-bit slave address, followed by the
read bit (high).
3. The addressed slave device asserts an acknowledge on SDA.
4. The master receives the first data byte.
5. The master asserts an acknowledge on SDA.
6. The master receives the second data byte.
7. The master asserts an acknowledge on SDA.
8. The master receives the third data byte.
9. The master asserts a no acknowledge on SDA.
10. The master asserts a stop condition on SDA, and the
transaction ends.
2. The master sends the 7-bit slave address, followed by the
3. The addressed slave device asserts an acknowledge on SDA.
4. The master receives the status byte.
5. The master asserts an acknowledge on SDA.
Tabl e 15 shows the ADM1178 status registers in detail. Note
that Bit 1, Bit 3, and Bit 5 are cleared by writing to Bit 4 of the
ALERT_EN register (CLEAR).
Rev. 0 | Page 20 of 24
read bit (high).
Figure 43. Status Read from ADM1178
12 345
SLAVE
S
ADDRESS
RA
DATA 1 A
06048-014
ADM1178
Table 15. Status Byte Operations
Bit Name Function
0 ADC_OC An ADC-based overcurrent comparison has been detected on the last three conversions.
1 ADC_ALERT
2 HS_OC
3 HS_ALERT The hot swap has failed since the last time this was reset. Cleared by writing to Bit 4 of the ALERT_EN register.
4 OFF_STATUS
5 OFF_ALERT An alert has been caused by either the ON pin or the SWOFF bit. Cleared by writing to Bit 4 of the ALERT_EN register.
An ADC-based overcurrent trip has happened, which has caused the alert. Cleared by writing to Bit 4 of the ALERT_EN
register.
The hot swap is off due to an analog overcurrent event. On parts that latch off, this is the same as the HS_ALERT status
bit (if EN_HS_ALERT = 1). On the retry parts, this indicates the current state: a 0 can indicate that the data was read
during a period when the device was retrying or that it has successfully hot swapped by retrying after at least one
overcurrent timeout.
The state of the ON pin. Set to 1 if the input pin is deasserted. Can also be set to 1 by writing to the SWOFF bit of the
CONTROL register.
Rev. 0 | Page 21 of 24
ADM1178
APPLICATIONS WAVEFORMS
1
2
3
4
CH1 1.5ACH2 1.00V
CH3 20.0V CH4 10.0V
M40.0ms
Figure 44. Inrush Current Control into 220 μF Load
LOAD
, CH2 = V
(CH1 = I
1
2
3
4
TIMER
, CH3 = V
GATE
, CH4 = V
OUT
1
2
3
4
CH1 1.5ACH2 1.00V
06048-070
CH3 20.0V CH4 10.0V
M10.0ms
06048-073
Figure 47. Overcurrent Condition During Operation (ADM1178-1 Model)
)
(CH1 = I
1
2
3
4
LOAD
, CH2 = V
TIMER
, CH3 = V
GATE
, CH4 = V
OUT
)
CH1 1.5ACH2 1.00V
CH3 20.0V CH4 10.0V
M10.0ms
Figure 45. Overcurrent Condition at Startup (ADM1178-1 Model)
(CH1 = I
LOAD
1
2
3
4
CH1 1.5ACH2 1.00V
CH3 20.0V CH4 10.0V
, CH2 = V
TIMER
, CH3 = V
M20.0ms
GATE
, CH4 = V
Figure 46. Overcurrent Condition at Startup (ADM1178-2 Model)
(CH1 = I
LOAD
, CH2 = V
TIMER
, CH3 = V
GATE
, CH4 = V
OUT
OUT
CH1 1.5ACH2 1.00V
06048-071
CH3 20.0V CH4 10.0V
M20.0ms
06048-074
Figure 48. Overcurrent Condition During Operation (ADM1178-2 Model)
LOAD
, CH2 = V
)
(CH1 = I
TIMER
, CH3 = V
GATE
, CH4 = V
OUT
)
06048-072
)
Rev. 0 | Page 22 of 24
ADM1178
V
ALERTB OUTPUT
The ALERTB output is an open-drain pin with 30 V tolerance.
This output can be used as an overcurrent flag by connecting it
to the general-purpose logic input of a controller. Under normal
operation, this output is pulled high. (An external pull-up resistor
should be used because this is an open-drain pin.) When an overcurrent condition occurs, the ADM1178 pulls this output low.
If any of the enabled latched alerts in the status byte (ADC_ALERT,
HS_ALERT, and OFF_ALERT) are triggered, the ALERTB output
asserts. For a programmable ADC-based overcurrent limit level
point, the ADC_ALERT latch must be enabled. The overcurrent
threshold that triggers an alert is then programmed via the
ALERT_TH register.
3.15V TO 16.5
R
SENSE
N-CHANNEL FET
KELVIN SENSE RESISTOR CONNECTION
When using a low value sense resistor for high current measurement, the problem of parasitic series resistance may arise.
The lead resistance can be a substantial fraction of the rated
resistance, making the total resistance a function of lead length.
This problem can be avoided by using a Kelvin sense connection.
This type of connection separates the current path through the
resistor and the voltage drop across the resistor.
the correct way to connect the sense resistor between the VCC
pin and the SENSE pin of the ADM1178.
SENSE RESISTOR
CURRENT
FLOW FROM
SUPPLY
Figure 50 shows
CURRENT
FLOW TO
LOAD
ADM1178
ON
TIMER
GND
SENSEVCC
GATE
SDA
SCL
ALERTB
ADR
CONTROLLER
P = VI
SDA
SCL
INTERRUPT
KELVIN SENSE TRACES
VCCSENSE
ADM1178
06048-100
Figure 50. Kelvin Sense Connections
06048-015
Figure 49. Using the ALERTB Output as an Interrupt
Rev. 0 | Page 23 of 24
ADM1178
OUTLINE DIMENSIONS
3.10
3.00
2.90
6
10
3.10
3.00
2.90
1
PIN 1
0.50 BSC
0.95
0.85
0.75
0.15
0.05
0.33
0.17
COPLANARITY
0.10
COMPLIANT TO JEDEC STANDARDS MO-187-BA
Figure 51. 10-Lead Mini Small Outline Package [MSOP]
5.15
4.90
4.65
5
1.10 MAX
SEATING
PLANE
0.23
0.08
8°
0°
(RM-10)
Dimensions shown in millimeters
0.80
0.60
0.40
ORDERING GUIDE
Model Hot Swap Retry Option Temperature Range Package Description Package Option Branding
ADM1178-1ARMZ-R71Automatic Retry Version −40°C to +85°C 10-Lead MSOP RM-10 M62
ADM1178-2ARMZ-R71Latched Off Version −40°C to +85°C 10-Lead MSOP RM-10 M64
EVAL-ADM1178EBZ
1
Z = Pb-free part.
1
Evaluation Board
Purchase of licensed I2C components of Analog Devices or one of its sublicensed Associated Companies conveys a license for the purchaser under the Philips I2C Patent
Rights to use these components in an I2C system, provided that the system conforms to the I2C Standard Specification as defined by Philips.