Input overvoltage (short-to-battery) protection of up to 18 V
Short-to-battery output flag for wire diagnostics
Wide input common-mode range with single 5 V supply
High performance video amplifier with 0.50 V/V gain
−3 dB bandwidth of 84 MHz
250 V/µs slew rate (2 V step)
Excellent video specifications
0.1 dB flatness to 28 MHz
SNR of 73 dB to 15 MHz
Differential gain/phase of 0.1%/0.1°
Wide supply range: 2.9 V to 5.5 V
Enable/output disable mode
Space saving 3 mm × 3 mm LFCSP package
Wide operating temperature range: −40°C to +125°C
Qualified for automotive applications
APPLICATIONS
Automotive vision systems
Automotive infotainment
Surveillance systems
FUNCTIONAL BLOCK DIAGRAM
Figure 1.
GENERAL DESCRIPTION
The ADA4830-1 (single) and ADA4830-2 (dual) are monolithic,
high speed difference amplifiers that integrate input overvoltage
(short-to-battery) protection of up to 18 V with a wide input
common-mode voltage range and excellent ESD robustness.
They are intended for use as receivers for differential or pseudo
differential CVBS and other high speed video signals in harsh,
noisy environments such as automotive infotainment and vision
systems. The ADA4830-1 and ADA4830-2 combine high speed
and precision, which allows for accurate reproduction of CVBS
video signals, yet rejects unwanted common-mode error voltages.
The short-to-battery protection that is integrated into the
ADA4830-1 and ADA4830-2 employs fast switching circuitry to
clamp and hold internal voltage nodes at a safe level when an input
overvoltage condition is detected. This protection allows the inputs
of the ADA4830-1 and ADA4830-2 to be directly connected to a
remote video source, such as a rearview camera, without the
need for large expensive series capacitors. The ADA4830-1 and
ADA4830-2 can withstand direct short-to-battery voltages as
high as 18 V on their input pins.
The ADA4830-1 and ADA4830-2 are designed to operate at supply
voltages as low as 2.9 V and as high as 5.5 V, using only 6.8 mA
of supply current per channel. These devices provide true singlesupply capability, allowing the input signal to extend 8.5 V
responsibility is assumed by Analog Devices for its use, nor for any infringements of patents or other
rights of third parties that may result from its use. Specifications subject to change without notice. No
license is granted by implication or otherwise under any patent or patent rights of Analog Devices.
Figure 2.
below ground rail and to 8.5 V above ground on a single 5 V
supply. At the output, the amplifier can swing to within 250 mV
of either supply rail into a 150 Ω load.
The ADA4830-1 and ADA4830-2 present a gain of 0.50 V/V at their
output. This is designed to keep the video signal within the allowed
range of the video decoder, which is typically 1 V p-p or less.
The ADA4830-1W and ADA4830-2W are automotive grade
version, qualified for automotive applications. See the
Automotive Products section for more details.
The ADA4830-1 and ADA4830-2 are available in 3 mm × 3 mm
LFCSP packages, 8-lead and 16-lead, respectively, and are specified
for operation over the automotive temperature range of −40°C
to +125°C.
One Technology Way, P.O. Box 9106, Norwood, MA 02062-9106, U.S.A.
Tel: 781.329.4700
www.analog.com
ADA4830-1/ADA4830-2 Data Sheet
TABLE OF CONTENTS
Features .............................................................................................. 1
Signal-to-Noise Ratio f = 100 kHz to 15 MHz, V
DC PERFORMANCE
Nominal Gain VIN to V
ADA4830-1W/ADA4830-2W only T
Output Bias Voltage 2.45 2.50 2.55 V
ADA4830-1W/ADA4830-2W only T
INPUT CHARACTERISTICS
Input Resistance (Differential Mode) 6.7 kΩ
Input Resistance (Common Mode) 2 kΩ
Input Common-Mode Voltage Range V
ADA4830-1W/ADA4830-2W only T
= 2.5 V (floating), V
REF
= 0.5 V p-p, RL = 150 Ω 64 71 MHz
OUT
= 0.1 V p-p, RL = 1 kΩ 84 MHz
OUT
= 0.1 V p-p, RL = 150 Ω 65 74 MHz
OUT
= 0.5 V p-p, RL = 150 Ω 28 MHz
OUT
= 2 V step 196/200 250/300 V/µs
OUT
= 2 V step 25 ns
OUT
OUT
voltage adjusted to optimized range −10 +9.5 V
REF
= +VS/2, R
INCM
OUT
= 5 kΩ to +VS, unless otherwise specified.
STB
MIN
MIN
MIN
to T
MAX
to T
60 MHz
MAX
to T
164/220 V/µs
MAX
56 MHz
Degrees
= 0.5 V p-p 73 dB
0.49 0.50 0.51 V/V
to T
MIN
MIN
MIN
0.49 0.51 V/V
MAX
to T
2.44 2.56 V
MAX
to T
−10 +9.5 V
MAX
ADA4830-1W/ADA4830-2W only T
MIN
to T
42 dB
MAX
SHORT-TO-BATTERY CHARACTERISTICS
Input Current VIN = 18 V (short-to-battery) 4.1 mA
Protected Input Voltage Range −9 +20 V
MIN
MAX
Short-to-Battery Output Flag Trigger
Level
ADA4830-1W/ADA4830-2W only T
Minimum VIN needed to signal an input fault
condition
to T
MIN
MAX
9.8 10.3 10.8 V
9.8 10.8 V
VOLTAGE REFERENCE INPUT
Input Voltage Range 0.2 to 3.9 V
Input Resistance 20 kΩ
Gain V
REF
to V
1 V/V
OUT
LOGIC OUTPUT/INPUT CHARACTERISTICS
STB V
OH
VIN ≤ 9.8 V (normal operation) 5.0 V
STB VOL VIN ≥ 10.8 V (fault condition), ADA4830-1/ADA4830-2110/253 mV
ENA VIH Voltage to enable device ≥3.0 V
ENA VIL Voltage to disable device ≤1.0 V
Rev. C | Page 3 of 22
ADA4830-1/ADA4830-2 Data Sheet
DYNAMIC PERFORMANCE
ADA4830-1W/ADA4830-2W only T
to T
59
MHz
Bandwidth for 0.1 dB Flatness
V
= 0.5 V p-p, RL = 150 Ω
20 MHz
Signal-to-Noise Ratio
f = 100 kHz to 15 MHz, V
= 0.5 V p-p
73 dB
Nominal Gain
VIN to V
0.49
0.50
0.51
V/V
ADA4830-1W/ADA4830-2W only T
to T
0.49 0.51
V/V
Input Current
VIN = 18 V (short-to-battery)
4.4 mA
Parameter Test Conditions/Comments Min Typ Max Unit
OUTPUT CHARACTERISTICS
Output Voltage Swing RL = 150 Ω to ground 0.01 to 4.75 V
Linear Output Current <1% THD at 100 kHz 125 mA
Short-Circuit Current Sourcing/sinking 248/294 mA
Capacitive Load Drive Peaking ≤ 3 dB 47 pF
POWER SUPPLY
Operating Range Operation outside of this range results in
performance degradation
Quiescent Current per Amplifier Enabled (ENA = 5 V), no load 6.8 10 mA
ADA4830-1W/ADA4830-2W only T
MIN
to T
10.4 mA
MAX
Disabled (ENA = 0 V), no load 90 µA
VIN = 18 V (short-to-battery), no load 5.3 mA
Power Supply Rejection Ratio (PSRR) +VS = 4.5 V to 5.5 V, V
is forced to 2.5 V 53 dB
REF
OPERATING TEMPERATURE RANGE −40 +125 °C
3.3 V OPERATION
TA = 25°C, +VS = 3.3 V, RL = 1 kΩ, V
Table 2.
Parameter Test Conditions/Comments Min Typ Max Unit
= 1.65 V (floating), V
REF
= +VS/2, R
INCM
= 5 kΩ to +Vs, unless otherwise specified.
STB
2.9 5.5 V
−3 dB Large Signal Bandwidth V
ADA4830-1W/ADA4830-2W only TV
V
Slew Rate (tR/tF) V
ADA4830-1W/ADA4830-2W only T
Settling Time to 0.1% V
= 0.5 V p-p, RL = 150 Ω 63 73 MHz
OUT
to T
MIN
= 0.1 V p-p, RL = 1 kΩ 89 MHz
OUT
= 0.1 V p-p, RL = 150 Ω 64 78 MHz
OUT
MIN
OUT
= 1 V step 147/155 165/180 V/µs
OUT
MIN
= 1 V step 25 ns
OUT
58 MHz
MAX
MAX
to T
136/145 V/µs
MAX
NOISE/DISTORTION PERFORMANCE
Output Voltage Noise f = 1 MHz 28 nV/√Hz
Differential Gain Error (NTSC) RL = 150 Ω, VIN = 1 V p-p 0.1 %
Differential Phase Error (NTSC) RL = 150 Ω, VIN = 1 V p-p 0.1 Degrees
OUT
DC PERFORMANCE
OUT
MIN
MAX
Output Bias Voltage 1.60 1.65 1.70 V
ADA4830-1W/ADA4830-2W only T
MIN
to T
1.59 1.71 V
MAX
INPUT CHARACTERISTICS
Input Resistance (Differential Mode) 6.7 kΩ
Input Resistance (Common Mode) 2 kΩ
Input Common-Mode Voltage Range V
ADA4830-1W/ADA4830-2W only T
voltage adjusted to optimized range −8 +6 V
REF
to T
MIN
−8 +6 V
MAX
Common-Mode Rejection (CMR) VIN = ±3.3 V 41 54 dB
ADA4830-1W/ADA4830-2W only T
MIN
to T
40 dB
MAX
SHORT-TO-BATTERY CHARACTERISTICS
Protected Input Voltage Range −9 +20 V
ADA4830-1W/ADA4830-2W only T
Short-to-Battery Output Flag Trigger
Level
ADA4830-1W/ADA4830-2W only T
to T
MIN
Minimum VIN needed to signal an input fault
−9 +20 V
MAX
7.4 7.8 8.2 V
condition
to T
MIN
Rev. C | Page 4 of 22
7.4 8.2 V
MAX
Data Sheet ADA4830-1/ADA4830-2
Output Voltage Swing
RL = 150 Ω to ground
0.01 to 3.08
V
ADA4830-1W/ADA4830-2W only T
to T
8.4
mA
Parameter Test Conditions/Comments Min Typ Max Unit
VOLTAGE REFERENCE INPUT
Input Voltage Range 0.2 to 2.2 V
Input Resistance 20 kΩ
Gain V
LOGIC OUTPUT/INPUT CHARACTERISTICS
STB V
OH
STB VOL VIN ≥ 8.2 V (fault condition), ADA4830-1/ADA4830-285/178 mV
ENA VIH Voltage to enable device ≥1.8 V
ENA VIL Voltage to disable device ≤0.8 V
OUTPUT CHARACTERISTICS
Linear Output Current <1% THD at 100 kHz 50 mA
Short-Circuit Current Sourcing/sinking 85/180 mA
Capacitive Load Drive Peaking ≤ 4 dB 47 pF
POWER SUPPLY
Operating Range Operation outside of this range results in
Quiescent Current per Amplifier Enabled (ENA = 3.3 V), no load 5.5 8.0 mA
Disabled (ENA = 0 V), no load 60 µA
VIN = 18 V (short-to-battery), no load 4.3 mA
Power Supply Rejection Ratio (PSRR) +VS = 3.0 V to 3.6 V, V
OPERATING TEMPERATURE RANGE −40 +125 °C
to V
REF
1 V/V
OUT
VIN ≤ 7.4 V (normal operation) 3.3 V
2.9 5.5 V
performance degradation
MIN
MAX
forced to 1.65 V 42 dB
REF
Rev. C | Page 5 of 22
ADA4830-1/ADA4830-2 Data Sheet
Supply Voltage (+VS Pin)
6 V
Stresses above those listed under Absolute Maximum Ratings
may cause permanent dam age to the device. This is a stress
rating only ; functional operation of the device at these or any
other conditions above those indicated in the operational
section of this specification is not implied. Exposure to absolute
maximum rating conditions for extended periods may affect
device reliability.
8-Lead LFCSP
50 5 °C/W
10020-050
0
0.5
1.0
1.5
2.0
2.5
3.0
0102030405060708090 100
MAXIMUM POWER DISSIPATION (W)
AMBIENT TEMPERATURE (°C)
16-LEAD LF CS P
8-LEAD LF CS P
ABSOLUTE MAXIMUM RATINGS
Table 3.
Parameter Rating
Supply Voltage Delta
+VS1 to +VS2, ADA4830-2 Only 0.5 V
Input Voltage Positive Direction (INNx, INPx) 22 V
Input Voltage Negative Direction (INNx, INPx) −10 V
Reference Voltage (VREFx Pin) +VS + 0.3 V
Power Dissipation See Figure 3
Storage Temperature Range −65°C to +150°C
Operating Temperature Range −40°C to +125°C
Lead Temperature (Soldering, 10 sec) 260°C
Junction Temperature 150°C
The power dissipated in the package (P
quiescent power dissipation and the power dissipated in the
package due to the load drive for all outputs. The quiescent
power is the supply voltage (+V
) times the quiescent current (IS).
S
The power dissipated due to load drive depends on the particular
application. The power due to load drive is calculated by
multiplying the load current by the associated voltage drop
across the device. RMS voltages and currents must be used
in these calculations.
Figure 3 shows the maximum power dissipation in the package vs.
the ambient temperature for the 8-lead LFCSP (116°C/W) and
the 16-lead LFCSP (54°C/W) on a JEDEC standard 4-layer board.
θ
values are approximate.
JA
) is the sum of the
D
.
JA
THERMAL RESISTANCE
θJA is specified for the device and its exposed paddle is soldered
to a high thermal conductivity, 4-layer (2s2p) circuit board, as
described in EIA/JESD 51-7.
Table 4.
Package Type θJA θJC Unit
16-Lead LFCSP 54 6 °C/W
MAXIMUM POWER DISSIPATION
The maximum safe power dissipation in the ADA4830-1 and
ADA4830-2 packages is limited by the associated rise in
junction temperature (T
which is the glass transition temperature, the plastic changes its
properties. Exceeding a junction temperature of 150°C for an
extended time can result in changes in the silicon devices,
potentially causing failure.
) on the die. At approximately 150°C,
J
Figure 3. Maximum Power Dissipation vs.
Ambient Temperature for a 4-Layer Board
ESD CAUTION
Rev. C | Page 6 of 22
Data Sheet ADA4830-1/ADA4830-2
NOTES
1. EXPOSED PAD ON BOTTOM SIDE
OF PACKAGE . NOT CONNECT E D
ELECTRI CALLY, BUT SHOULD BE
SOLDERED TO A METALIZED AREA
ON THE PCB TO MINIMIZE THERMAL
RESISTANCE .
3INN
4GND
1VREF
2INP
6 VOUT
5 STB
8 +VS
7 ENA
ADA4830-1
TOP VIEW
(Not to S cale)
10020-003
3
INN
Negative Input.
PIN CONFIGURATIONS AND FUNCTION DESCRIPTIONS
Figure 4. ADA4830-1 Pin Configuration
Table 5. ADA4830-1 Pin Function Descriptions
Pin No. Mnemonic Description
1 VREF Voltage Reference Input. Sets the output dc bias voltage. Internally biased to +VS/2 when left floating. See the
Applications Information section.
2 INP Positive Input.
4 GND Power Supply Ground Pin.
5 STB Short-to-Battery Indicator Output Pin. A logic low indicates an overvoltage condition (short-to-battery), whereas a
logic high indicates normal operation. An open-drain configuration requires external pull-up resistor.
6 VOUT Amplifier Output.
7 ENA Enable Pin. Connect to +VS or float for normal operation. Connect to ground for device disable.
8 +VS Positive Power Supply Pin. Bypass this pin with a 0.1 µF capacitor to ground.
EPAD Exposed Pad. The exposed pad is located on the bottom side of the package. The pad is not connected electrically
but should be soldered to a metalized area on the printed circuit board (PCB) to minimize thermal resistance.
Rev. C | Page 7 of 22
ADA4830-1/ADA4830-2 Data Sheet
10020-004
12
11
10
1
3
4
VOUT1
NOTES
1. EXPOSED PAD ON BOTTOM SIDE
OF PACKAGE . NOT CONNECT E D
ELECTRI CALLY, BUT SHOULD BE
SOLDERED TO A METALIZED AREA
ON THE PCB TO MINIMIZE THERMAL
RESISTANCE .
STB1
STB2
9
VOUT2
INP1
INN2
2
INN1
INP2
6GND2
5VREF2
7+VS2
8
ENA2
16
VREF1
15
GND1
14
+VS1
13
ENA1
TOP
VIEW
ADA4830-2
10, 11
STB2, STB1
Short-to-Battery Indicator Output Pins. A logic low indicates an overvoltage condition (short-to-battery), whereas a
Figure 5. ADA4830-2 Pin Configuration
Table 6. ADA4830-2 Pin Function Descriptions
Pin No. Mnemonic Description
1, 4 INP1, INP2 Positive Inputs.
2, 3 INN1, INN2 Negative Inputs.
5, 16 VREF2, VREF1 Voltage Reference Inputs. Sets the output dc bias voltage. Internally biased to +VS/2 when left floating. See
the Applications Information section.
6, 15 GND2, GND1 Power Supply Ground Pins.
7, 14 +VS2, +VS1 Positive Power Supply Pins. These pins must be connected together, to the same voltage. Bypass these pins
with a 0.1 µF capacitor to ground.
8, 13 ENA2, ENA1 Enable Pins. Connect to +VS or float for normal operation and to ground for device disable.
9, 12 VOUT2, VOUT1 Amplifier Outputs.
logic high indicates normal operation. An open-drain configuration requires an external pull-up resistor.
EPAD Exposed Pad. The exposed pad is located on the bottom side of the package. The pad is not connected
electrically, but should be soldered to a metalized area on the PCB to minimize thermal resistance.
Rev. C | Page 8 of 22
Data Sheet ADA4830-1/ADA4830-2
3
0
–3
–6
–9
–12
–15
–18
0.1110100
FREQUENCY (MHz)
NORMALIZED GAIN (dB)
10020-005
VIN = 200mV p-p
RL = 150Ω
R
L
= 1kΩ
3
0
–3
–6
–9
–12
–15
–18
0.1110100
FREQUENCY (MHz)
NORMALIZ E D GAIN (dB)
10020-006
VIN = 200mV p-p
+VS = 3.3V
+VS = 5V
3
0
–3
–6
–9
–12
–15
–18
–21
–24
110100
FREQUENCY (MHz)
NORMALIZED GAIN (dB)
10020-008
+125°C
+25°C
–40°C
VIN = 200mV p-p
3
0
–3
–6
–9
–12
–15
–18
0.1110100
FREQUENCY (MHz)
NORMALIZED GAIN (dB)
10020-010
V
IN
= 1V p-p
R
L
= 150Ω
R
L
= 1kΩ
3
0
–3
–6
–9
–12
–15
–18
0.1
110100
FREQUENCY (MHz)
NORMALIZ E D GAIN (dB)
10020-011
V
IN
= 1V p-p
+V
S
= 3.3V
+V
S
= 5V
3
0
–3
–6
–9
–12
–15
–18
–21
–24
110100
FREQUENCY (MHz)
NORMALIZED GAIN (dB)
10020-013
+25°C
+125°C
–40°C
+VS = 3.3V
V
IN
= 1V p-p
R
L
= 150Ω
TYPICAL PERFORMANCE CHARACTERISTICS
TA = 25°C, +VS = 5 V, RL = 1 kΩ, V
= 2.5 V (floating), V
REF
= +VS/2, R
INCM
= 5 kΩ to +VS, unless otherwise specified.
STB
Figure 6. Small Signal Frequency Response for Various Loads
Figure 7. Small Signal Frequency Response for Various Supply Voltages
Figure 9. Large Signal Frequency Response for Various Loads
Figure 10. Large Signal Frequency Response for Various Supply Voltages
Figure 8. Small Signal Frequency Response for Various Temperatures
Figure 11. Large Signal Frequency Response for Various Temperatures
Rev. C | Page 9 of 22
ADA4830-1/ADA4830-2 Data Sheet
7
6
5
4
3
2
1
0
–1
–2
–3
0.1110100
FREQUENCY (MHz)
NORMALIZED GAIN (dB)
10020-012
V
IN
= 1V p-p
R
L
= 150Ω
CL = 0pF
C
L
= 68pF
NO SERIES OUTPUT RESISTOR
CL = 47pF
CL = 22pF
CL = 10pF
0.1
0
–0.1
–0.2
–0.3
–0.4
–0.5
0.1110100
FREQUENCY (MHz)
NORMALIZED GAIN (dB)
10020-014
VIN = 1V p-p
R
L
= 150Ω
–90
–80
–70
–60
–50
–40
–30
–20
0.1110100
COMMON-M ODE REJECTIO N ( dB)
FREQUENCY (MHz)
10020-042
VIN = 1V p-p
V
INCM
= −8V
V
INCM
= +8V
V
INCM
= 0V
–70
–65
–60
–55
–50
–45
–40
–35
–30
–25
–12 –10 –8 –6 –4 –2
0 2468 10 12 14
COMMON-M ODE REJECTIO N ( dB)
INPUT COMMON-MODE VOLTAGE (V)
VIN = 200mV p-p
f = 5MHz
+VS = 3.3V+VS = 5.0V
10020-017
–70
–60
–50
–40
–30
–20
–10
0
0.1110100
GAIN (dB)
FREQUENCY (MHz)
10020-019
V
IN
= 1V p-p
ENA = 0V
6
3
0
–3
–6
–9
–12
–15
0.1110100
FREQUENCY (MHz)
NORMALIZED GAIN (dB)
10020-009
V
REF
= 200mV p-p
+VS = 5.0V
R
L
= 1kΩ
+V
S
= 3.3V
R
L
= 150Ω
+VS = 5.0V
R
L
= 150Ω
+V
S
= 3.3V
R
L
= 1kΩ
Figure 12. Large Signal Frequency Response for Various Capacitor Loads
Figure 13. 0.1 dB Flatness
Figure 15. Small Signal CMR vs. V
for Various Supply Voltages
INCM
Figure 16. Input-to-Output Isolation with Device Disabled
Figure 14. CMR Frequency Response for Various Input Common-Mode
Voltages
Figure 17. V
to V
Frequency Response
REF
OUT
Rev. C | Page 10 of 22
Data Sheet ADA4830-1/ADA4830-2
1.5
1.7
1.9
2.1
2.3
2.5
2.7
2.9
01020304050607080
OUTPUT VOLTAGE (V)
TIME (ns)
10020-020
+V
S
= 3.3V
V
OUT
= 1V p-p
R
L
= 1kΩ
R
L
= 150Ω
–2
0
2
4
6
8
10
12
14
16
050 100 150 200 250 300 350500400 450
VOLTAGE (V)
TIME (ns)
10020-022
INP
R
STB
= 500Ω
R
STB
= 1kΩ
C
STB
= 11pF
R
STB
= 5kΩ
6
5
4
3
2
1
0
–1
1000200300400500600
TIME (ns)
VOLTAGE (V)
10020-024
ENA
V
OUT
–20
–10
0
10
20
30
40
–12 –10 –8 –6 –4 –2 0 2468 10 12 14
OUTPUT OFFSET VOLTAGE (mV)
INPUT COMMON-MODE VOLTAGE (V)
10020-033
+V
S
= 3.3V
+V
S
= 5V
0
1
2
3
4
5
6
7
8
9
10
00.5 1.0 1.5 2.0 2.5 3.0 3.5 4.0 4.5 5.0
SUPPLY CURRENT (mA)
ENABLE VOLTAGE (V)
V
INP,VINN
= FLOATING
+VS = 3.3V
+VS = 5V
10020-134
0
20
40
60
80
100
120
140
46515661667176818691
COUNT
CMR (dB)
10020-045
Figure 18. Pulse Response at +VS = 3.3 V
Figure 19. Short-to-Battery Output Flag Response for Va rious R
, ADA4830-1
STB
Figure 21. Output Offset Voltage (V
OUT
− V
Input Common-Mode Voltage
Figure 22. Supply Current vs. Enable Voltage
) vs.
REF
Figure 20. Enable Turn-on/ Turn-off Time
Figure 23. Typical Distribution of Common-Mode Rejection
Rev. C | Page 11 of 22
ADA4830-1/ADA4830-2 Data Sheet
10020-046
–95
–90
–85
–80
–75
–70
–65
–60
–55
–50
–45
0.1110100
CROSSTALK (dB)
FREQUENCY (MHz)
V
IN
= 2V p-p
1.0
1.5
2.0
2.5
3.0
3.5
4.0
0102030405060708090 100
V
OUT
(V)
TIME (ns)
V
IN
= 4V p-p
C
L
= 0pF
CL = 22pF
C
L
= 10pF
10020-047
10
100
1k
10k
101001k10k100k1M10M100M
VOLTAGE NOISE (nV/√Hz)
FREQUENCY (Hz)
10020-048
5.0
5.5
6.0
6.5
7.0
7.5
8.0
8.5
9.0
9.5
10.0
–40 –25 –10 520 35 50 65 80 95 110 125
SUPPLY CURRENT (mA)
TEMPERATURE (°C)
10020-051
10020-028
–110
–100
–90
–80
–70
–60
–50
–40
0.010.1110
DISTORTION (dBc)
FREQUENCY (MHz)
V
OUT
= 1V p-p
SINGLE - E NDE D INPUT
HD2
SINGLE - E NDE D INPUT
HD3
DIFFERENTIAL INPUT
HD2
DIFFERENTIAL INPUT
HD3
–70
–60
–50
–40
–30
–20
–10
0
10
101001k10k100k1M10M
PSR (dB)
FREQUENCY (Hz)
10020-029
+VS RIPPLE = 100mV p-p
C
VREF
= 0.1µF
C
VREF
= 10µF
C
VREF
= 4.7µF
Figure 24. Crosstalk (Output-to-Output) vs. Frequency, ADA4830-2
Figure 25. Pulse Response for Various Capacitor Loads
Figure 27. Supply Current vs. Temperature
Figure 28. Harmonic Distortion Vs Frequency
Figure 26. Total Output Voltage Noise vs. Frequency
Figure 29. PSR vs. Frequency for Various VREF Bypass Capacitors
Rev. C | Page 12 of 22
Data Sheet ADA4830-1/ADA4830-2
REF
INNINP
OUT
V
VV
V+
−
=
2
THEORY OF OPERATION
CORE AMPLIFIER
At the core of the ADA4830-1 and ADA4830-2 are high speed,
rail-to-rail op amps that are built on a 0.35 µm CMOS process.
Togeth er with the core amplifier, the ADA4830-1and ADA4830-2
combine four highly matched on-chip resistors into a difference
amplifier function. Common-mode range extension at its inputs
is achieved by employing a resistive attenuator. The closed-loop
differential to single-ended gain of the video channel is internally
fixed at 0.50 V/V (−6 dB) to ensure compatibility with video
decoders whose input range is constrained to 1 V p-p or less.
The transfer function of the ADA4830-1 and ADA4830-2 is
where:
V
is the voltage at the output pin, VOUT.
OUT
V
INP
and V
are the input voltages at the INP and INN pins,
INN
respectively.
V
is the voltage at the VREF pin.
REF
OVERVOLTAGE (SHORT-TO-BATTERY)
PROTECTION
Robust inputs guarantee that sensitive internal circuitry is not
subjected to extreme voltages or currents during a stressful event. A
short-to-battery condition usually consists of a voltage on either
input (or both inputs) that is significantly higher than the power
supply voltage of the amplifier. Duration may vary from a short
transient to a continuous fault.
The ADA4830-1 and ADA4830-2can withstand voltages of up
to 18 V on the inputs. Critical internal nodes are protected from
exposure to high voltages by circuitry that clamps the inputs at a
safe level and limits internal currents. This protection is available
whether the device is enabled or disabled, even when the supply
voltage is removed.
SHORT-TO-BATTERY OUTPUT FLAG
The short-to-battery output flag (STB pin) is functionally
independent of the short-to-battery protection. Its purpose is
to indicate an overvoltage condition on either input. Because
protection is provided passively, it is always available; the flag
merely indicates the presence or absence of a fault condition.
ESD PROTECTION
All pins on the ADA4830-1 and ADA4830-2 are protected with
internal ESD protection structures connected to the power supply
pins (+VS and GND). These structures provide protection during
the handling and manufacturing process.
The inputs (INN and INP) of the ADA4830-1 and ADA4830-2
can be exposed to dc voltages well above the supply voltage;
therefore, conventional ESD structure protection cannot be used.
The ADA4830-1 and ADA4830-2 employ Analog Devices, Inc.,
proprietary ESD devices at the input pins (INN, INP) to allow
for a wide common-mode voltage range and ESD protection
well beyond the handling and manufacturing requirements.
The inputs of the ADA4830-1 and ADA4830-2 are ESD protected
to survive ±8 kV human body model (HBM)
POWER SUPPLY PINS (ADA4830-2)
As indicated in the Absolute Maximum Ratings section, the voltage
difference between the +VS1 and +VS2 pins of the ADA4830-2
cannot exceed 0.5 V. To ensure compliance with the Absolute
Maximum Ratings, it is recommended that these supply pins be
connected together to the same power supply source.
The ADA4830-1 and ADA4830-2 can be operated in a pseudo
differential configuration with an unbalanced input signal. This
allows the receiver to be driven by a single-ended source. Pseudo
differential mode uses a single conductor to carry an unbalanced
signal and connects the negative input terminal to the ground
reference of the source.
Use the positive wire or coaxial center conductor to connect the
source output to the positive input (INP) of the ADA4830-1 or
ADA4830-2. Next, connect the negative wire or coaxial shield from
the negative input (INN) back to a ground reference on the source
printed circuit board (PCB). The input termination should match
the source impedance and be referenced to the remote ground.
An example of this configuration is shown in Figure 30.
Pseudo differential signaling is typically implemented using
unbalanced source termination, as shown in Figure 30. With
this arrangement, however, common-mode signals on the
positive and negative inputs receive different attenuation due to
unbalanced termination at the source. This effectively converts
some of the common-mode signal into differential mode signal,
degrading the overall common-mode rejection of the system.
System common-mode rejection can be improved by balancing
the output impedance of the driver, as shown in Figure 31.
Splitting the source termination resistance evenly between the
hot and cold conductors results in matched attenuation of the
common-mode signals, ensuring maximum rejection.
Figure 31. Pseudo Differential Mode with Balanced Source Impedance
Rev. C | Page 14 of 22
Fully Differential Mode
The differential inputs of the ADA4830-1 and ADA4830-2 allow
full balanced transmission using a differential source. In this
configuration, the differential input termination is equal to twice
the source impedance of each output. For example, a source
with 37.5 Ω back termination resistors in each leg should be
terminated with a differential resistance of 75 Ω. An illustration
of this arrangement is shown in Figure 32.
Figure 32. Fully Differential Mode
VOLTAGE REFERENCE (VREF PIN)
An internal reference level (V
when the differential input voltage is zero. A resistor divider
connected between the supply rails sets the V
with a pair of matched 40 kΩ resistors, the divider sets this
voltage to +V
S
/2.
The voltage reference pin (VREF) normally floats at its default
value of +V
/2. However, it can be used to vary the output
S
reference level from this default value. A voltage applied to VREF
appears at the output with unity gain, within the bandwidth limit
of the internal reference buffer. Figure 17 shows the frequency
response of the VREF input.
Any noise on the +V
supply rail appears at the output with only
S
6 dB of attenuation (the divide-by-two provided by the reference
divider). Even when this pin is floating, it is recommended that
an external capacitor be connected from the reference node to
ground to provide further attenuation of noise on the power supply
line. A 4.7 µF capacitor combined with the internal 40 kΩ resistor
sets the low-pass corner at under 1 Hz and results in better than
40 dB of supply noise attenuation at 100 Hz.
) determines the output voltage
REF
voltage. Built
REF
Data Sheet ADA4830-1/ADA4830-2
3.3
1.651
–7.6
3.6
–15
–10
–5
0
5
10
15
2.53.03.54.04.55.0
5
.56.0
INPUT COMMON-MODE VOLTAGE (V)
S
UPPLYVOLTAGE (V)
V
INCM (MAX)
V
INCM (MIN)
VREF PIN FLOATING
10020-037
INPUT COMMON-MODE RANGE
In a standard four resistor difference amplifier with 0.50 V/V
gain, the input common-mode (CM) range is three times the CM
range of the core amplifier. In the ADA4830-1 and ADA4830-2,
however, the input CM range has been extended to more than 18 V
(with a 5 V supply). The input CM range can be approximated
by using the following formulas:
For the maximum CM voltage,
5(+V
− 1.25) − 4V
S
For the minimum CM voltage,
−10 V ≤ V
INCM(MIN)
Approximate minimum and maximum CM voltages are shown
in Tabl e 7 for several common supply voltages.
Table 7. Input Common-Mode Range Examples
+VS (V) V
3.0 1.51 –7.0 2.8
3.0 0.97 –4.9 4.9
≈ V
REF
≈ − (1 + 4V
(V) V
REF
INCM(MAX)
REF
INCM(MIN)
≤ 9.5 V
)
(V) V
INCM(MAX)
(V)
In the falling direction, the speed with which the flag output
responds primarily depends on the external capacitance attached to
this node and the sink current that can be provided. For example, if
the load is 10 pF, and the external pull-up voltage is 3.3 V, the fall
time is a few nanoseconds. In the rising direction, the speed is
determined by external capacitance and the magnitude of the
pull-up resistor. For the case of 10 pF of external capacitance
and a pull-up of 5 kΩ, the time constant of the rising edge is
approximately 50 ns.
Table 8. STB Pin Function
STB Pin Output Device State
High (Logic 1) Normal operation
Low (Logic 0) STB fault condition
ENABLE/DISABLE MODES (ENA PIN)
The power-down, or enable/disable (ENA) pin, is internally pulled
up to +V
pin is high, the amplifier is enabled; pulling ENA low disables
the channel. With no external connection, this pin floats high,
enabling the amplifier channel.
through a 250 kΩ resistor. When the voltage on this
S
3.3 1.15 –5.6 5.6
3.6 1.81 –8.2 4.5
3.6 1.34 –6.4 6.4
5.0 2.51 –10 8.7
5.0 2.22 –9.9 9.5
1
Floating (default condition).
Figure 33. Input Common-Mode Range vs. Supply Voltage
SHORT-TO-BATTERY OUTPUT FLAG PIN
The flag output (STB) is an active low, open-drain logic
configuration. A low level on this output indicates that an
overvoltage event has been detected on either the positive or
the negative input or both. Flags from multiple chips can be
wire-OR'ed to form a single fault detection signal. The output is
driven by a grounded source NMOS device, capable of sinking
approximately 10 mA while pulling within a few hundred millivolts
above ground. The output high level is set with an external pull-up
resistor connected to the supply voltage of the logic family that is
used to monitor the state of the flag.
Table 9. ENA Pin Function
ENA Pin Input Device State
High (Logic 1) Enabled
Low (Logic 0) Disabled
High-Z (Floating) Normal operation
PCB LAYOUT
As with all high speed applications, attention to PCB layout is of
paramount importance. Adhere to standard high speed layout
practices in designs using the ADA4830-1 and ADA4830-2. A
solid ground plane is recommended, and placing a 0.1 µF surfacemount, ceramic power supply, decoupling capacitor as close as
possible to the supply pin(s) is recommended.
Connect the GND pin(s) to the ground plane with a trace that is as
short as possible. In cases where the ADA4830-1 and ADA4830-2
drive transmission lines, series terminate the outputs and use
controlled impedance traces of the shortest length possible to
connect to the signal I/O pins, which should not pass over any
voids in the ground plane.
Rev. C | Page 15 of 22
EXPOSED PADDLE (EPAD) CONNECTION
The ADA4830-1 and ADA4830-2 have an exposed thermal pad
(EPAD ) on the bottom of the package. This pad is not electrically
connected to the die and can be left floating or connected to the
ground plane. Should heat dissipation be a concern, thermal
resistance can be minimized by soldering the EPAD to a
metalized pad on the PCB. Connect this pad to the ground
plane with multiple vias. Note that the thermal resistance (θ
of the device is specified with the EPAD soldered to the PCB.
)
JA
ADA4830-1/ADA4830-2 Data Sheet
ADA4830-2
INP1
GND2
VREF2
+VS2
0.1µF
ENA2
ENABLE2
(INPUT)
+V
S
4.7µF
4.7µF
VREF1
+VS1
GND1
ENA1
VOUT1
VOUT2
STB1
STB2
5kΩ5kΩ
+V
S
+V
S
1
2
3
4
6785
12
11
10
9
151413
16
75Ω
75Ω
75Ω
DIFFERENTIAL
INPUT 1
75Ω
75Ω
DIFFERENTIAL
INPUT 2
CONNECT
TO VIDEO
DECODER
75Ω
INN1
INN2
INP2
STB FLAGS
(OUTPUTS)
2.2µF
0.1µF
+
ENABLE1
(INPUT)
10020-049
USING THE ADA4830-2 AS A LOW COST VIDEO
SWITCH
Figure 34 shows a video multiplexer/switch using the ADA4830-2,
dual, high speed difference amplifier. This circuit allows the user
to input two remote video sources into a single channel of a video
decoder, such as the ADV7180.
Traditional CMOS multiplexers and switches suffer several
disadvantages at video frequencies where their on-resistance
introduces distortion, degrades differential gain and phase
performance, and interacts with the termination resistor to
attenuate the incoming video signal and affect the luminance.
System designers generally address these issues by adding
external buffers to add gain and increase drive capability.
Video multiplexing can be simplified by using high speed video
amplifiers with a disable/enable function (sometimes called powerdown). When the amplifier is disabled, its output stage goes into
a high impedance state, allowing several amplifier outputs to be
wired together. High speed video op amps have all the key features
required to make them ideal for this function. Their high input
impedance does not affect the characteristic impedance of the
transmission line, thus allowing back termination. They also have
inherently good video specifications, including differential gain and
phase, slew rate, bandwidth, and 0.1 dB flatness.
Each channel of the ADA4830-2 is a high speed difference
amplifier circuit that eliminates common-mode noise and phase
noise caused by ground potential differences between the incoming
video signal and the receiver. The ADA4830-2 also offers integrated
short-to-battery protection and heightened ESD tolerance in a
small foot print. The fault detection output (the STB pins) of the
ADA4830-2 allows for proactive wire diagnostics when connected
to a microcontroller or video decoder and are used to generate
an interrupt during a fault condition.
Figure 34. Low Cost Video Switch Using the ADA4830-2
Rev. C | Page 16 of 22
Data Sheet ADA4830-1/ADA4830-2
ADA4830-1
+
–
CL = 47pF
R
S
= 49.9Ω
RL = 1kΩ
10020-052
1.0
1.5
2.0
2.5
3.0
3.5
4.0
050100150200250
V
OUT
(V)
TIME (ns)
10020-135
+VS = 5V
RL = 1kΩ
CL = 47pF
NO R
S
R
S
= 49.9Ω
ADA4830-1
+
–
CL = 47pF
C
SNT
= 0.1uF
RL = 1kΩ
R
SNT
= 73.2Ω
10020-053
1.0
1.5
2.0
2.5
3.0
3.5
4.0
050100150200250
V
OUT
(V)
TIME (ns)
10020-137
+V
S
= 5V
R
L
= 1kΩ
CL = 47pF
NO SNUBBER
CIRCUIT
R
SNT
= 73.2Ω
C
SNT
= 0.1µF
DRIVING CAPACITIVE LOADS
The ADA4830-1 and ADA4830-2 are capable of driving large
capacitive loads while maintaining its rated performance.
Several performance curves vs. capacitive load are shown in
Figure 12 and Figure 25. Capacitive loads interact with an op amp’s
output impedance to create an extra delay in the feedback path.
This reduces circuit stability and can cause unwanted ringing
and oscillation.
The capacitive load drive of the ADA4830-1and ADA4830-2 can
be increased by adding a low valued resistor, R
capacitive load. Figure 35 shows the test circuit.
, in series with the
S
Another method of reducing the resonant peaking caused by
driving large capacitive loads at the output of the ADA4830-1
and ADA4830-2 is with the use of a R-C shunt circuit or a snubber
circuit. This method acts to resistively load the amplifier output,
thus reducing frequency response peaking. One drawback to this
approach is a slight loss of signal bandwidth. Figure 37 shows a
simple circuit representation of the implementation of the R-C
snubber circuit with R
a R-C snubber circuit driving 47 pF, where R
SNT
and C
. Figure 38 shows the effects of
SNT
= 73.2 Ω and C
SNT
SNT
= 0.1 µF.
Figure 35. R
Test Circuit
S
Introducing a series resistor tends to isolate the capacitive load
from the feedback loop, thereby diminishing its influence. One
drawback to this approach is a slight loss of signal amplitude.
Figure 36 shows the effects of a series resistor on the capacitive
drive. For very large capacitive loads, the frequency response of
the amplifier is dominated by the roll-off of the series resistor
and capacitive load.
Figure 37. R-C Test Circuit
Figure 38. Pulse Response With and Without R-C Snubber Circuit
Figure 36. Pulse Response With and Without Series Resistor
Rev. C | Page 17 of 22
ADA4830-1/ADA4830-2 Data Sheet
INN
VOUT
TO VIDEO
DECODER
GND
INP
VREF
ADA4830-1
75Ω
−
+
75Ω
POSITIVE W IRE
NEGATIVE W IRE
DRIVER PCB
+
STBENA+VS
SINGLE ENDED
AMPLIFIER
4.7µF
0.1µF
+VS
ENABLE
(INPUT)
STB FLAG
(OUTPUT)
2.2µF
0.1µF
+V
S
(2.9V TO 5.5V)
5kΩ
×1
10020-038
INN
VOUT
TO VIDEO
DECODER
GND
INP
ADA4830-1
75Ω
−
+
37.5Ω
37.5Ω
DRIVER PCB
STBENA+VS
4.7µF
0.1µF
+VS
+
ENABLE
(INPUT)
STB FLAG
(OUTPUT)
2.2µF
0.1µF
5kΩ
×1
+V
S
(2.9V TO 5.5V)
VREF
DIFFERENTIAL
AMPLIFIER
10020-039
TYPICAL APPLICATIONS CIRCUITS
Figure 39. Typical Application with Pseudo Differential Input
Figure 40. Typical Application with Full y Differential Input
Rev. C | Page 18 of 22
Data Sheet ADA4830-1/ADA4830-2
−
+
ADV7180
INN
VOUT
GND
INP
ADA4830-1
75Ω
+
STBENA+VS
4.7µF
0.1µF
0.1µF
21
25
24
23
19
3
143022
18
A
IN
1
A
IN
2
A
IN
3
20
13
11
32
1
31
4
12
26
28
17
82nF
10nF
2
29
ELPF
27
ALSB
SCLKSCLK
DGND
DGND
SDA
SDATA
XTAL1
XTAL
0.1µF
+VS
ENABLE
(INPUT)
STB FLAG
(OUTPUT)
2.2µF
0.1µF
5kΩ
+V
S
(2.9V TO 5.5V)
VREF
D
VDDIO
0.1µF10nF
A
VDD
_1.8V
0.1µF10nF
0.1µF10nF
D
VDD
_1.8V
D
VDD
_3.3V
D
VDDIO
P
VDD
_1.8V
P
VDD
_1.8V
D
VDD
_1.8V
A
VDD
_1.8V
0.1µF10nF
KEEP VREFN AND V RE FP CAPACITORS AS CLOSE AS
POSSIBLE TO THE ADV 7180 AND ON THE SAME SI DE
OF THE P CB AS THE ADV7180.
LOCATE CLOSE TO, AND
ON THE SAME SIDE AS,
THE ADV7180
ALSB TIED HI
≥ I2C ADDRE S S = 0x42
ALSB TIED LOW
≥ I
2
C ADDRE S S = 0x40
RESET
RESET
P0
P1
P2
P3
P4
P5
P6
P7
P0
YCrCb
8-BIT
656 DATA
P[0:7]
P1
P2
P3
P4
P5
P6
P7
16
15
10
9
8
7
6
5
VREFN
DVDDIO
DVDD
DVDD
AVDD
PVDD
VREFP
28.63636MHz
47pF
47pF
1MΩ
4kΩ
LLC
1.69kΩ
INTRQ
SFL
VS/FIELD
EXTERNAL
LOOP FILTER
KEEP CLOS E TO THE ADV7180 AND ON
THE SAME SIDE OF PCB AS T HE ADV 7180.
HS
LLC
INTRQ
SFL
VS/FIELD
HS
10020-040
×1
The ADA4830-1 and ADA4830-2 are differential receivers whose
overall performance is independent of the transmitter IC used
and whether the transmission line is ac-coupled or dc-coupled.
The ADA4830-1 and ADA4830-2 are specifically designed to
perform as differential line receivers. The circuit in Figure 41
shows a detailed schematic of the ADA4830-1 and the ADV7180
configured for this function. The signal is received differentially
relative to the common of the source circuitry, and that voltage
is exactly reproduced with an attenuating gain of 0.50 V/V. This
is designed to keep the video signal within the allowed range of
the video decoder, which is typically 1 V p-p or less.
Figure 41. ADA4830-1 Driving an ADV7180 Video Decoder
The common-mode rejection vs. frequency, shown in Figure 14,
typically 65 dB at low frequencies, enables the recovery of video
Rev. C | Page 19 of 22
signals in the presence of large common-mode noise. The high
input impedance permits the ADA4830-1 and ADA4830-2 to
operate as a bridging amplifier across low impedance terminations
with negligible loading.
ADA4830-1/ADA4830-2 Data Sheet
R
T
+V
S
INN
VOUT
TO VIDEO
DECODER
GND
INP
ADA4830-1
75Ω
−
+
GND
LPF
LPF
+
+
STBENA+VS
4.7µF
0.1µF
+VS
ENABLE
(INPUT)
STB FLAG
(OUTPUT)
2.2µF
0.1µF
5kΩ
+V
S
(2.9V TO 5.5V)
STBENA+VS
ENABLE
(INPUT)
STB FLAG
(OUTPUT)
2.2µF
0.1µF
+V
S
(2.7V TO 3.6V)
VREF
+IN
–IN
–OUT
+OUT
−
+
75Ω
TWISTED
PAIR
37.5Ω
37.5Ω
FROM
IMAGER
OR VIDEO
ENCODER
×1
10020-041
FULLY DC-COUPLED TRANSMISSION LINE
The wide input common-mode range and high input impedance of
the ADA4830-1 and ADA4830-2allow them to be used in fully
dc-coupled transmission line applications in which there may be a
significant discrepancy between voltage levels at the ground pins of
the driver and receiver. As long as the voltage difference between
reference levels at the transmitter and receiver is within the
common-mode range of the receiver, very little current flow
results, and no image degradation should be anticipated.
Figure 42 shows an example configuration of a completely dccoupled transmission using a low impedance differential dr iver.
Figure 42. Differential Video Filter Driver and ADA4830-1Difference Amplifier
Rev. C | Page 20 of 22
Data Sheet ADA4830-1/ADA4830-2
2.44
2.34
2.24
TOP VIEW
8
1
5
4
0.30
0.25
0.20
BOTTOM VIEW
PIN 1 INDEX
AREA
SEATING
PLANE
0.80
0.75
0.70
1.70
1.60
1.50
0.203 REF
0.05 MAX
0.02 NOM
0.50 BSC
EXPOSED
PAD
3.10
3.00 SQ
2.90
PIN 1
INDICATOR
(R 0.15)
FOR PROPER CONNECTION OF
THE EXPOSED PAD, REFER TO
THE PIN CONFIGURATION AND
FUNCTION DESCRIPTIONS
SECTION OF THIS DATA SHEET.
COPLANARITY
0.08
0.50
0.40
0.30
COMPLIANT
TO
JEDEC STANDARDS MO-229-WEED
01-24-2011-B
3.10
3.00 SQ
2.90
0.30
0.23
0.18
1.75
1.60 SQ
1.45
08-16-2010-E
1
0.50
BSC
BOTTOM VIEWTOP VIEW
16
5
8
9
12
13
4
EXPOSED
PAD
PIN 1
INDICATOR
0.50
0.40
0.30
SEATING
PLANE
0.05 MAX
0.02 NOM
0.20 REF
0.25 MIN
COPLANARITY
0.08
PIN 1
INDICATOR
FOR PROP E R CONNECTION O F
THE EXPOSED PAD, REFER TO
THE PIN CO NFIGURATION AND
FUNCTIO N DE S CRIPTIONS
SECTION OF THIS DATA SHEET.
0.80
0.75
0.70
COMPLIANT
TO
JEDEC STANDARDS MO-220-WEED-6.
ADA4830-1WBCPZ-R7
−40°C to +125°C
8-Lead Lead Frame Chip Scale Package [LFCSP_WD]
CP-8-11
4H1
1500
PACKAGING AND ORDERING INFORMATION
OUTLINE DIMENSIONS
ORDERING GUIDE
1, 2
Model
ADA4830-1BCP-EBZ Evaluation Board
ADA4830-1BCPZ-R7 −40°C to +125°C 8-Lead Lead Frame Chip Scale Package [LFCSP_WD] CP-8-11 H30 1500
ADA4830-1BCPZ-R2 −40°C to +125°C 8-Lead Lead Frame Chip Scale Package [LFCSP_WD] CP-8-11 H30 250
ADA4830-2BCPZ-R7 −40°C to +125°C 16-Lead Lead Frame Chip Scale Package [LFCSP_WQ] CP-16-22 H31 1500
ADA4830-2BCPZ-R2 −40°C to +125°C 16-Lead Lead Frame Chip Scale Package [LFCSP_WQ] CP-16-22 H31 250
ADA4830-2WBCPZ-R7 −40°C to +125°C 16-Lead Lead Frame Chip Scale Package [LFCSP_WQ] CP-16-22 4H2 1500
1
Z = RoHS Compliant Part.
2
W = Qualified for Automotive Applications.
Temperature Range Package Description
Figure 43. 8-Lead Lead Frame Chip Scale Package [LFCSP_WD]
3 mm × 3 mm Body, Very Very Thin, Dual Lead
Figure 44. 16-Lead Lead Frame Chip Scale Package [LFCSP_WQ]
The ADA4830-1W and ADA4830-2W models are available with controlled manufacturing to support the quality and reliability
requirements of automotive applications. Note that these automotive models may have specifications that differ from the commercial
model; therefore, designers should review the Specifications section of this data sheet carefully. Only the automotive grade products
shown are available for use in automotive applications. Contact your local Analog Devices account representative for specific product
ordering information and to obtain the specific Automotive Reliability reports for these models.
trademarks are the proper ty of their
D10020-0-6/12(C)
www.analog.com/ADA4830-1/ADA4830-2
Rev. C | Page 22 of 22
Loading...
+ hidden pages
You need points to download manuals.
1 point = 1 manual.
You can buy points or you can get point for every manual you upload.